201122922 六、發明說明： 【發明所屬之技術領域】 本發明’係有關於指示體檢測裝置以及指示體檢測方 法’更詳細而言’係有關於能夠高速地檢測出複數的指示 體之指示體檢測裝置以及指示體檢測方法。 【先前技術】 於先前技術中，作爲在觸控面板等之中所使用的手指 或者是專用之筆等的指示體之位置檢測的方式，例如，係 提案有電阻膜方式、靜電耦合方式（靜電電容方式）等之 各種的感測方式。其中，於近年，靜電耦合方式之指示體 檢測裝置的開發係活躍地進行。 在靜電耦合方式中，係存在有表面型（Surface Capacitive Type)與投影型（Projected Capacitive Type) 之2種類的方式。表面型，例如係被適用在ATM ( Automated Teller Machine，現金自動提存機）等之中，投 影型，例如係被適用在行動電話等之中。另外，此兩種方 式，均係將感測電極與指示體（例如手指、靜電筆等）之 間的靜電耦合狀態之變化檢測出來，而檢測出指示體之位 置。 投影型靜電耦I合方式之指不體檢測裝置，例如係在玻 璃等之透明基板或是透明薄膜上，將電極以特定之圖案來 形成並構成之’並將指示體作了接近時之指示體與電極間 的靜電耦合狀態之變化檢測出來。於先前技術中，關於此 201122922 種方式的指示體檢測裝置，係提案有用以將其之構成作最 適化的各種之技術（例如，參考專利文獻1〜3 )。另外， 在專利文獻1中，係記載著將使用有正交展頻碼的代碼分 割多重化方式適用在多使用者觸控系統中之技術。在專利 文獻2中’係記載著使用有擬似隨機訊號之座標輸入裝置 。又，在專利文獻3中’係記載著在靜電電容型座標裝置 中所被使用的筆。 進而’在先前技術中’係提案有將投影型靜電耦合方 式更進一步作了發展的被稱作交叉點靜電耦合方式之方式 的指示體檢測裝置。於此’對於交叉點靜電耦合方式之指 示體檢測裝置的動作，參考圖面而作簡單說明。圖75 (a )以及（b )中’係分別展示有在交叉點靜電耦合方式之 指示體檢測裝置中的感測部近旁之槪略構成以及輸出訊號 波形。 一般而言，感測部900，係具備有由複數之送訊導體 9〇2所成的送訊導體群901、和由複數之受訊導體904所成 的受訊導體群903。另外，在送訊導體群901與受訊導體群 903之間’係被形成有絕緣層。送訊導體902，係爲延伸於 特定方向（圖75(a)中之X方向）上的具備有特定之形狀的 導體’複數之送訊導體902，係相互離開有特定之間隔地 被作並列配置。又，受訊導體904，係爲延伸於與送訊導 體902之延伸方向相交叉的方向（圖75(a)中之Y方向）上 的具備有特定之形狀的導體，複數之受訊導體904，係相 互離開有特定之間隔地被作並列配置。 -6- 201122922 在使用有此種構成之感測部900的指示體檢測裝置中 ’例如’係對於特定之送訊導體9 0 2而供給特定之訊號， 並將在被供給有該特定之訊號的送訊導體902與受訊導體 904之間的交點（以下，稱作交叉點）處所流動之電流的 變化’在全部的交叉點之每一者處而檢測出來。於此，在 此感測部9 0 0上，於手指等之指示體9 1 0所被放置之位置處 ’在送訊導體902處所流動之電流的—部份，係經由指示 體910而被作分流’藉由此，流入至受訊導體904處之電流 係改變。因此，藉由將供給了訊號之送訊導體902與電流 作改變的受訊導體904間之交叉點檢測出來，能夠檢測出 指示體910之位置。又，在交叉點靜電耦合方式之指示體 檢測裝置中，由於係在被形成於感測部900上之複數的交 叉點之每一者處而檢測出電流變化，因此，係能夠同時地 將複數之指示體檢測出來。 於此，對於交叉點靜電耦合方式之位置檢測的原理作 更具體之說明。例如，考慮如同圖75 ( a )中所示一般， 對於送訊導體Y6而供給特定之訊號，並將在送訊導體¥6上 之指示體9 1 0 (例如手指）的指示位置檢測出來的情況。 首先，在對於送訊導體Υ6而供給了訊號的狀態下，經由差 動放大器905而將在受訊導體X,以及χ2之各個處所流動之 電流的差檢測出來。接著，在經過特定時間後，將被連接 於差動放大器905處之受訊導體切換爲受訊導體Χ2以及Χ3 ，並將在兩受訊導體Χ2以及Χ3之各個處所流動的電流之差 檢測出來。反覆進行此動作，直到到達受訊導體ΧΜ處爲止 201122922 而後，將在送訊導體Y6與受訊導體間之各交叉點處的 差動放大器90 5之輸出訊號之準位變化求取出來。對於該 特性作了展示者，係爲圖75 ( b )。於此，此圖75 ( b )之 特性橫軸，係代表使受訊導體Xi〜Xm被時間性地依序作選 擇並連接於差動放大器905處所輸出的檢測訊號。另外， 藉由圖75 ( b )中的虛線所展示之特性，係代表實際上從 差動放大器905所輸出之訊號的準位變化，實線之特性， 係代表差動放大器905之輸出訊號的積分値之變化。 如圖7 5 ( a )中所示一般，指示體9 1 0 (手指），由於 係被放置在送訊導體Y6與受訊導體X5以及ΧΜ·5之間的交叉 點附近處，因此，在此交叉點附近所流動之電流係改變。 故而’如圖75 ( b )中所示一般，在對應於送訊導體人之 與受訊導體X5以及ΧΜ·5之間的交叉點附近之位置處，差動 放大器905之輸出訊號係改變，而其之積分値係改變。根 據此積分値之改變’能夠檢測出指示體9 1 0之位置。在先 前技術之指示體檢測裝置中，係將上述一般之檢測一面對 於送訊.導體902 —次一根地作切換—面進行。 [先前技術文獻] [專利文獻] [專利文獻1]日本特開2003-22158號公報 [專利文獻2]日本特開平9_222947號公報 [專利文獻3 ]日本特開平丨〇 _丨6 i 7 9 5號公報 201122922 【發明內容】 [發明所欲解決之課題] 然而，上述一般之先前技術的交叉點靜電耦合方式之 指示體檢測裝置，係對於構成各交叉點之送訊導體以及受 訊導體的每一者而進行訊號之供給與受訊處理，而進行指 示體之位置檢測處理。因此，係有著下述之問題：亦即是 ，若是對於全部的交叉點而進行位置檢測處理，則該處理 係會耗費長時間。例如，在具備有64根之送訊導體以及 1 28根之受訊導體的感測部中，若是將在各交叉點處之檢 測處理時間設爲2 5 6psec，則在全交叉點（8192個）中， 係成爲會耗費約2sec的檢測時間，而並不實用。 有鑑於上述問題，本發明，係以提供一種能夠將指示 體更高速的檢測出來之指示體檢測裝置以及指示體檢測方 法作爲目的。 [用以解決課題之手段] 本發明之指示體檢測裝置，係爲用以將位置在導體圖 案上之指示體檢測出來的指示體檢測裝置，該導體圖案， 係由被配置在第1方向上的複數之導體、和被配置在相對 於第1方向而交叉之第2方向上的複數之導體所成，該指示 體檢測裝置，其特徵爲，具備有：碼供給電路，係具備有 碼互爲相異的複數之碼列，並且用以對於構成導體圖案之 被配置在第1方向上的複數之導體的各個，而供給特定之 碼列；和相關値演算用碼供給電路，係爲用以供給與複數 -9 - 201122922 之碼列的各個而相對應了的相關値演算用碼；和相關演算 電路，係用以對於在被配置於第2方向上之各個的導體處 所產生之訊號、和相關値演算用碼，而進行兩者間之相關 演算，根據經由相關演算電路所求取出了的相關演算結果 ，來將位置在導體圖案上之指示體檢測出來。 又，本發明之指示體檢測方法，係爲用以將位置在導 體圖案上之指示體檢測出來的指示體檢測方法，該導體圖 案，係由被配置在第1方向上的複數之導體、和被配置在 相對於第1方向而交叉之第2方向上的複數之導體所成，該 指示體檢測方法，其特徵爲，具備有：碼供給步驟，係具 備有碼互爲相異的複數之碼列，並且用以對於構成導體圖 案之被配置在第1方向上的複數之導體的各個，而供給特 定之碼列；和相關値演算用碼供給步驟，係爲用以供給與 複數之碼列的各個而相對應了的相關値演算用碼；和相關 演算處理步驟，係用以對於在被配置於第2方向上之各個 的導體處所產生之訊號、和相關値演算用碼，而進行兩者 間之相關演算，根據經由相關演算處理步驟所求取出了的 相關演算結果，來將位置在導體圖案上之指示體檢測出來 [發明之效果] 在本發明中，指示體檢測裝置，係具備有：碼供給電 路，係具備有碼互爲相異的複數之碼列，並且用以對於構 成導體圖案之被配置在第1方向上的複數之導體的各個， -10- 201122922 而供給特定之碼列；和相關 以供給與複數之碼列的各個 :和相關演算電路，係用以 各個的導體處所產生之訊號 兩者間之相關演算，根據經 相關演算結果，來將位置在 。因此，若依據本發明，則 體檢測裝置中，係能夠更高 及其之指示位置同時地檢測 値演算用碼供給電路，係爲用 而相對應了的相關値演算用碼 ，對於在被配置於第2方向上之 、和相關値演算用碼，而進行 由相關演算電路所求取出了的 導體圖案上之指示體檢測出來 在交叉點靜電耦合方式之指示 速地將複數的指示體之存在以 出來。 【實施方式】 以下，針對本發明之指 方法的實施形態，參考圖面 在以下之實施形態中，雖係 作說明，但是，本發明係並 是將作了接近或者是接觸的 處理的裝置，則亦可適用在 1、 第1實施形態：基本 2、 第2實施形態：使用 構成例 3、 第3實施形態：使用 構成例 4、 第4實施形態：展頻 5、 第5實施形態：受訊 示體檢測裝置以及指示體檢測 而依下述順序作說明。另外， 列舉出指示體檢測裝置爲例並 不被限定於此實施形態，只要 指示體檢測出來並進行某些之 其他裝置中。 構成例 被作了 P S K調變後之展頻碼的 被作了 FSK調變後之展頻碼的 碼之其他供給方法 導體之選擇方法 -11 - 201122922 6、 第6實施形態：感測部之其他構成例 7、 第7實施形態：放大電路之其他構成例 8、 第8實施形態：懸浮狀態之檢測 <1、第1實施形態：基本構成例> 參考圖1乃至圖1 8，對於本發明之指示體檢測裝置以 及指示體檢測方法的基本構成例作說明。另外，本發明之 位置檢測方式，係採用根據感測部之送訊導體以及受訊導 體間的靜電耦合狀態之變化而檢測出指示體之位置的靜電 耦合方式。又，在本實施形態中，係針對對於全部的送訊 導體而將展頻碼（碼列）同時作供給，並藉由各個的受訊 導體而同時地進行訊號檢測之構成例，來進行說明。 〔指示體檢測裝置之構成〕 於圖1中，對於第1實施形態之指示體檢測裝置的槪略 構成圖作展示。 指示體檢測裝置1，主要係藉由感測部〗〇 〇、和送訊部 2 0 〇、和受訊部3 0 0、和對於送訊部2 〇 〇以及受訊部3 0 0的動 作作控制之控制電路4 0所構成。以下，針對各部之構成作 說明。 首先，參考圖1以及圖2’對於感測部1〇〇之構成作說 明。 感測部1 0 ’係具備有如同圖2中所示—般之略平板狀 的第1基板15、和由複數之送訊導體12所成之送訊導體群 -12- 201122922 1 1、和由複數之受訊導體1 4所成的受訊導體群1 3、和間隔 物1 6、以及平板狀之第2基板1 7。而，此感測部1 〇〇，係在 第1基板1 5上，依序將送訊導體1 2與間隔物1 6與受訊導體 Μ以及第2基板I7作配置，而形成之。故而，送訊導體12 與受訊導體1 4，係以隔著間隔物1 6而相對向的方式而被作 配置。 手指或是靜電筆等之指不體’係在第2基板1 7側（和 第2基板17之與第1基板I5相對向的面相反之側）處而被作 使用。故而，受訊導體14，係相較於送訊導體12而被更接 近於檢測面地作配置。另外。第1基板1 5以及第2基板1 7， 例如係使用具備有透過性之週知的玻璃基板，但是，代替 玻璃基板，係亦可使用由合成樹脂等所成的薄片狀（薄膜 狀）基材。 送訊導體12以及受訊導體14，例如，係藉由由ITO ( Indium Tin Oxide)膜所成之透明電極膜或者是銅箱等所 形成者。此送訊導體1 2之電極圖案，例如，係可如同下述 一般地而形成。首先，將藉由上述之材料等所形成了的電 極膜，例如藉由濺鍍法、蒸鍍法、塗布法等而形成在第1 基板1 5上。接著，對於所形成了的電極膜進行蝕刻’並形 成特定之電極圖案。受訊導體14之電極圖案，亦可同樣地 而形成在第2基板17上。另外，當將送訊導體12以及受訊 導體I4藉由銅箔來形成的情況時，亦可使用噴墨印表機’ 來將包含有銅粒子之墨水噴附至玻璃板等之上並形成特定 之電極圖案。另外，送訊導體12以及受訊導體14之形狀’ -13- 201122922 例如係可藉由直線狀（線形狀）導體來形成。又，送訊導 體1 2之形狀’係亦可設爲鑽石形狀、直線圖案等之形狀。 間隔物16’例如，係可藉由PVB( PolyVinyl Butyral )、EVA ( Ethylene Vinyl Acetate copolymer)、丙烯酸 系樹脂等的合成樹脂來形成之。又，間隔物1 6，係亦可藉 由高折射率（高介電率）之矽樹脂等來構成。進而，間隔 物1 6 ’係亦可藉由高折射率（高介電率）之油等的液體來 構成。如此這般，藉由在間隔物1 6處採用高折射率之素材 ，能夠將在間隔物1 6處之視差作抑制，而光學特性係被改 善。 當將間隔物1 6藉由合成樹脂來形成的情況時，例如， 係亦可將塑膠薄片挾持在送訊導體12與受訊導體14之間， 並一面對於導體間作真空抽氣，一面進行加壓以及加熱， 而形成間隔物1 6。又，例如，亦可使液體狀之合成樹脂流 入至送訊導體12以及受訊導體14之間，之後，使合成樹脂 固化，而形成間隔物1 6。 而，如圖1中所示一般，送訊導體群1 1，例如，係由 延伸於特定方向（圖1中之X方向）上的64根之送訊導體1 2 所構成。此送訊導體1 2，係分別相互離開有特定之間隔地 而被作並排配置。受訊導體群1 3，例如，係由延伸於與送 訊導體12之延伸方向相正交的方向（圖1中之Y方向）上而 形成的128根之受訊導體14所構成。此受訊導體I4，係分 別相互離開有特定之間隔地而被作並排配置。另外’送訊 導體12以及受訊導體14，係均可藉由直線狀（板狀）之導 -14 - 201122922 體來形成之。 如此這般，藉由將送訊導體群11與受訊導體群13隔著 間隔物16來作對向配置，在送訊導體群11與受訊導體群13 之間的交叉點處，係被形成有約0.5 p F之電容器。 又’在以下之說明中’雖係對於將被形成爲直線狀之 送訊導體12與受訊導體14以相正交之方式來作了配置的情 況而作例示並作說明，但是，送訊導體1 2以及受訊導體1 4 之形狀，係因應於實施形態而被適當作設定。又，亦可設 爲使送訊導體群1 1與受訊導體群13以正交以外之角度、例 如使送訊導體1 2與受訊導體1 4作傾斜交叉的構成。關於其 他實施形態，係於後再述。又，在電性特性上，較理想， 係將受訊導體1 4之寬幅設爲較送訊導體1 2之寬幅更細。此 係因爲，藉由使浮游電容減少，能夠將混入至受訊導體14 中之雜訊降低之故。 送訊導體1 2以及受訊導體1 4之配置間隔（節距），例 如，係以均使其成爲3.2mm的方式來作形成。另外，送訊 導體12以及受訊導體14之根數以及節距，係並不被限定於 此，而係因應於感測部1 〇〇之尺寸或是所需要之檢測精確 度等來適宜作設定。 以下，爲了便於說明，構成送訊導體群11之各送訊導 體12，係從接近受訊部3 00之側的送訊導體12起，而將其 之索引標號η設爲「1」〜「64」’並適宜將與各索引標號 η相對應的送訊導體1 2，亦標記爲送訊導體Υη。又，關於 受訊導體群1 3，亦同樣的，係從遠離送訊部200之側的受 -15- 201122922 訊導體14起，而將其之索引標號m設爲「1」〜「128」， 並適宜將與各索引標號m相對應的受訊導體1 4，亦標記爲 送訊導體Xm。 又，在此第1實施形態中，係將送訊導體群1 1以及受 訊導體群1 3分別分割爲1 6個的群組（區塊）。另外，在以 下之說明中，係將送訊導體群1 1之群組記述爲送訊區塊， 並將受訊導體群1 3之群組記述爲檢測區塊。 此送訊區塊，係藉由4根的送訊導體12而構成。而， 各送訊區塊，係藉由相鄰接（索引標號η爲連續）之4根的 送訊導體1 2所構成。更具體而言，在本實施形態中，係將 送訊導體群11，分割爲送訊區塊{Υ,〜Υ4} 、{Υ5〜Υ8} 、…、{丫57〜丫6。}以及{丫61〜丫64}。 同樣的，檢測區塊，係藉由8根的受訊導體Μ而構成 。而，各檢測區塊，係藉由相鄰接（索引標號m爲連續） 之8根的受訊導體14所構成。更具體而言，在本實施形態 中，係將受訊導體群1 3，分割爲檢測區塊{ X!〜X8 } ' { x9 〜X16 } ..... { X113 〜χ120 }以及{ X121 〜Xi28 }。但 是，本發明，係並不被限定於此，在1個的群組內之導體 的根數或者是群組數、群組之形態（隸屬於同一群組之導 體的位置關係等），係爲因應於感測部1 〇〇之尺寸或者是 所需要之檢測速度等而適宜作設定者。詳細內容，係於後 再述。 接下來，針對送訊部200作說明。送訊部200 ’係如圖 1中所示一般，具備有：展頻碼供給電路21、和送訊導體 -16- 201122922 選擇電路22、和時脈產生電路23。送訊導體選擇電路22、 展頻碼供給電路2 1以及時脈產生電路2 3，係依此順序而從 感測部1 〇〇側來作配置。展頻碼供給電路2 1，係被連接於 後述之控制電路40與時脈產生電路23處，並被輸入有從時 脈產生電路23所輸出之時脈訊號。另外，從此時脈產生電 路23所輸出之時脈，係亦被輸入至後述之控制電路40中。 接著，參考圖3，針對展頻碼供給電路21作說明。於 此圖3中，展示展頻碼供給電路21的槪略構成之其中一例 〇 此第1實施形態中之展頻碼供給電路2 1，係爲以使在 後述之受訊部3 00的相關値算出電路34中而因應於指示體 之有無所得到之値成爲特定之値的方式，來對於送訊導體 1 2之各個而供給具備有特定位元數之碼、例如供給展頻碼 的電路。此展頻碼供給電路2 1，例如，係藉由與送訊導體 群11之送訊區塊的數量同數量（16個）之展頻碼產生電路 24所構成。此複數之展頻碼產生電路24，係根據後述之控 制電路40的控制，而產生分別具備有2η位元之碼長度（η :整數）的展頻碼〇1{(1^:1〜16之整數）。藉由各個的展 頻碼產生電路24所產生之展頻碼Ck，例如係與從時脈產生 電路23所輸出之時脈訊號同步地而被產生，並且，在此時 脈訊號之上揚的時序處，而輸出所產生了的展頻碼之第η 個的碼。另外，此展頻碼供給電路21，係亦可設爲下述之 構成：亦即是，在ROM等之中，而將根據展頻碼所產生了 的資料預先作保持，並藉由對於ROM之讀出位址作控制， -17- 201122922 而將用以供給至各送訊導體處之訊號作輸出。以下，將藉 由16個的展頻碼產生電路24所產生之16個的展頻碼，分別 稱作展頻碼C!、C2、C3.....C16。在此16個的展頻碼c, 〜C ! 6之中，例如係可適用分別被作了同步的哈德瑪得碼 (Hadamard code )。關於此哈德瑪得碼，係於後再述。 另外，如同後述一般，本發明，係亦可使用藉由P S K 調變或者是FSK調變等而作了調變之展頻碼。又，在採用 了 CDMA之無線通訊技術中，由於所謂「碼片」之表面係 —般性地被使用，因此，在以下之說明中，係將通訊速度 稱作碼片速率。 接著，參考圖4，針對送訊導體選擇電路22作說明。 於此圖4中，展示送訊導體選擇電路22之內部構成。 送訊導體選擇電路22，係爲用以將從展頻碼供給電路 21所供給而來之展頻碼（^〜（：16選擇性地供給至送訊導體 12處之電路。構成送訊導體群11之各送訊導體12,係被分 割爲將4根的送訊導體12作爲1個群組之16個的送訊區塊25 ，送訊導體選擇電路22，係由與各送訊區塊25相同數量（ 16個）之開關22 a所構成。各開關22a之4個的輸出端子22b ，係分別被連接於相對應之送訊導體12處，1個的輸入端 子22c，係被連接於相對應的展頻碼產生電路24 (參考圖3 )之輸出端子處。而，各開關22a，係成爲以特定之時間 間隔（具體而言，係爲從時脈產生電路23所輸出之時脈的 16週期之量的時間間隔），來將被選擇了的送訊導體12與 將相對應之特定的展頻碼Ck作輸出之展頻碼產生電路24的 -18- 201122922 輸出端子作連接之構造。另外，各開關22a之切換動作， 係藉由控制電路40而被作控制。 接著，參考圖5，針對送訊導體選擇電路22之切換動 作的其中一例作說明。於此，假設各送訊區塊25，係設爲 將最大之索引標號的送訊導體1 2 (亦即是導體Y4、Y8、… 、Y6q以及Υ64 )經由開關22a來分別與相對應之展頻碼產 生電路24的輸出端子作連接者（圖4中所示之狀態）。 首先，從構成展頻碼供給電路21之各展頻碼產生電路 24所輸出了的展頻碼C,〜C16，係分別被同時性地供給至 藉由開關22a所作了選擇的16根之送訊導體12處。於此狀 態下，在特定時間（時脈之1 5週期）之間，而進行指示體 之位置檢測。接著，在經過特定時間後，亦即是，若是對 於被開關22 a所選擇了的各送訊導體12而進行之展頻碼C, 〜C! 6的供給結束，則開關22a係將被連接於展頻碼產生電 路24處之送訊導體12切換至位置在使索引標號η減少之方 向處的相鄰接之送訊導體12 (亦即是送訊導體Υ2、Υ6、… 、Υ58以及Υ62 )處。而，在此切換後，對於所選擇了的16 根之送訊導體1 2而同時地供給從各展頻碼產生電路24所輸 出之展頻碼C ,〜C , 6，並進行位置檢測。一面反覆進行此 種動作，一面對於全部的送訊導體12而進行展頻碼之供給 〇 而後，在各送訊區塊25內之最小索引標號的送訊導體 12 (亦即是送訊導體Υι、γ5.....Υ57以及Y61 )藉由開關 2 2a而被作了選擇，並進行了展頻碼Cl〜C16之供給後，再 -19- 201122922 度藉由開關22a而對於各送訊區塊25內之最大索引標號的 送訊導體12作選擇’並在各區塊內而反覆進行上述動作。 另外’送訊導體12之切換動作的處理程序，係並不被限定 於圖5中所示之例。例如，在圖5中，送訊導體12之切換動 作’係針對在將供給至各個的送訊導體12處之展頻碼Ck作 了供給後再進行切換的情況而作了例示，但是，送訊導體 12之切換’係亦可設爲在每供給1碼片時便作切換。針對 其他之變形例，係於後詳述。 如同上述一般，複數之送訊導體1 2，係被區分爲各群' 組爲由特定數量M(M爲^2之整數，在圖5之例中，係爲 M = 4 )之導體所成的複數之群組。而，經由展頻碼供給電 路2 1所產生了的各個的展頻碼C 1〜C , 6，係被供給至構成 各群組之特定的送訊導體12處，並且在各群組內，對於供 給該展頻碼之導體依序作切換。藉由如此這般地來構成， 能夠將用以進行位置檢測之展頻碼同時性地供給至複數之 送訊導體12處。於此例中，由於係同時地供給有16種之展 頻碼，因此，在用以進行位置檢測之訊號的送訊中所耗費 的時間，係能夠縮短至先前技術之1 / 1 6。 接下來，針對受訊部3 00作說明。受訊部300，係如圖 1中所示一般，具備有：受訊導體選擇電路31、和放大電 路32、和A/D (Analog to Digital)變換電路33、和相關 値算出電路34、和位置檢測電路35。藉由受訊部3 00之相 關値算出電路34所得到了的相關値，係相當於指示體之檢 測狀態，由該指示體之檢測狀態，來藉由位置算出電路3 5 -20- 201122922 而算出指示體之位置。 接著，參考圖6，針對受訊導體選擇電路31作說明。 構成受訊導體群13之各受訊導體14’係被區分爲將8 根的受訊導體1 4作爲1個群組之1 6個的檢測區塊3 6 °而’ 受訊導體選擇電路31，係由與此〜檢測區塊36相同數量（16 個）之開關3 1 a所成。而，此開關3 1 a ’係在各檢測區塊3 6 之每一者中而分別各被設置有1個，並根據後述之控制電 路40的控制訊號，來將被選擇的受訊導體14作切換。 各開關3 1 a之輸入側之8個的端子3 1 b，係分別被與相 對應之受訊導體14相連接。又，各開關31a之輸出側的1個 的端子31c，係被與相對應之一個的1/ V變換電路32a (於 後再述）之輸入端子相連接。進而，各開關3 1 a，係以特 定之時間間隔（送訊導體選擇電路22之開關22a的切換時 序之4倍的週期），而將與1/ V變換電路32a作連接之受訊 導體I4作切換。而後，從1/ V變換電路32a而來之輸出訊 號’係在未圖示之放大器處而被放大爲特定之訊號準位， 之後’係經由切換開關32d而被輸出至A/D變換電路33處 〇 接著’參考圖7’對於此受訊導體選擇電路31之切換 動作作說明。於此，各檢測區塊36 ’假設係經由開關3 i a 而使最小索引標號之受訊導體14 (亦即是受訊導體乂1、χ9 .....以及)與放大電路32作連接（圖6之狀態）。 首先，在此圖6中所示之狀態下，於特定時間之間， 受訊導體選擇電路31係對於複數之受訊導體〗4同時作選擇 -21 - 201122922 ，並得到身爲電流訊號之從各檢測區塊3 6而來的輸出訊號 S 1、S 2、…、s I 6。 接著，若是經過特定之時間，則受訊導體選擇電路3 1 之各開關31a，係將受訊導體14，切換爲位置在使其索引 標號m增加之方向的位置處之相鄰接的受訊導體14，亦即 是，切換爲受訊導體X2、X1Q.....以及X122。而，在此切 換後，係得到從被與開關31a作了連接的受訊導體X2、X,。 .....Xll4以及X122所輸出了的新的輸出訊號Si、S2、… 、S16。之後，受訊導體選擇電路31之開關31a，係反覆進 行此種切換動作。 而後，開關3 1 a係被與各檢測區塊3 6內的最大索引標 號之受訊導體14 (亦即是受訊導體X8、X16.....X12Q以及201122922 VI. Description of the Invention: [Technical Field of the Invention] The present invention relates to a pointer detection apparatus and a pointer detection method. More specifically, the indicator detection of a pointer capable of detecting a complex number at a high speed is performed. Device and indicator detection method. [Prior Art] In the prior art, as a method of detecting a position of a finger used in a touch panel or the like, or a pointer such as a dedicated pen, for example, a resistive film method or an electrostatic coupling method (electrostatic system) is proposed. Various sensing methods such as capacitive mode). Among them, in recent years, the development of the electrostatic coupling type indicator detecting device has been actively carried out. In the electrostatic coupling method, there are two types of surface type (Surface Capacitive Type) and Projected Capacitive Type. The surface type is applied to, for example, an ATM (Automated Teller Machine), and the projection type is applied to, for example, a mobile phone or the like. In addition, both of these methods detect the change in the electrostatic coupling state between the sensing electrode and the indicator (e.g., a finger, an electrostatic pen, etc.), and detect the position of the pointer. The projection type electrostatic coupling type I refers to a non-body detecting device, for example, which is formed on a transparent substrate such as glass or a transparent film, and the electrode is formed in a specific pattern and constitutes an indication when the indicator body is approached. A change in the electrostatic coupling state between the body and the electrode is detected. In the prior art, the indicator detecting device of the 201122922 method is proposed to be used to optimize the configuration thereof (for example, refer to Patent Documents 1 to 3). Further, Patent Document 1 describes a technique in which a code division multiplexing method using orthogonal spreading codes is applied to a multi-user touch system. In Patent Document 2, a coordinate input device using a pseudo random signal is used. Further, in Patent Document 3, a pen used in a capacitance type coordinate device is described. Further, in the prior art, a pointer detecting device called a cross-point electrostatic coupling method in which a projection type electrostatic coupling method has been further developed has been proposed. Here, the operation of the indicator detecting device of the cross-point electrostatic coupling method will be briefly described with reference to the drawings. Fig. 75 (a) and (b) show the schematic configuration and the output signal waveform in the vicinity of the sensing portion in the pointer detecting device of the electrostatic coupling type at the intersection. Generally, the sensing unit 900 is provided with a transmission conductor group 901 formed by a plurality of transmission conductors 9A and a signal conductor group 903 formed by a plurality of signal conductors 904. Further, an insulating layer is formed between the transmission conductor group 901 and the received conductor group 903. The transmitting conductor 902 is a plurality of conductors 902 having a specific shape and extending in a specific direction (the X direction in FIG. 75(a)), and are arranged side by side at a certain interval. Configuration. Further, the signal conductor 904 is a conductor having a specific shape extending in a direction intersecting the extending direction of the transmission conductor 902 (the Y direction in FIG. 75(a)), and the plurality of signal conductors 904 are extended. They are arranged side by side at a specific interval from each other. -6-201122922 In the indicator detecting device using the sensing unit 900 having such a configuration, 'for example, 'a specific signal is supplied to a specific transmitting conductor 902, and the specific signal is supplied thereto. The change in the current flowing at the intersection between the signal conductor 902 and the signal conductor 904 (hereinafter referred to as the intersection) is detected at each of all the intersections. Here, in the sensing portion 900, the portion of the current flowing at the transmitting conductor 902 at the position where the pointer 9 1 0 of the finger or the like is placed is via the indicator 910. By shunting, the current flowing into the signal conductor 904 changes. Therefore, the position of the pointer 910 can be detected by detecting the intersection between the signal transmission conductor 902 to which the signal is supplied and the signal conductor 904 whose current is changed. Further, in the pointer detecting device of the cross-point electrostatic coupling type, since the current change is detected at each of the plurality of intersections formed on the sensing unit 900, the plural can be simultaneously The indicator is detected. Here, the principle of position detection of the electrostatic coupling method at the intersection is described in more detail. For example, consider that, as shown in FIG. 75(a), a specific signal is supplied to the transmission conductor Y6, and the indication position of the indicator 9 1 0 (for example, a finger) on the transmission conductor ¥6 is detected. Happening. First, in a state where a signal is supplied to the transmission conductor Υ 6, the difference between the currents flowing through the respective portions of the received conductors X and χ2 is detected via the differential amplifier 905. Then, after a certain period of time elapses, the signal conductor connected to the differential amplifier 905 is switched to the signal conductors Χ2 and Χ3, and the difference between the currents flowing between the two signal conductors Χ2 and Χ3 is detected. . This action is repeated until it reaches the receiving conductor. 201122922 Then, the level change of the output signal of the differential amplifier 90 5 at each intersection between the transmitting conductor Y6 and the received conductor is extracted. The exhibitor for this feature is shown in Figure 75(b). Here, the horizontal axis of the characteristic of Fig. 75(b) represents a detection signal which is outputted by the signalling conductors Xi to Xm in time series and connected to the differential amplifier 905. In addition, the characteristic shown by the broken line in FIG. 75(b) represents the level change of the signal actually outputted from the differential amplifier 905, and the characteristic of the solid line represents the output signal of the differential amplifier 905. The change in points. As shown in Fig. 7 5 (a), the indicator body 9 1 0 (finger) is placed near the intersection between the signal conductor Y6 and the signal conductor X5 and ΧΜ·5, so The current flowing near this intersection changes. Therefore, as shown in FIG. 75(b), the output signal of the differential amplifier 905 changes at a position corresponding to the intersection between the signal conductor and the signal conductor X5 and ΧΜ5. And its points are changed. Based on the change of the integral ’, the position of the pointer 910 can be detected. In the pointer detecting device of the prior art, the above-described general detection is performed on the face-to-face with the conductor 902 being switched one by one. [PRIOR ART DOCUMENT] [Patent Document 1] Japanese Laid-Open Patent Publication No. Hei. No. Hei. No. Hei. No. Hei. SUMMARY OF THE INVENTION [Problem to be Solved by the Invention] However, the above-described conventional prior art cross-point electrostatic coupling type indicator detecting device is for each of the transmission conductor and the signal conductor constituting each intersection. In one case, the supply and reception processing of the signal is performed, and the position detection processing of the pointer is performed. Therefore, there is a problem that if the position detection processing is performed for all the intersections, the processing takes a long time. For example, in a sensing unit having 64 transmission conductors and 128 signal conductors, if the detection processing time at each intersection is 2 6 6 sec, then at the full intersection (8192) In the case, it takes about 2 seconds to detect, and it is not practical. In view of the above problems, the present invention has an object of providing a pointer detecting device and a pointer detecting method capable of detecting a pointer at a higher speed. [Means for Solving the Problem] The pointer detecting device of the present invention is a pointer detecting device for detecting a pointer positioned on a conductor pattern, and the conductor pattern is disposed in the first direction. The conductor of the plurality of conductors and the plurality of conductors arranged in the second direction intersecting with respect to the first direction, the pointer detecting device is characterized in that: the code supply circuit is provided with code mutual a code sequence of different plural numbers, and for supplying a specific code sequence to each of the plurality of conductors constituting the conductor pattern arranged in the first direction; and the correlation 値 calculation code supply circuit is used Corresponding to the 値 calculus code corresponding to each of the code columns of the plural -9 - 201122922; and the related calculus circuit for generating signals for the conductors disposed in the second direction, And the correlation calculus code, and the correlation calculation between the two is performed, and the indicator on the conductor pattern is detected based on the correlation calculation result obtained by the correlation calculation circuit. . Further, the pointer detecting method of the present invention is a pointer detecting method for detecting a pointer whose position is on a conductor pattern, the conductor pattern being a plurality of conductors arranged in the first direction, and A plurality of conductors disposed in a second direction intersecting with respect to the first direction, the pointer detecting method characterized by comprising: a code supply step having a plurality of codes having mutually different codes a code sequence for supplying a specific code sequence to each of a plurality of conductors constituting the conductor pattern arranged in the first direction; and a correlation 値 calculation code supply step for supplying the code of the complex number Corresponding calculus codes corresponding to the columns; and related arithmetic processing steps for performing signals generated on the conductors disposed in the second direction and associated calculus codes The correlation calculation between the two is based on the correlation calculation result obtained by the correlation calculation processing step, and the indicator on the conductor pattern is detected. [Effect of the invention] In the present invention, the indicator detecting device is provided with a code supply circuit including a plurality of code sequences having mutually different codes, and for a plurality of conductors arranged in the first direction constituting the conductor pattern. Each, -10- 201122922 provides a specific code train; and each of the associated code columns of supply and complex: and the associated calculus circuit are used for the correlation calculation between the signals generated by the respective conductors, according to the correlation The result of the calculation, to position the position. Therefore, according to the present invention, in the body detecting device, the 値 calculation code supply circuit can be detected at the same time as the higher and the indicated position, and the associated 値 calculation code is used for the body detection device. In the second direction, and the correlation 値 calculation code, the indicator on the conductor pattern extracted by the correlation calculation circuit detects the presence of the plurality of indicator at the intersection of the electrostatic coupling method at the intersection. Come out. [Embodiment] Hereinafter, embodiments of the method of the present invention will be described with reference to the drawings in the following embodiments. However, the present invention is a device that performs processing close to or in contact with each other. The first embodiment can be applied to the first embodiment: the second embodiment, the second embodiment, the configuration example 3, the third embodiment, the configuration example 4, the fourth embodiment: the spread spectrum 5, and the fifth embodiment: The signal detecting device and the pointer detecting are described in the following order. Further, the indicator detecting device is exemplified and is not limited to this embodiment, as long as the indicator is detected and performed in some other devices. Other methods for selecting the code of the spread spectrum code after the FSK modulation of the spread spectrum code after the PSK modulation is selected. -11 - 201122922 6. The sixth embodiment: the sensing unit Other Configuration Example 7 and Seventh Embodiment: Other Configuration Example 8 of the Amplifying Circuit, Eighth Embodiment: Detection of Floating State <1, First Embodiment: Basic Configuration Example> Referring to FIG. 1 to FIG. A basic configuration example of the pointer detecting device and the pointer detecting method of the present invention will be described. Further, the position detecting method of the present invention employs an electrostatic coupling method in which the position of the pointer is detected based on a change in the electrostatic coupling state between the transmitting conductor and the receiving conductor of the sensing portion. Further, in the present embodiment, a description will be given of a configuration example in which a spreading code (code sequence) is simultaneously supplied to all of the transmission conductors, and signal detection is simultaneously performed by each of the received conductors. . [Configuration of Indicator Detection Apparatus] Fig. 1 is a schematic view showing a schematic configuration of the indicator detection apparatus according to the first embodiment. The pointer detecting device 1 mainly operates by the sensing unit 〇〇, the transmitting unit 20 〇, and the receiving unit 300, and the transmitting unit 2 〇〇 and the receiving unit 300 The control circuit 40 is configured to be controlled. Hereinafter, the configuration of each unit will be described. First, the configuration of the sensing unit 1A will be described with reference to Figs. 1 and 2'. The sensing unit 10' is provided with a first substrate 15 having a substantially flat shape as shown in FIG. 2, and a transmission conductor group -12-201122922 1 1 formed by a plurality of transmission conductors 12, and The signal conductor group 13 formed by the plurality of signal conductors 14 and the spacers 16 and the second substrate 17 having a flat shape. On the other hand, the sensing unit 1 is formed by sequentially arranging the transmission conductor 12 and the spacer 16 and the signal receiving conductor Μ and the second substrate I7 on the first substrate 15. Therefore, the signal conductor 12 and the signal conductor 14 are disposed to face each other with the spacer 16 interposed therebetween. A finger or an electrostatic pen or the like is used in the second substrate 17 side (the side opposite to the surface of the second substrate 17 facing the first substrate I5). Therefore, the signal conductor 14 is disposed closer to the detection surface than the signal conductor 12. Also. For example, a glass substrate having a well-known transparency is used as the first substrate 1 5 and the second substrate 1 7 . However, instead of the glass substrate, a sheet-like (film-like) group made of synthetic resin or the like may be used. material. The signal conductor 12 and the signal conductor 14 are formed, for example, by a transparent electrode film made of an ITO (Indium Tin Oxide) film or a copper box. The electrode pattern of the signal conductor 12 can be formed, for example, as follows. First, an electrode film formed by the above-described material or the like is formed on the first substrate 15 by, for example, a sputtering method, a vapor deposition method, a coating method, or the like. Next, the formed electrode film is etched' and a specific electrode pattern is formed. The electrode pattern of the signal conductor 14 can also be formed on the second substrate 17 in the same manner. Further, when the signal conductor 12 and the signal conductor I4 are formed of a copper foil, an ink jet printer can be used to eject ink containing copper particles onto a glass plate or the like and form. Specific electrode pattern. Further, the shape of the signal conductor 12 and the signal conductor 14 '13-201122922 can be formed, for example, by a linear (line shape) conductor. Further, the shape of the transmitting conductor 1 2 may be a shape such as a diamond shape or a straight line pattern. The spacer 16' can be formed, for example, by a synthetic resin such as PVB (PolyVinyl Butyral), EVA (Ethylene Vinyl Acetate copolymer), or an acrylic resin. Further, the spacers 16 may be formed of a high refractive index (high dielectric constant) ruthenium resin or the like. Further, the spacer 16' may be formed of a liquid such as a high refractive index (high dielectric constant) oil. In this manner, by using a material having a high refractive index at the spacer 16, the parallax at the spacer 16 can be suppressed, and the optical characteristics are improved. When the spacer 16 is formed of a synthetic resin, for example, the plastic sheet may be held between the signal conductor 12 and the signal conductor 14, and vacuum evacuated between the conductors. Pressurization and heating form spacers 16. Further, for example, a liquid synthetic resin may be introduced between the signal conductor 12 and the signal conductor 14, and then the synthetic resin may be solidified to form a spacer 16. Further, as shown in Fig. 1, the transmission conductor group 1, for example, is constituted by 64 transmission conductors 1 2 extending in a specific direction (X direction in Fig. 1). The signal transmission conductors 12 are arranged side by side with a specific interval apart from each other. The received conductor group 13 is composed of, for example, 128 signal conductors 14 which are formed in a direction (Y direction in Fig. 1) which is orthogonal to the extending direction of the transmitting conductor 12. The signal conductors I4 are arranged side by side at a specific interval apart from each other. Further, the 'sending conductor 12 and the signal conductor 14 can be formed by a linear (plate-shaped) guide -14 - 201122922. In this manner, by disposing the transmission conductor group 11 and the signal receiving conductor group 13 with the spacer 16 interposed therebetween, the intersection between the transmission conductor group 11 and the signal conductor group 13 is formed. There is a capacitor of about 0.5 p F. In the following description, the case where the transmission conductor 12 and the signal conductor 14 which are formed in a straight line are arranged to be orthogonal to each other is exemplified and described, but the transmission is performed. The shape of the conductor 1 2 and the received conductor 14 is appropriately set in accordance with the embodiment. Further, the transmission conductor group 11 and the received conductor group 13 may be formed such that the transmission conductor 12 and the signal conductor 14 are obliquely intersected at an angle other than the orthogonal direction. Other embodiments will be described later. Further, in terms of electrical characteristics, it is preferable to set the width of the signal conductor 14 to be thinner than the width of the transmission conductor 12. This is because the noise mixed into the signal conductor 14 can be reduced by reducing the floating capacitance. The arrangement interval (pitch) of the transmission conductor 1 2 and the signal receiving conductor 14 is formed, for example, so as to be 3.2 mm. In addition, the number and pitch of the signal conductor 12 and the signal conductor 14 are not limited thereto, and are suitable for the size of the sensing unit 1 or the required detection accuracy. set up. Hereinafter, for convenience of explanation, each of the transmission conductors 12 constituting the transmission conductor group 11 is set from the transmission conductor 12 on the side close to the receiving unit 300, and its index number η is set to "1" to "" 64"' is also suitable for marking the signal conductor 12 corresponding to each index number η as the signal conductor Υn. Further, the same is true for the received conductor group 13 from the -15-201122922 conductor 14 away from the side of the transmitting unit 200, and the index number m is set to "1" to "128". And it is preferable to mark the received conductor 14 corresponding to each index mark m as the transmission conductor Xm. Further, in the first embodiment, the transmission conductor group 11 and the signal conductor group 13 are divided into 16 groups (blocks). Further, in the following description, the group of the transmission conductor group 1 1 is described as a transmission block, and the group of the received conductor group 13 is described as a detection block. This communication block is constituted by four transmission conductors 12. Further, each of the transmission blocks is constituted by four transmission conductors 12 adjacent to each other (the index number n is continuous). More specifically, in the present embodiment, the transmission conductor group 11 is divided into communication blocks {Υ, Υ4}, {Υ5 to Υ8}, ..., {丫57 to 丫6. } and {丫61~丫64}. Similarly, the detection block is constructed by eight signal conductors. Further, each detection block is constituted by eight received conductors 14 adjacent to each other (index number m is continuous). More specifically, in the present embodiment, the received conductor group 13 is divided into detection blocks { X! to X8 } ' { x9 to X16 } ..... { X113 χ 120 } and { X121 ~Xi28 }. However, the present invention is not limited thereto, and the number of conductors in one group or the number of groups, the form of a group (positional relationship of conductors belonging to the same group, etc.) It is suitable for setting according to the size of the sensing unit 1 or the required detection speed. The details will be described later. Next, the transmission unit 200 will be described. The transmitting unit 200' is generally provided with a spread spectrum code supply circuit 21, a transmission conductor -16 - 201122922 selection circuit 22, and a clock generation circuit 23 as shown in Fig. 1 . The transmission conductor selection circuit 22, the spread spectrum code supply circuit 21, and the clock generation circuit 23 are arranged from the side of the sensing unit 1 in this order. The spread code supply circuit 2 1 is connected to a control circuit 40 and a clock generation circuit 23 which will be described later, and is supplied with a clock signal output from the clock generation circuit 23. Further, the clock output from the pulse generating circuit 23 is also input to the control circuit 40 which will be described later. Next, the spread code supply circuit 21 will be described with reference to FIG. 3. In Fig. 3, an example of a schematic configuration of the spread spectrum code supply circuit 21 is shown. The spread code supply circuit 2 1 of the first embodiment is related to the signal receiving unit 300 which will be described later. In the calculation circuit 34, a signal having a specific number of bits, for example, a supply of a spread spectrum code, is supplied to each of the transmission conductors 12 in response to a defect obtained by the presence or absence of the pointer. . The spread code supply circuit 2 1, for example, is constituted by the same number (16) of spread code generation circuits 24 as the number of transmission blocks of the transmission conductor group 11. The plurality of spread spectrum code generating circuits 24 generate spread spectrum codes 〇1 (1^: 1 to 16) each having a code length (η: integer) of 2 η bits, according to control of the control circuit 40 to be described later. The integer). The spread code Ck generated by each of the spread code generating circuits 24 is generated, for example, in synchronization with the clock signal output from the clock generating circuit 23, and the timing of the pulse signal is raised at this time. And output the nth code of the spread code generated. Further, the spread code supply circuit 21 may be configured to hold data generated in accordance with the spread spectrum code in advance in the ROM or the like, and to hold the ROM in advance. The read address is controlled, -17-201122922, and the signal for supply to each of the signal conductors is output. Hereinafter, the 16 spreading codes generated by the 16 spreading code generating circuits 24 are referred to as spreading codes C!, C2, C3, ..., C16, respectively. Among the 16 spread codes c, ~C! 6, for example, a Hadamard code which is synchronized separately can be applied. This Hadmar code is described later. Further, as will be described later, in the present invention, a spread code which is modulated by P S K modulation or FSK modulation or the like may be used. Further, in the wireless communication technology using CDMA, since the surface of the "chip" is used in general, the communication speed is referred to as the chip rate in the following description. Next, the transmission conductor selection circuit 22 will be described with reference to FIG. In Fig. 4, the internal configuration of the transmission conductor selection circuit 22 is shown. The transmission conductor selection circuit 22 is a circuit for selectively supplying a spread spectrum code (^~ (16) to the transmission conductor 12 from the spread spectrum code supply circuit 21. Each of the transmission conductors 12 of the group 11 is divided into four transmission conductors 12 as a group of 16 transmission blocks 25, a transmission conductor selection circuit 22, and each communication area. The same number (16) of switches 22a are formed in block 25. The four output terminals 22b of each switch 22a are respectively connected to the corresponding signal conductor 12, and one input terminal 22c is connected. At the output terminals of the corresponding spread code generating circuit 24 (refer to FIG. 3), each switch 22a is at a specific time interval (specifically, when outputted from the clock generating circuit 23) The time interval of the 16 cycles of the pulse) is used to connect the selected signal conductor 12 to the -18-201122922 output terminal of the spread code generation circuit 24 that outputs the corresponding spread code Ck. In addition, the switching operation of each switch 22a is controlled by the control circuit 40. Next, an example of the switching operation of the transmission conductor selection circuit 22 will be described with reference to Fig. 5. Here, it is assumed that each of the transmission blocks 25 is set as the transmission index 1 2 having the largest index number (also That is, the conductors Y4, Y8, ..., Y6q, and Υ64) are respectively connected to the output terminals of the corresponding spread code generating circuit 24 via the switch 22a (the state shown in Fig. 4). The spread codes C, C16, which are output from the spread code generation circuits 24 of the code supply circuit 21, are simultaneously supplied to the 16 transmission conductors 12 selected by the switch 22a. In this state, the position detection of the pointer is performed between the specific time (15 cycles of the clock). Then, after a certain period of time has elapsed, that is, if the transmission is selected for the switch 22a When the supply of the spreading code C, ~C! 6 by the conductor 12 is completed, the switch 22a switches the transmission conductor 12 connected to the spreading code generating circuit 24 to the position in the direction in which the index number η is decreased. Adjacent communication conductor 12 (ie, a transmission conductor) 2. Υ6, ..., Υ58, and Υ62), and after the switching, the spreading codes output from the respective spreading code generating circuits 24 are simultaneously supplied to the selected 16 transmitting conductors 1 2 . C, ~C, 6, and position detection. While performing such an operation in turn, the supply of the spreading code is performed for all of the transmission conductors 12, and then the minimum index number in each of the transmission blocks 25. The transmission conductors 12 (i.e., the transmission conductors Υι, γ5.....Υ57 and Y61) are selected by the switch 2 2a, and the supply of the spreading codes C1 to C16 is performed, and then -19 - 201122922 The selection of the transmission conductor 12 of the largest index number in each of the communication blocks 25 by the switch 22a is selected and repeated in the respective blocks. Further, the processing procedure of the switching operation of the transmission conductor 12 is not limited to the example shown in Fig. 5. For example, in FIG. 5, the switching operation of the transmission conductor 12 is exemplified for the case where the spreading code Ck supplied to each of the transmission conductors 12 is supplied and then switched, but the transmission is performed. The switching of the conductor 12 can also be set to switch every 1 chip. Other modifications will be described in detail later. As described above, the plurality of transmission conductors 12 are divided into groups of groups by a conductor of a specific number M (M is an integer of ^2, in the example of Fig. 5, M = 4). Group of plurals. Further, the respective spread codes C 1 to C , 6 generated by the spread code supply circuit 2 1 are supplied to the specific transmission conductors 12 constituting each group, and within each group, The conductors supplying the spread spectrum code are sequentially switched. With such a configuration, the spreading code for position detection can be simultaneously supplied to the plurality of signal conductors 12. In this example, since 16 kinds of spreading codes are simultaneously supplied, the time spent in the transmission of the signal for position detection can be shortened to 1 / 16 of the prior art. Next, an explanation will be given for the receiving unit 300. The receiving unit 300 is generally provided with a signal receiving conductor selection circuit 31, an amplifying circuit 32, an A/D (Analog to Digital) converting circuit 33, and an associated 値 calculating circuit 34, and Position detecting circuit 35. The correlation 得到 obtained by the correlation calculation circuit 34 of the receiving unit 300 is equivalent to the detection state of the pointer, and the detection state of the pointer is calculated by the position calculation circuit 3 5 -20- 201122922. The position of the indicator. Next, the received conductor selection circuit 31 will be described with reference to FIG. Each of the received conductors 14' constituting the received conductor group 13 is divided into eight receiving conductors 14 as one group of sixteen detecting blocks 3 6 ° and the received conductor selecting circuit 31 It is made up of the same number (16) of switches 3 1 a as this ~ detection block 36. Further, the switch 3 1 a ' is provided in each of the detection blocks 36 and is provided one by one, and the selected signal conductor 14 is selected according to the control signal of the control circuit 40 to be described later. Switch. The eight terminals 3 1 b on the input side of each switch 3 1 a are respectively connected to the corresponding signal conductors 14 . Further, one terminal 31c on the output side of each switch 31a is connected to an input terminal of a corresponding 1/V conversion circuit 32a (to be described later). Further, each of the switches 31a is a signal conductor I4 connected to the 1/V conversion circuit 32a at a specific time interval (a period of four times the switching timing of the switch 22a of the transmission conductor selection circuit 22). Switch. Then, the output signal 'from the 1/V conversion circuit 32a is amplified to a specific signal level at an amplifier (not shown), and then is output to the A/D conversion circuit 33 via the changeover switch 32d. Next, the switching operation of the received conductor selection circuit 31 will be described with reference to FIG. 7'. Here, each detection block 36' assumes that the signal conductors 14 (that is, the signal conductors 乂1, χ9 .....) of the smallest index number are connected to the amplifying circuit 32 via the switch 3 ia ( State of Figure 6). First, in the state shown in FIG. 6, between the specific time, the received conductor selection circuit 31 simultaneously selects 21 - 201122922 for the plurality of received conductors 4 and obtains the slave as a current signal. Output signals S 1 , S 2 , ..., s I 6 from each detection block 36. Then, if a specific time has elapsed, the switches 31a of the received conductor selection circuit 3 1 switch the received conductor 14 to the adjacent one of the positions at the position where the index mark m increases. The conductor 14, that is, is switched to the signal conductors X2, X1Q, ..., and X122. However, after this switching, the received conductors X2, X connected to the switch 31a are obtained. ..... X11 and X16 output new output signals Si, S2, ..., S16. Thereafter, the switch 31a of the received conductor selection circuit 31 repeatedly performs such switching operation. Then, the switch 3 1 a is received by the signal conductor 14 (i.e., the signal conductor X8, X16.....X12Q) of the largest index mark in each detection block 36.
Xl28)作連接，並得到從此被選擇了的受訊導體X8、X16、 …、Xl2Q以及Xl28處所輸出之新的輸出訊號。之後，開關 3 1 a係再度得到從各檢測區塊3 6內的最小索引標號之受訊 導體1 4所輸出之新的輸出訊號》此動作，係在各檢測區塊 36內而被反覆進行。另外，較理想，係將並未被開關3 1 a 所選擇的受訊導體14與任意之基準電位或者是接地作連接 。如此這般，藉由將並未被開關31a所選擇之受訊導體14 與任意之基準電位或者是接地相連接，由於係能夠避免並 未被作選擇之受訊導體14的雜訊，因此，係能夠將雜訊耐 性提升。又，亦能夠將送訊訊號之繞入降低。進而，受訊 導體1 4之切換動作的處理程序，係並不被限定於圖7之例 。針對其之變形例，係於後詳述。 -22- 201122922 如上述一般，受訊導體選擇電路，係將複數之受訊導 體，區分成各群組爲由特定數量之導體所成的複數之群組 ，而對於構成各群組之至少1根的導體分別作選擇，並且 ，對於構成各群組之各導體依序作切換。藉由如此這般地 來構成，能夠將用以進行位置檢測之輸出訊號同時性地從 受訊導體群處而檢測出來。於此第1實施形態中，由於係 將受訊導體群分割爲1 6個群組，因此，在用以進行位置檢 測之訊號的受訊中所耗費的時間，係能夠縮短至先前技術 之 1 / 1 6。 接著，參考圖6，針對放大電路32作說明。放大電路 32，係爲將從受訊導體1 4所輸出之電流訊號變換爲電壓訊 號並且作放大之電路。此放大電路32，係由與受訊導體群 13之檢測群組數量（16個）相同數量之1/ V變換電路32a 和切換開關32d所構成，對於1個的檢測區塊36，係被連接 有1個的1/ V變換電路3 2 a。 I/V變換電路32a，係由1輸入1輸出之放大器32b (運 算放大器：Operational Amplifier)、和被與此放大器32b 作了並聯連接之電容器3 2c，而構成之。 而，各1/ V變換電路32a，係將構成受訊導體選擇電 路31之各檢測區塊36的輸出訊號Si、S2、…、Si6變換爲電 壓訊號作並作輸出。另外，實際上，係爲了直流偏壓調整 用而將電阻元件或是電晶體等與電容器32c並聯地作設置 ，但是，於此係省略其記載。Xl28) is connected and obtains a new output signal outputted from the selected conductors X8, X16, ..., Xl2Q and Xl28. Thereafter, the switch 3 1 a again obtains a new output signal outputted from the signal conductor 14 of the smallest index number in each detection block 36. This action is repeated in each detection block 36. . Further, it is preferable that the signal conductor 14 which is not selected by the switch 3 1 a is connected to any reference potential or ground. In this way, by connecting the signal conductor 14 not selected by the switch 31a to any reference potential or ground, since the noise of the signal conductor 14 that is not selected is avoided, It is able to improve the tolerance of noise. Moreover, it is also possible to reduce the rounding of the transmission signal. Further, the processing procedure of the switching operation of the received conductor 14 is not limited to the example of Fig. 7. Modifications thereof will be described in detail later. -22- 201122922 As described above, the signal conductor selection circuit divides the plurality of signal conductors into groups of a plurality of conductors formed by a specific number of conductors, and at least 1 for each group. The conductors of the root are individually selected, and the conductors constituting each group are sequentially switched. With such a configuration, the output signal for position detection can be detected simultaneously from the received conductor group. In the first embodiment, since the group of the received conductors is divided into 16 groups, the time taken for the signal for detecting the position can be shortened to 1 in the prior art. / 1 6. Next, the amplification circuit 32 will be described with reference to FIG. The amplifying circuit 32 is a circuit that converts a current signal output from the signal receiving conductor 14 into a voltage signal and amplifies it. The amplifying circuit 32 is composed of the same number of 1/V converting circuits 32a and switching switches 32d as the number of detecting groups (16) of the received conductor group 13, and is connected to one detecting block 36. There is one 1/V conversion circuit 3 2 a. The I/V conversion circuit 32a is constituted by an input/output amplifier 32b (Operational Amplifier) and a capacitor 32c connected in parallel with the amplifier 32b. Further, each of the 1/V conversion circuits 32a converts the output signals Si, S2, ..., Si6 constituting the detection blocks 36 of the signal receiving conductor selection circuit 31 into voltage signals for output. Further, actually, a resistor element, a transistor, or the like is provided in parallel with the capacitor 32c for DC bias adjustment, but the description thereof is omitted here.
切換開關3 2d，係爲在每一特定時間中，而將與A/ D -23- 201122922 變換電路33相連接之1/ V變換電路32a依序作切換，並將 從此1/ V變換電路32a所輸出之電壓訊號以時間分割而輸 出至A/ D變換電路33處的電路。當設爲了此種構成的情 況時，在受訊部3 00內，由於係只要設置1系統之A/ D變 換電路33以及相關値算出電路34即可，因此，係能夠將受 訊部3 00之電路構成簡略化。另外，於此圖6中，雖係針對 將切換開關32d設置在放大電路32內的情況作了例示，但 是，此切換開關32d，係亦可設置在受訊導體選擇電路3 1 與放大電路32之間。如此這般，當將切換開關32d設置在 受訊導體選擇電路3 1與放大電路3 2之間的情況時，由於係 成爲並不需要設置與構成受訊導體選擇電路31之開關31a 的個數相同數量之1/ V變換電路32a，因此，係能夠將受 訊部3 00之電路構成更加簡略化。另外，在此第1實施形態 中，雖係對於藉由設置切換開關32d來將後段之A/ D變換 電路33以及相關値算出電路34分別設爲了 1系統的情況而 作了例示，但是，本發明係並不被限定於此，亦可將A/ D變換電路33以及相關値算出電路34之個數設置爲與I/V 變換電路32a之數量（16個）相同。若是設爲此種構成， 則由於係並不需要進行由切換開關32d所致之切換控制， 因此，在構成被要求有更加高速之訊號處理之指示體檢測 裝置的情況時，係爲合適。 A/ D變換電路33，係如圖1中所示一般，爲被連接於 放大電路32之輸出端子處，並將從放大電路32所輸出之類 比訊號變換爲數位訊號而作輸出之電路。。在I/V變換電 -24- 201122922 路32a處而被變換爲電壓訊號的輸出訊號Si、S2.....S16 ，係在此A/D變換電路33中而被變換爲數位訊號並被輸 出。另外，在此A/D變換電路33處，係可使用週知之A/ D變換器。 接下來，參考圖8，對相關値算出電路34之構成作詳 細說明。相關値算出電路34，係爲用以根據後述之控制電 路40的控制來從由A/ D變換電路33所輸出之輸出訊號S!、 S2.....S16而算出相關値之電路，並如圖1中所示一般， 被與A/ D變換電路33和控制電路40以及後述之位置檢測 電路3 5作連接。 此相關値算出電路34，係具備有：訊號延遲電路34a 、和與展頻碼Ck&數量相同數量（16個）的相關器34b、 34b2、34b3.....34b16、和將相關値演算用碼供給至此些 之各相關器341m〜34b 16處的相關値演算用碼產生電路34C| 、34c2、34c3、…、34c"' 34ci6、以及相關値記憶電路 34d ° 訊號延遲電路34a，係爲用以將從A/ D變換電路33所 輸出之數位訊號暫時性地作保持，並將此被作了保持的資 料同時地供給至各相關器34b,〜34b, 6處之電路。此訊號延 遲電路34a，係由與展頻碼Ck之碼長度相同數量（16個） 的D -正反器電路34a!、34a〗、34a3.....34a!5、34a!6所構 成。此 D -正反器電路 34a16、34a15、34a 丨 4.....34a3、 34a2、34a!，係依此順序而被從A/ D變換電路33側作串聯 連接所構成者。而，此D-正反器電路34a,〜34a16之各個的 -25- 201122922 輸出端子，係被與相鄰接之其他的D-正反器電路（例如， 若是D-正反器電路3 4a16，則係爲D-正反器電路34a15)、 以及各相關器341^-341^6作連接，從各D-正反器電路34a! 〜34a16而來之輸出訊號，係被輸入至所有的相關器34bl〜 34b16處。以下，將由此16個的D-正反器電路34ai〜34a16 而來之16碼片的輸出訊號，分別稱爲？31、？32、？33—·· 、P S 1 5、P S 1 6。 相關器341),- 34b16，係爲將從各D-正反器電路34ai〜 34a16所輸出之各輸出訊號PS,' PS2.....PS16，和從後述 之相關値演算用碼產生電路34c ,〜34c16所輸入之各相關値 演算用碼Ci’〜C16’作乘算，而計算出各展頻碼匕之相關値 的電路。相關器34M〜34b16，由於係分別對於展頻碼Ci〜 C16而進行相關演算，因此，係被設置有16個。亦即是， 相關器3 41m，係將從各D-正反器34ai〜34a16而來之輸出訊 號PS,、PS2.....PS16與相關値演算用碼CV作乘算而演算 出相關値，相關器3 4b2，係將各受訊訊號與相關値演算用 碼C2 ’作相關演算而演算出相關値，以下，同樣的，而將 關於16個的全部之展頻碼（^〜（：16的相關値計算出來。而 ，各相關器341m〜34b16，係將算出了的相關値輸出至相關 値記憶電路34d處。 相關値演算用碼產生電路34Cl、34c2、34c3..... 34c15、34c16，係爲用以供給各相關器34lM〜34b16所用來 進行相關演算之相關値演算用碼Ck’的電路。各相關値演 算用碼產生電路34Cl〜 34c16 ’係分別被與相對應之各相關 -26- 201122922 器34b!〜34b16作連接。由此相關値演算用碼產生電路34C] 〜34c16而對於相對應之相關器34b,〜34b, 6所供給之相關 値演算用碼C 1 ’〜C 16 ’，係分別具備有2 η的碼長度，例如， 相關器3 4b ! ’由於係進行展頻碼c i之相關演算，因此，相 關値演算用碼C ! ’係成爲1 6碼片。以下，將從各相關値演 算用碼產生電路34c,〜34cI6而供給至各相關器3 4b,〜34b16 處之相關値演算用碼，稱爲Cx’（PN〆、PN2’、PN3’..... PN15’、PN16’）。 而後，若是各相關器34b, 〜34b16對於輸出訊號PS,、 PS2.....PS16與相關値演算用碼C|’〜Cl6 ’進行相關演算 ，則當在感測部1 〇 〇上並不存在有指示體1 9的情況時，係 得到一定之値的相關値，而當在感測部1 0 0上存在有指示 體的情況時，則係成爲得到與此一定之値的相關値相異之 値的相關値。 相關値記憶電路34d，係爲用以將藉由在相關器34b , 〜3 4b ! 6中之相關演算所得到的相關値作暫時性記憶之記憶 部。此相關値記憶電路34d，係由與相關器34b,〜34bl6相 同數量之複數的暫存器（未圖示）所構成。如同在圖4以 及圖5中所作了說明一般，由於送訊導體選擇電路22之各 送訊區塊25，係藉由4根之送訊導體12所構成，並藉由開 關22a來對此作切換，因此，若是在1個的受訊導體14處而 進行指示體1 9之檢測，則係能夠得到4個的相關値。故而 ，構成相關値記憶電路3 4 d之各暫存器，係具備有4個的區 域。而，在此4個的區域中，係分別被記憶有進行相關演 -27- 201122922 算所得到了的相關値。故而，在構成此暫存器之各區域中 ’係被儲存有與由任意一根之送訊導體12與構成受訊導體 群1 3之全部的受訊導體1 4間所成的交叉點相同數量之資料 (128個）。而，在相關値記憶電路34d處，被作了輸入的 於各交叉點處之相關値，係與感測部1 〇〇全面性對應地而 被作映射，並產生相關値之空間分布（映射資料）。The switch 3 2d switches the 1/V conversion circuit 32a connected to the A/D -23-201122922 conversion circuit 33 in sequence at each specific time, and will switch from the 1/V conversion circuit 32a. The output voltage signal is outputted to the circuit at the A/D conversion circuit 33 in time division. In the case where such a configuration is adopted, it is only necessary to provide the A/D conversion circuit 33 of the one system and the correlation calculation circuit 34 in the reception unit 300, so that the reception unit 3 can be provided. The circuit structure is simplified. Further, in FIG. 6, although the case where the changeover switch 32d is provided in the amplifier circuit 32 is exemplified, the changeover switch 32d may be provided in the received conductor selection circuit 3 1 and the amplifier circuit 32. between. In this manner, when the changeover switch 32d is disposed between the received conductor selection circuit 31 and the amplifying circuit 32, the number of switches 31a constituting the received conductor selection circuit 31 does not need to be provided. Since the same number of 1/V conversion circuits 32a are used, the circuit configuration of the receiving unit 300 can be simplified. In the first embodiment, the A/D conversion circuit 33 and the related 値 calculation circuit 34 in the subsequent stage are respectively provided as one system by providing the changeover switch 32d. However, this example is exemplified. The invention is not limited thereto, and the number of A/D conversion circuits 33 and associated 値 calculation circuits 34 may be set to be the same as the number (16) of I/V conversion circuits 32a. According to this configuration, since the switching control by the changeover switch 32d does not need to be performed, it is suitable when the pointer detecting device that requires higher speed signal processing is configured. The A/D conversion circuit 33, as shown in Fig. 1, is a circuit which is connected to the output terminal of the amplifying circuit 32 and converts the analog signal output from the amplifying circuit 32 into a digital signal for output. . The output signals Si, S2, ..., S16 which are converted into voltage signals at the path 32a of the I/V conversion electric-24-201122922 are converted into digital signals by the A/D conversion circuit 33 and are converted into digital signals. Output. Further, at this A/D conversion circuit 33, a well-known A/D converter can be used. Next, the configuration of the correlation 値 calculation circuit 34 will be described in detail with reference to Fig. 8 . The correlation calculation circuit 34 is a circuit for calculating the correlation 从 from the output signals S!, S2.....S16 outputted by the A/D conversion circuit 33 according to the control of the control circuit 40 to be described later, and As shown in Fig. 1, generally, it is connected to the A/D conversion circuit 33 and the control circuit 40 and a position detecting circuit 35 which will be described later. The correlation calculation circuit 34 is provided with: a signal delay circuit 34a, and a correlator 34b, 34b2, 34b3, ..., 34b16 having the same number (16) as the spread code Ck& and calculating the correlation The correlation 値 calculation code generating circuits 34C|, 34c2, 34c3, ..., 34c" '34ci6, and the associated 値 memory circuit 34d ° signal delay circuit 34a supplied to the respective correlators 341m to 34b 16 of the codes are The digital signal output from the A/D conversion circuit 33 is temporarily held, and the held data is simultaneously supplied to the circuits of the correlators 34b, 〜34b, and 6. The signal delay circuit 34a is composed of the same number (16) of D-reactor circuits 34a!, 34a, 34a3, ..., 34a! 5, 34a! 6 as the code length of the spread code Ck. . The D-reciprocator circuits 34a16, 34a15, 34a 丨 4.....34a3, 34a2, 34a! are formed in series by the A/D conversion circuit 33 side in this order. However, the -25-201122922 output terminals of the D-reciprocator circuits 34a, 3434a16 are connected to other adjacent D-reactor circuits (for example, if the D-reciprocator circuit 3 4a16 The D-reciprocator circuit 34a15) and the correlators 341^-341^6 are connected, and the output signals from the D-reactor circuits 34a! to 34a16 are input to all of them. Correlators 34b1 to 34b16. Hereinafter, the 16-chip output signals of the 16 D-reactor circuits 34ai to 34a16 are respectively referred to as ? 31,? 32,? 33—··, P S 1 5, P S 1 6 . The correlators 341), - 34b16 are output signals PS, 'PS2.....PS16, which are output from the respective D-reciprocator circuits 34ai to 34a16, and the associated 値 calculation code generating circuit, which will be described later. The circuits related to the respective spread spectrum codes are calculated by multiplying the correlation calculus codes Ci' to C16' input by 34c and ~34c16. The correlators 34M to 34b16 are associated with the spreading codes Ci to C16, respectively, and therefore 16 are provided. That is, the correlator 3 41m is calculated by multiplying the output signals PS, PS2, . . . , PS16 from the respective D-reciprocators 34ai to 34a16 and the related 値 calculation code CV.値, the correlator 3 4b2 calculates the correlation between each received signal and the related calculus code C2 ', and the following, the same, will be about 16 of the entire spread code (^~( The correlation : of 16 is calculated, and each correlator 341m to 34b16 outputs the calculated correlation 至 to the relevant 値 memory circuit 34d. The correlation 値 calculation code generation circuit 34Cl, 34c2, 34c3..... 34c15 and 34c16 are circuits for supplying the correlation calculus code Ck' for performing correlation calculations by the correlators 34lM to 34b16. The correlation calculus generating circuits 34c1 to 34c16' are respectively associated with each other. Each of the related -26-201122922 devices 34b! to 34b16 is connected. Thus, the correlation 値 calculation code generating circuits 34C] to 34c16 and the corresponding 値 calculation code C 1 supplied to the corresponding correlators 34b, 〜34b, 6 '~C 16 ', which has a code length of 2 η, for example, a correlator 3 4b ! ' Since the correlation calculation of the spread spectrum code ci is performed, the correlation 値 calculation code C ! ' is set to 16 chips. Hereinafter, the correlation 値 calculation code generation circuits 34c, 34cI6 are supplied. The correlation calculus code to each correlator 34b, 〜34b16 is called Cx' (PN〆, PN2', PN3'.....PN15', PN16'). Then, if it is each correlator 34b, ～34b16 performs correlation calculation on the output signals PS, PS2, ..., PS16 and the related 値 calculation code C|'~Cl6', when there is no indicator body 19 on the sensing unit 1 In the case of a situation, a certain correlation is obtained, and when there is a pointer in the sensing unit 100, the correlation is obtained after the correlation is determined. The correlation memory circuit 34d is a memory unit for temporarily storing the correlation obtained by the correlation calculations in the correlators 34b, 34b, 6. 6. The correlation memory circuit 34d is composed of The correlators 34b, 34bbl6 are composed of the same number of registers (not shown), as in Figures 4 and 5. In general, since each of the transmission blocks 25 of the transmission conductor selection circuit 22 is constituted by four transmission conductors 12, and is switched by the switch 22a, if it is one When the signal conductor 14 is detected and the pointer 19 is detected, four correlations can be obtained. Therefore, each of the registers constituting the memory circuit 34d has four regions. However, in the four regions, the correlations obtained by the relevant performances are calculated. Therefore, in each of the areas constituting the register, the intersection between the signal conductor 12 and the signal conductor 14 constituting all of the signal conductor groups 13 is stored. Quantity information (128). However, at the associated memory circuit 34d, the correlations at the intersections that are input are mapped to the sensing unit 1 in a comprehensive manner, and the spatial distribution of the correlation is generated (map data).
接下來，針對相關値算出電路34之動作作說明。1/V 變換電路32a之輸出訊號S,、S2.....S16，係在A/D變換 電路33中而被變換爲數位訊號，並被輸入至相關値算出電 路34處。由此A/ D變換電路33所輸入至相關値算出電路 34處之數位訊號，首先係被記憶在訊號延遲電路34a之D-正反器電路3416中。而後，此D-正反器電路34a16，係將 此記憶了的資料供給至各相關器34b,〜34b, 6處。接著，若 是從A/D變換電路33所輸出之下一個的數位訊號被供給 至D-正反器電路34al6處，則D-正反器電路34a16，係將至 此爲止所記憶了的資料輸出至相鄰接之D_正反器電路34ai 5 處，而將新供給而來之數位訊號作記憶，並且，將此新記 憶了的資料輸出至各相關器34b,〜341^ 6處。之後，當每次 被輸入有新的資料時，各D-正反器電路34&1〜34a16，係反 覆進行將至此爲止所記憶了的資料輸出至相鄰接之D-正反 器電路以及各相關器6處並且將新供給而來之數 位訊號作記憶的處理。 被記憶在各D-正反器電路34ai〜34a16中之16碼片的輸 出訊號PSi〜PSI6’係被供給至16個的相關器341η〜341)16 -28- 201122922 處。各相關器341^-3415,6 ’係將分別從各D-正反器電路 34ai~34a16所供給而來之輸出訊號PS,〜PS16，和從相關 値演算用碼產生電路34Cl〜34c16所供給而來之相關値演算 用碼C,’〜C16’作相關演算，而得到相關値。 而後，各相關器341m〜34b16 ’係根據後述之控制電路 40的控制，而僅將在第1 6n次之演算結果中所得到的相關 値輸出至相關値記憶電路34d處。藉由反覆進行此，係僅 有當對於與任意之一根的受訊導體Μ相交叉之全部的送訊 導體1 2而供給了展頻碼C ,〜C ! 6時所得到之輸出訊號而進 行了相關演算後之結果，會被輸出至相關値記憶電路34d 處。而，此身爲相關演算後之結果的相關値，係被記憶在 相關値記憶電路34d之各暫存器的特定之區域中。 同樣的，對於構成受訊導體選擇電路3 1之開關3 1 a以 及放大電路32之切換開關32d適宜作切換，並對於從構成 感測部100之全部的受訊導體14所得到之輸出訊號而進行 相關演算。 另外，在圖8中，雖係針對使用與展頻碼Ck相同數量 之相關器341^-341^6並藉由各個的相關器341)^341^6來 個別進行相關演算之相關値算出電路34作了例示，但是， 亦可設爲下述之構成：亦即是，對於1個的相關器而依序 供給複數之相關値演算用碼C , ’〜C , 6 ’，並藉由時間分割來 進行相關演算。 以下，參考圖9，針對對於1個的相關器而依序供給複 數之相關値演算用碼，並且藉由時間分割來進行相關演算 -29- 201122922 之相關値算出電路其中一例作說明。此圖9，係爲對於以 時間分割來進行各展頻碼之相關演算的相關値算出電路之 其中一構成例作展示者。 以下，針對圖9中所示之相關値算出電路134的構成來 作說明。此相關値算出電路1 3 4，係由訊號延遲電路3 4a、 和相關器34bx、和相關値演算用碼產生電路134cx、和相關 値記憶電路34d、以及暫存器134e所構成。暫存器134e， 係被設置在構成訊號延遲電路3 4a之各D-正反器電路34&1 〜34a16的輸出端子與相關器34bx之間，並將從各D-正反器 電路34ai〜34a16所輸出之16碼片的輸出訊號PS,’〜PS16’暫 時性地作記憶。 相關器34bx，係爲對於被記憶在暫存器134e中之資料 和從相關値演算用碼產生電路1 34cx所供給而來之相關値 演算用碼Cx ’而進行相關演算並算出相關値之電路。此相 關値34bx之輸出端子，係被與相關値記憶電路34d相連接 〇 相關値演算用碼產生電路134cx，係爲對於相關器34bx 而供給相關値演算用碼Cx’（ ΡΝ〆、PN2’、PN3’..... PN15’、PN16’）之電路。此相關値演算用碼產生電路134cx ，係將供給至相關器34bx處之相關値演算用碼Cx’經時性地 作切換並作供給。 相關値記憶電路34d，係爲用以將從相關器34bx所輸 出之相關値暫時性地作記憶之記億部，並被與相關器34bx 和位置檢測電路3 5 (參考圖1 )作連接。其他之構成’由 -30- 201122922 於係爲與圖8中所示之相關値算出電路34相同之構成，因 此’關於相同之構成’係附加與圖8相同之號碼，並省略 詳細之說明。 以下’針對相關値算出電路134之動作作詳述。圖6中 所示之I/V變換電路32a之輸出訊號，係在A/D變 換電路33中而被變換爲數位訊號，之後，被輸入至訊號延 遲電路34a處。被輸入至此訊號延遲電路34a中之數位訊號 ’係被依序供給至被作了 1 6段的串聯連接之D -正反器電路 34a!〜34a16處。而後’各D -正反器電路34a,〜34a16，係將 被供給之資料暫時性地作記憶，並且，將此記憶了的資料 輸出至暫存器134e處。之後，各D-正反器電路34ai〜34a16 ’係在每次被供給有新的數位訊號時，將正作保持的資料 供給至相鄰接之D-正反器電路34^處，並將此新供給而來 之資料作記憶，並且，將此新供給而來之資料作爲輸出訊 號而輸出至暫存器134e處。 另一方面，相關器3 4b x，若是在暫存器134e中而資料 已齊備，則係根據後述之控制電路40的控制，來對於被記 憶在暫存器1 3 4e中之資料和從相關値演算用碼產生電路 1 3 4 cx所供給而來之相關値演算用碼C i ’而進行相關演算， 並算出相關値。而後，相關器34bx，係將此身爲演算結果 之相關値輸出至相關値記憶電路34d處。之後’相關器 34\ ’係對於相關値演算用碼C2’、C3’.....C16’而亦進 行相同之相關演算，並將身爲演算結果之相關値隨時地輸 出至相關値記憶電路34d處。之後’相關器34bx ’若是對 -31 - 201122922 於全部的相關値演算用碼而進行了相關演算’則係將被記 憶在暫存器134e中之資料廢棄’並進行待機’直到下一個 的資料被作記錄爲止。之後’藉由反覆進行上述處理’而 對於從構成感測部1〇〇之全部的受訊導體14所得到之受訊 訊號來進行相關演算。 如同上述一般，藉由將相關値算出電路設爲如同此圖 9中所示一般之構成，能夠藉由較圖8中所示之相關値算出 電路而更少的相關器以及相關値演算用碼產生電路，來與 準備有和展頻碼之數量相同數量之相關器的情況時相同地 而得到各個的展頻碼之相關値。 接下來，參考圖1 〇，針對相關器之構成作詳細說明。 圖10，係爲對於在圖8以及圖9中所展示了的各相關器34b, 〜34b16以及34bx之構成例作展示者。相關器34b，係由16 個的乘算器34f,、34f2.....34f16，和加算器34g所構成。 在此第1實施形態中，將乘算器34f,〜34f16設爲了 16個的 原因，係爲了求取出16碼片之展頻碼Ck的相關之故。故而 ’乘算器之數量，係因應於展頻碼Ck之碼片數而成爲相異 之設置數。 在各個的乘算器34f,〜34f16處，係被供給有輸出訊號 之各碼片PS,〜PS16、和相關値演算用碼之各碼片PNl，〜 pNle’’並將同一碼片位置之彼此的訊號作乘算，而得到 乘算訊號。在各乘算器34〇〜34Γ16處所算出之乘算訊號， 係被供給至加算器34g處。加算器34g，係將從各乘算器 34h〜34fie所供給而來之全部的碼片位置之訊號作加算， -32- 201122922 並得到相關値。此相關値’係被記憶在相關値記憶電路 34d中。另外，依存於所使用之碼，亦可在乘算器34fi〜 3 4fl6處，使用加算器或者是減算器。 位置檢測電路3 5 ’係爲從被記憶在相關値記憶電路 3 4d中之映射資料’來求取出超過特定之臨限値的相關値 之區域’並將該區域作爲指示體之位置而計算出來之電路 。此位置檢測電路3 5，係如圖1中所示一般，被與相關値 算出電路34和控制電路40相連接。另外，亦可設爲：在此 位置檢測電路35處’係被設置有：當指示體存在於交叉點 之間的情況時，而從被記億在相關値記憶電路34d中之相 關値來將該指示體所位置之座標計算出來之內插處理電路 ，以計算出更加高解析度之內插値的映射資料。 控制電路40，係爲用以對於本發明之指示體檢測裝置 1的各部進行控制之電路。此控制電路4 0，係如圖1中所示 一般，被與時脈產生電路23、和展頻碼供給電路2 1、和送 訊導體選擇電路22、和相關値算出電路34、以及位置檢測 電路3 5相連接。而，控制電路40，係根據從時脈產生電路 23所輸出之時脈訊號，來適當地產生以及輸出送訊載 入訊號Stlc)ad以及受訊載入訊號Sr1()ad，並對於上述各部之 動作時序作控制。 以下，參考圖1、圖9以及圖1 1 ’針對在第1實施形態 中之控制電路4 0以及指示體檢測裝置1的動作作說明。另 外，在以下之說明中，爲了能夠易於對原理作理解，係對 於將相關値算出電路藉由圖9中所示之相關値算出電路134 -33- 201122922 來構成的情況而作例示並說明之。 於此，圖1 1 ( a )，係爲從時脈產生電路2 3而供給至 控制電路40以及展頻碼供給電路21處之時脈訊號S(：lk的訊 號波形。此時脈訊號SUk之週期，例如係被設定爲展頻碼 匕之1碼片長度。圖1 1 ( b )，係爲從控制電路40而供給至 送訊導體選擇電路22以及受訊導體選擇電路31處之送訊載 入訊號StUad的訊號波形。此送訊載入訊號StUad，係爲將 週期設定爲展頻碼匕之碼長度（時脈訊號之16週期）的脈 衝訊號。圖11 (c)，係爲從控制電路40而供給至相關値 算出電路34處之受訊載入訊號Srl£)ad的訊號波形。此受訊 載入訊號Sr1(3ad，係爲將週期設定爲例如展頻碼Ck之碼長 度（時脈訊號之1 6週期）的脈衝訊號。而，此受訊載入訊 號Srl()ad，係成爲相較於送訊載入訊號StUad而更延遲了時 脈訊號5。11{的1週期之時間地被作輸出。圖1 1 ( d )，係爲 從展頻碼供給電路2 1所對於送訊導體群1 1 (參考圖1 )而 將碼作送訊之輸出時序圖。圖1 1 ( e )，係爲經由D-正反 器電路34ai〜34a16而被設定於暫存器134e中之16碼片的輸 出訊號之時序圖，圖11(f)，係爲被與該設定了的受訊 訊號作乘算之相關値演算用碼的產生碼（Ct’、C2’、C3,、 …、C 1 6 ’）。 從時脈產生電路23所輸出之時脈訊號Selk (圖1 l(a)) ，若是被輸入至控制電路4〇以及展頻碼供給電路2 1中，則 控制電路40係與此時脈訊號Selk同步地而將送訊載入訊號 StUad (圖11(b))輸入至送訊導體選擇電路22以及受訊導 -34- 201122922 體選擇電路3 1處。而，在經過1時脈週期後，控制電路4 0 ，係將受訊載入訊號Srl()ad輸入至A/D變換電路33中。 送訊導體選擇電路22，係當送訊載入訊號311。!1(1爲 HIGH準位，並且在時脈訊號Selk之上揚時序（圖11中之t〇 )處，而開始對於送訊導體12之展頻碼Ck的供給。之後， 此送訊導體選擇電路22，係當每一次之送訊載入訊號 StlQad爲HIGH準位的時脈訊號Selk之上揚時序（例如，圖1 1 中之t2以及t4 )處，而將供給展頻碼Ck的送訊導體12作切 換。 同樣的，受訊導體選擇電路31的開關31a，係當送訊 載入訊號St1。ad爲HIGH準位，並且在時脈訊號Selk2上揚時 序處，而對於最初所進行受訊之受訊導體1 4作選擇（圖6 之狀態）。之後，此受訊導體選擇電路31，係在每被輸入 有4次之送訊載入訊號311。^的脈衝時，而對於開關31a作控 制，並對於所選擇之受訊導體1 4作切換。於此，設定爲使 受訊導體選擇電路31在每被輸入有4次之送訊載入訊號 StUad的脈衝時而進行切換的原因，係在於：由於送訊區 塊25 (參考圖4 )係由4根的送訊導體12所構成，因此，若 是在此時序處而將供給展頻碼Ck之送訊導體12作切換，則 能夠對於構成各送訊區塊25之全部的送訊導體12來供給展 頻碼Ck之故。其結果，係成爲對於構成感測部1 〇〇之全部 的送訊導體12而供給展頻碼Ck。 如同上述一般，在藉由送訊導體選擇電路22而被選擇 了的各送訊導體12處，係於時脈訊號Selk2上揚時序處， -35- 201122922 而被供給有各展頻碼Ck之第η碼片的碼。亦即是，在時間 點tQ處，係被供給有各展頻碼c 1〜C , 6之第1碼片的碼，並 在每一時脈處，而因應於時脈之上揚時序，來將供給至各 送訊導體12處之碼切換爲第2碼片、第3碼片、…（圖11(d) )。而後’在下一個的送訊載入訊號St1()ad之上揚時序、 亦即是在時脈訊號Selk之第17次的上揚時序處，由於對於 被送訊導體選擇電路22所選擇了的各送訊導體12之各展頻 碼Ck的供給係結束，因此，送訊導體選擇電路22，係於此 時序處，而將所選擇之送訊導體12切換爲下一個的切換導 體12。之後，同樣的，係成爲在各送訊載入訊號Stl(jad2 上揚時序處，而對於送訊導體12作切換。另外，如同此圖 Π中所示一般，在下一個的展頻碼Ck之供給開始時序前而 存在有1個時脈的並未被供給有構成展頻碼Ck之各碼片的 期間之原因，係在於爲了防止由於受訊導體選擇電路22進 行切換所產生的過渡現象而導致之雜訊的發生之故。 而後，送訊導體選擇電路22，若是被輸入有送訊載入 訊號之第4次的脈衝，則係回到最初階段，並反覆進行上 述之切換動作》 另外，在上述時脈訊號Selk之上揚時序處，係從被受 訊導體選擇電路31所選擇了的各受訊導體14處而被輸出有 輸出訊號》受訊導體選擇電路31，係當送訊載入訊號 Stl()ad之第4次的脈衝爲HIGH準位，並且在時脈訊號Selk2 上揚的時序處，而對於所選擇之受訊導體14依序作切換。 而，受訊導體選擇電路31，係當送訊載入訊號Stl()ad之第 -36- 201122922 33次的脈衝爲HIGH準位，並且在時脈訊號Selk之上揚的時 序處，而回到最初階段，並反覆進行上述切換動作。 另一方面，在時脈訊號Seu之上揚時序處而經由受訊 導體選擇電路31所得到了的輸出訊號，係在放大電路32處 而使訊號準位被放大，並在A/D變換電路33處而被變換 爲數位訊號並被輸入至相關値算出電路134(參考圖9)處 。此數位訊號，係如同上述一般，從被連接於A/D變換 電路33之輸出端子處的訊號延遲電路34a之D -正反器電路 34a16起而依序被輸入（參考圖9)。此D -正反器電路34a16 ，係將從A/ D變換電路33所輸入之數位訊號作記憶，並 且供給至被設置在此D -正反器電路34a16之後段處的各相關 器 34b,〜34b16 處。 從訊號延遲電路34a所輸出之各送訊訊號PS〆〜PS16’ ，係當送訊載入訊號St,。^爲HIGH準位，並且在時脈訊號Next, the operation of the correlation calculation circuit 34 will be described. The output signals S, S2, ..., S16 of the 1/V conversion circuit 32a are converted into digital signals by the A/D conversion circuit 33, and are input to the correlation circuit 34. Thus, the digital signal input to the associated 値 calculation circuit 34 by the A/D conversion circuit 33 is first stored in the D-reverse circuit 3416 of the signal delay circuit 34a. Then, the D-reciprocator circuit 34a16 supplies the stored data to each of the correlators 34b, 34b, and 6. Next, if the next digital signal outputted from the A/D conversion circuit 33 is supplied to the D-reciprocator circuit 34al6, the D-reciprocator circuit 34a16 outputs the data thus memorized to The adjacent D_ flip-flop circuit 34ai 5 is used to memorize the newly supplied digital signal, and the newly memorized data is output to the correlators 34b, 341^6. Thereafter, each time a new data is input, each of the D-reciprocal circuits 34 & 1 to 34a16 repeatedly outputs the data thus memorized to the adjacent D-reactor circuit and Each correlator 6 processes the newly supplied digital signal. The 16-chip output signals PSi to PSI6' memorized in each of the D-reciprocator circuits 34ai to 34a16 are supplied to 16 correlators 341n to 341) 16 -28 to 201122922. Each of the correlators 341^-3415, 6' supplies the output signals PS, PS16, and the slave 値 calculation code generating circuits 34c1 to 34c16 supplied from the respective D-reciprocator circuits 34ai to 34a16, respectively. The related calculus is calculated by the code C, '~C16', and the relevant 値 is obtained. Then, the correlators 341m to 34b16' are output only to the correlation memory circuit 34d by the correlation 得到 obtained in the first 6nth calculation result in accordance with the control of the control circuit 40 to be described later. By repeating this, it is only the output signal obtained when the spreading code C, ~C! 6 is supplied to all of the transmission conductors 12 that intersect with any one of the received conductors. The result of the relevant calculation is output to the relevant memory circuit 34d. However, the correlation between the results of the related calculations is stored in a specific area of each of the registers of the associated memory circuit 34d. Similarly, the switch 3d that constitutes the signal conductor selection circuit 3 1 and the switch 32d of the amplifier circuit 32 are appropriately switched, and the output signals are obtained from the received conductors 14 constituting all of the sensing unit 100. Perform related calculations. In addition, in FIG. 8, the correlation calculation circuit for the correlation calculation is performed for each of the correlators 341^-341^6 using the same number of the spreading code Ck and by the respective correlators 341)^341^6. 34 is exemplified, but it may be configured as follows: that is, a plurality of correlation 値 calculation codes C, '~C , 6 ' are sequentially supplied to one correlator, and time is used. Split to perform related calculations. Hereinafter, an example of the correlation 値 calculation circuit for sequentially supplying the correlation 値 calculation code for one correlator and performing the correlation calculation by time division -29-201122922 will be described with reference to Fig. 9 . Fig. 9 is a display example of one of the configuration examples of the correlation calculation circuit for performing the correlation calculation of the respective spreading codes by time division. Hereinafter, the configuration of the correlation 値 calculation circuit 134 shown in Fig. 9 will be described. The correlation 値 calculation circuit 134 is composed of a signal delay circuit 34a, a correlator 34bx, and an associated 値 calculation code generation circuit 134cx, an associated 値 memory circuit 34d, and a register 134e. The register 134e is disposed between the output terminals of the D-reciprocal circuits 34 & 1 to 34a16 constituting the signal delay circuit 34a and the correlator 34bx, and is supplied from each D-reactor circuit 34ai~ The 16-chip output signal PS, '~PS16' output by 34a16 is temporarily memorized. The correlator 34bx is a circuit that performs correlation calculation on the data stored in the register 134e and the correlation 値 calculation code Cx' supplied from the correlation 値 calculation code generation circuit 134cx and calculates the correlation 値. The output terminal of the correlation 値 34bx is connected to the associated 値 memory circuit 34d, and the 値 calculation code generation circuit 134cx is supplied with the correlation 値 calculation code Cx' (ΡΝ〆, PN2', for the correlator 34bx. Circuit of PN3'..... PN15', PN16'). The correlation 値 calculation code generation circuit 134cx supplies and supplies the correlation 値 calculation code Cx' supplied to the correlator 34bx over time. The correlation/memory circuit 34d is a unit for temporarily memorizing the correlation 输 output from the correlator 34bx, and is connected to the correlator 34bx and the position detecting circuit 35 (refer to Fig. 1). The other configurations are the same as those of the correlation calculation circuit 34 shown in Fig. 8. Therefore, the same reference numerals are given to the same components as in Fig. 8, and the detailed description thereof will be omitted. The following description of the operation of the correlation calculation circuit 134 will be described in detail. The output signal of the I/V conversion circuit 32a shown in Fig. 6 is converted into a digital signal by the A/D conversion circuit 33, and then input to the signal delay circuit 34a. The digital signals input to the signal delay circuit 34a are sequentially supplied to the D-reactor circuits 34a! to 34a16 which are connected in series of 16 segments. Then, each of the D-reciprocator circuits 34a, 34a16 temporarily stores the supplied data, and outputs the stored data to the register 134e. Thereafter, each of the D-reciprocator circuits 34ai to 34a16' supplies the data to be held to the adjacent D-reactor circuit 34^ each time a new digital signal is supplied, and The newly supplied data is memorized, and the newly supplied data is output as an output signal to the register 134e. On the other hand, if the correlator 3 4b x is in the register 134e and the data is ready, the data and the slave information stored in the register 1 3 4e are controlled according to the control of the control circuit 40 to be described later. The calculus calculation code 1 3 4 cx supplies the correlation calculus code C i ' to perform the correlation calculation, and calculates the correlation 値. Then, the correlator 34bx outputs the correlation 身 which is the result of the calculation to the relevant 値 memory circuit 34d. After that, the 'correlator 34\' also performs the same correlation calculation for the relevant calculus code C2', C3'.....C16', and outputs the relevant result of the calculation result to the relevant memory at any time. At circuit 34d. After that, the 'correlator 34bx' performs the relevant calculation for all the relevant calculus codes for -31 - 201122922, and then discards the data memorized in the register 134e and waits until the next data. It is recorded. Thereafter, the correlation processing is performed on the received signal obtained from all of the received conductors 14 constituting the sensing unit 1 by repeating the above-described processing. As described above, by setting the correlation 値 calculation circuit to a general configuration as shown in FIG. 9, it is possible to have fewer correlators and related 値 calculation codes by the correlation 値 calculation circuit shown in FIG. The circuit is generated to obtain the correlation of the respective spreading codes in the same manner as in the case of preparing the same number of correlators as the number of spreading codes. Next, referring to FIG. 1A, the configuration of the correlator will be described in detail. Fig. 10 shows an example of the configuration of each of the correlators 34b, 34b16, and 34bx shown in Figs. 8 and 9. The correlator 34b is composed of 16 multipliers 34f, 34f2, ..., 34f16, and an adder 34g. In the first embodiment, the reason why the multipliers 34f to 34f16 are set to 16 is to extract the spread code Ck of 16 chips. Therefore, the number of multipliers is a different number of settings depending on the number of chips of the spread spectrum code Ck. At each of the multipliers 34f, 34f16, each of the chips PS, PS16, and the chips PN1, pNle'' associated with the calculus code are supplied and the same chip position is provided. The signals of each other are multiplied to obtain a multiplication signal. The multiplication signals calculated at the respective multipliers 34A to 34Γ16 are supplied to the adder 34g. The adder 34g adds the signals of all the chip positions supplied from the respective multipliers 34h to 34fie, -32-201122922 and obtains correlation. This correlation 値 is stored in the associated memory circuit 34d. Further, depending on the code used, an adder or a subtractor may be used at the multipliers 34fi to 3 4fl6. The position detecting circuit 3 5 ' is calculated from the map data stored in the associated memory circuit 34 d to extract the region 値 that exceeds the specific threshold ' and uses the region as the position of the pointer. The circuit. This position detecting circuit 35, as shown in Fig. 1, is connected to the associated 电路 calculating circuit 34 and the control circuit 40. In addition, it may be set as follows: at the position detecting circuit 35, it is set to be: when the indicator exists between the intersections, and the correlation is from the related memory in the associated memory circuit 34d. The interpolation processing circuit calculated by the coordinates of the position of the pointer is used to calculate the mapping data of the interpolation with higher resolution. The control circuit 40 is a circuit for controlling each part of the pointer detecting apparatus 1 of the present invention. The control circuit 40, as shown in FIG. 1, is connected to the clock generation circuit 23, the spread spectrum code supply circuit 2, and the transmission conductor selection circuit 22, and the correlation calculation circuit 34, and the position detection. Circuits 35 are connected. The control circuit 40 appropriately generates and outputs the transmission load signal Stlc)ad and the received load signal Sr1()ad according to the clock signal output from the clock generation circuit 23, and for the above-mentioned parts. The timing of the action is controlled. Hereinafter, the operation of the control circuit 40 and the pointer detecting device 1 in the first embodiment will be described with reference to Figs. 1, 9, and 11. In the following description, in order to facilitate understanding of the principle, the related 値 calculation circuit is exemplified and explained by the correlation 电路 calculation circuit 134 - 33 - 201122922 shown in FIG. . Here, FIG. 11 ( a ) is a signal waveform of the clock signal S (: lk supplied from the clock generation circuit 23 to the control circuit 40 and the spread spectrum code supply circuit 21. At this time, the pulse signal SUk The period is, for example, set to a chip length of the spread spectrum code 。. Fig. 11 (b) is supplied from the control circuit 40 to the signal conductor selection circuit 22 and the signal conductor selection circuit 31. The signal waveform of the signal St9ad is loaded. The signal loading signal StUad is a pulse signal that sets the period to the code length of the spread spectrum code (16 cycles of the clock signal). Figure 11 (c) is The signal waveform of the received load signal Srl£)ad supplied to the correlation calculation circuit 34 from the control circuit 40. The received signal Sr1 (3ad) is a pulse signal whose period is set to, for example, the code length of the spread code Ck (16 cycles of the clock signal), and the received signal Srl()ad, It is delayed compared to the transmission load signal StUad, and the time of the pulse signal 5.11{1 cycle is output. Figure 1 1 (d) is from the spread spectrum code supply circuit 2 1 An output timing chart for transmitting a code to the transmission conductor group 1 1 (refer to FIG. 1). FIG. 11 (e) is set to the register 134e via the D-reactor circuits 34ai to 34a16. The timing chart of the output signal of the 16-chip chip, FIG. 11(f), is the generation code (Ct', C2', C3 of the calculus code associated with the set received signal. , ..., C 1 6 '). The clock signal Selk (Fig. 1 l (a)) output from the clock generating circuit 23, if input to the control circuit 4 〇 and the spread spectrum code supply circuit 2 1 The control circuit 40 inputs the transmission loading signal StUad (Fig. 11(b)) to the transmission conductor selection circuit 22 and the signal receiving guide-34-201122922 body selection circuit in synchronization with the pulse signal Selk at this time. 3, and after 1 clock cycle, the control circuit 40 inputs the received load signal Srl() ad to the A/D conversion circuit 33. The transmission conductor selection circuit 22 is sent The load signal 311.!1 (1 is the HIGH level, and at the timing of the clock signal Selk (t〇 in Fig. 11), the supply of the spread code Ck to the signal conductor 12 is started. The signal transmission conductor selection circuit 22 is provided at a timing of rising the Selk signal (eg, t2 and t4 in FIG. 11) for each time the transmission signal ST10Qad is at a HIGH level. Similarly, the transmission conductor 12 of the frequency code Ck is switched. Similarly, the switch 31a of the signal conductor selection circuit 31 is when the signal is loaded into the signal St1. The ad is at the HIGH level and is at the rising timing of the clock signal Selk2. The signal conductor 1 4 that is initially subjected to the reception is selected (the state of Fig. 6). Thereafter, the signal conductor selection circuit 31 is a pulse for loading the signal 311 every 4 times. At the same time, the switch 31a is controlled, and the selected signal conductor 14 is switched. Here, it is set to be received. The reason why the conductor selection circuit 31 switches every time the pulse of the transmission load signal StUad is input four times is that the transmission block 25 (refer to FIG. 4) is composed of four transmission conductors 12 According to this configuration, if the transmission conductor 12 supplied with the spread spectrum code Ck is switched at this timing, the spread spectrum code Ck can be supplied to all of the transmission conductors 12 constituting each of the transmission blocks 25. . As a result, the spread spectrum code Ck is supplied to the transmission conductors 12 constituting all of the sensing unit 1A. As described above, each of the transmission conductors 12 selected by the transmission conductor selection circuit 22 is supplied with the respective spreading code Ck at the timing of the rising timing of the clock signal Selk2, -35-201122922. The code of the n chip. That is, at the time point tQ, the code of the first chip of each of the spreading codes c 1 to C, 6 is supplied, and at each clock, and in response to the timing of the clock, The code supplied to each of the signal conductors 12 is switched to the second chip, the third chip, ... (Fig. 11(d)). Then, in the next transmission loading signal St1() ad rising timing, that is, at the 17th rising timing of the clock signal Selk, the respective transmissions selected by the signal transmission conductor selection circuit 22 are selected. The supply of the spread code Ck of the conductor 12 is completed. Therefore, the transmission conductor selection circuit 22 switches the selected transmission conductor 12 to the next switching conductor 12 at this timing. Thereafter, the same is done at each of the transmission load signals St1 (jad2 up-and-down timing, and for the transmission conductor 12 to switch. In addition, as shown in this figure, the supply of the next spread code Ck is provided. The reason why the period of each of the chips constituting the spread spectrum code Ck is not supplied before the start of the sequence is due to the transition phenomenon caused by the switching of the received conductor selection circuit 22 is caused. Then, the transmission conductor selection circuit 22 returns to the initial stage and repeats the above-described switching operation if the fourth pulse of the transmission load signal is input. At the timing of the above-mentioned clock signal Selk, the output signal "received conductor selection circuit 31" is output from each of the received conductors 14 selected by the signal receiving conductor selection circuit 31. The fourth pulse of the signal St1()ad is at the HIGH level, and is switched at the timing of the rising of the clock signal Selk2, and sequentially switches to the selected signal conductor 14. However, the received conductor selection circuit 31, When sending a message The signal number Stl()ad -36- 201122922 33 times of the pulse is HIGH level, and at the timing of the clock signal Selk rising, returning to the initial stage, and repeating the above switching action. The output signal obtained by the received conductor selection circuit 31 at the rising timing of the clock signal Seu is at the amplifying circuit 32 to amplify the signal level, and is converted to A at the A/D conversion circuit 33. The digital signal is input to the correlation 値 calculation circuit 134 (refer to Fig. 9). This digital signal is D-positive from the signal delay circuit 34a connected to the output terminal of the A/D conversion circuit 33 as described above. The inverter circuit 34a16 is sequentially input (refer to Fig. 9). The D-reactor circuit 34a16 memorizes the digital signal input from the A/D conversion circuit 33, and supplies it to be set at this D. - each of the correlators 34b, 34b16 at the subsequent stage of the flip-flop circuit 34a16. The respective signal signals PS〆~PS16' output from the signal delay circuit 34a are sent as the signal St, and are HIGH. Position and clock signal
Sclk之上揚時序處，而被設定在暫存器134e中。此動作， 係以當送訊載入訊號Sti。a<1爲HIGH準位，並且在時脈訊號The Sclk is raised at the timing and is set in the register 134e. This action is to send the signal Sti when the message is sent. a < 1 is HIGH level, and in the clock signal
Sclk之上揚時序U、t2、t4、…處作爲基準，而被反覆進行 〇 另一方面，相關値算出電路134，係當受訊載入訊號 Sruad之脈衝爲HIGH準位，並且在時脈訊號Selk之上揚時序 處（於圖1 1中，係爲時刻t3 )，而從相關値演算用碼產生 電路134 cx來依序產生16種類之相關値演算用碼匚,，〜C16, ’並供給至相關器34b ,處。相關器34bx，係當此受訊載入 訊號Sr|Qad爲HIGH準位，並且在時脈訊號Selk之上揚時序處 -37- 201122922 ，而開始此相關値演算用碼cr〜cie’與被設定在暫存器 1 34e中之訊號間的相關演算（圖1 1 (f))。而後’相關器 3 4bx，係將此演算結果依序輸出至相關値記憶電路34d處 (圖1 1(g))。之後’如同圖1 1 ( f)以及（g )中所示—般 ，對於展頻碼C2〜C16而亦進行相同之相關演算’並將其 演算結果輸出至相關値記憶電路34(1處。如同上述一般’ 而得到與各個的相關値演算用碼C Γ〜c 16 ’之間的相關値。 〔位置檢測之原理〕 接著，對於本發明之指示體檢測裝置1的位置檢測原 理，參考圖12〜16而作說明。如上述一般’本發明之指不 體檢測裝置1，係爲交叉點靜電耦合方式’並根據感測部 之送訊導體以及受訊導體間的靜電耦合狀態之變化而檢測 出指示體。 首先，參考圖1 2，對於指示體之檢測原理作說明。於 此，圖1 2 ( a )以及（b )，係爲對於手指等之指示體存在 於感測部1 〇〇上的情況以及並不存於感測部1 00上的情況下 之送訊導體12以及受訊導體Μ間的靜電耦合狀態作展示之 剖面圖。 當指示體1 9並不存在於感測部1 00上的情況時，如圖 12(a)中所示一般，被配置在第1基板15處的送訊導體12 以及被配置在第2基板1 7處之受訊導體1 4之間，係隔著間 隔物1 6而作靜電耦合，從送訊導體1 2所發出之電場，係在 受訊導體1 4處而作收斂。其結果，全部的電流係從送訊導 -38- 201122922 體I2而朝向受訊導體！4流動。另一方面，當指示體19存在 於感測部1 〇〇上的情況時，如圖1 2 ( b )中所示一般，受訊 導體1 4，係成爲並非僅與送訊導體1 2相耦合，而亦經由指 示體1 9來與接地作了靜電耦合的狀態。在此種狀態下，從 送訊導體1 2所發出之電場的一部份，係在指示體1 9處而收 斂，從送訊導體1 2而朝向受訊導體1 4所流動之電流的一部 份，係經由指示體1 9而分流至接地處。其結果，流入至受 訊導體1 4中之電流係減少。藉由檢測出此電流變化，而將 由指示體1 9所致之指示位置檢測出來。 接下來，依據圖1 3以及圖1 4，針對由指示體所致之指 示位置的座標之算出原理作說明。另外，在以下之說明中 ，爲了能夠容易地對於該原理作理解，係對於被供給有展 頻碼C2之送訊導體Y9與受訊導體Xl24之間的交叉點（圖13 (a )中以白色圓圈所示之位置。以下，單純稱作交叉點 )作注目，並將在此交叉點處而因應於指示體19之存在的 有無所得到之相關値作對比說明。又，從與作注目之受訊 導體X】24相交叉之其他的送訊導體12，係被供給有其他之 展頻碼（C!以及（：3〜（^6)，並且假設在作注目之交叉點 以外的交叉點處，係並不存在有指示體1 9。 首先，參考圖1 3，針對指示體1 9並不存在於感測部 1 00上的情況時之藉由受訊導體1 4所得到的相關値作說明 。當指示體19並不存在於此交叉點上時，受訊導體14係僅 與送訊導體12作靜電耦合（參考圖12(a))。其結果，由於 應流動至受訊導體1 4處之電流係全部流動至受訊導體丨4處 -39- 201122922 ，因此，在對於從受訊導體X! 24而來之輸出訊號作相關演 算所得到的相關値中，相關器之輸出訊號與展頻碼之碼編 號間之相關特性係成爲一定之値（參考圖1 3 (b))。 相對於此，當指示體19存在於交叉點上的情況時，受 訊導體x9，係成爲經由指示體1 9來與接地作了靜電耦合的 狀態（參考圖1 2(b))。如此一來，如圖1 4 ( a )中所示一 般，原本應該流動至受訊導體X9處之電流的一部份，係經 由指示體1 9而分流至接地處。其結果，若是對於從受訊導 體X! 24而來之輸出訊號作相關演算，則相關器之輸出訊號 與展頻碼之碼編號之間的相關特性，在此展頻碼C2處所得 到之相關値係成爲較藉由在其他之展頻碼處的相關演算所 得到之相關値而更小（參考圖1 4(b))。 故而，依據在圖1 4 ( b )中所示之相關特性是在何者 之展頻碼的相關値處而出現凹陷一事，能夠將構成被放置 有指示體19之交叉點的送訊導體特定出來。於圖14所示之 例中，由於係在展頻碼C2處而產生有相關値降低之大的凹 陷區域，因此，可以特定出，被供給有此展頻碼C2之送訊 導體Y9，係爲指示體19所被放置之送訊導體。而，藉由在 被記憶於相關値記憶電路34d中的相關値之空間分布中而 特定出相關値爲較特定之臨限値更小的區域，能夠將感測 部1 〇〇上之指示體1 9的位置（座標）檢測出來。 接著，參考圖15以及16，對於身爲指示體的1根之手 指19被放置在感測部100的複數之交叉點上的情況時之位 置檢測的原理作說明。在以下之說明中，爲了能夠容易地 -40- 201122922 理解此位置檢測之原理，假設在各送訊導體γ!〜γ64處係 被供給有各展頻碼（^〜（：16(參考圖4)，並對於如同圖15 中所示一般之1根的手指1 9被放置在涵蓋於受訊導體X, 24 與送訊導體Y i〜Υ4之間之複數的交叉點處的情況來作考慮 。另外，在指示體19所被放置之送訊導體Yi〜Υ4處，係被 供給有展頻碼C丨。 在此圖1 5中所示之狀態下，在受訊導體X ! 24與送訊導 體Yi〜Y4之各個間所形成的複數之交叉點處，流入至受訊 導體X! 24中之電流係減少。故而，如同圖16 ( a)中所示一 般，在受訊導體XI24處之相關器的輸出訊號與展頻碼的碼 編號之間的相關特性6 4，在展頻碼C ,處而藉由相關演算所 得到之相關値，係成爲較藉由在其他之展頻碼處的相關演 算所得到之相關値更小。當將展頻碼C ,供給至送訊導體Y2 〜Υ4處時，亦會成爲與此圖16(a)相同之特性。 另一方面，在被形成於送訊導體Xi 24與受訊導體Υ5〜 Υ64的各個間之複數的交叉點處，由於係並不存在有指示 體1 9，因此，如同圖1 6 ( b )中所示一般，相關特性6 5係 成爲一定之値。 如此這般，本發明，就算是指示體涵蓋於複數之交叉 點而被作放置的情況時，亦能夠將指示體之有無檢測出來 。另外，若是在上述之位置檢測電路35處設置內插處理電 路，則由於亦能夠將在交叉點間之指示體1 9的存在與否檢 測出來，因此，係成爲亦能夠對於被放置在感測部1 00上 之指示體1 9的形狀作推測。 -41 - 201122922 〔哈德瑪得碼之例〕 在上述第1實施形態之例中，係對於在 100之訊號中而供給具備有211碼片之碼長度 例子而作了展示。在此展頻碼Ck中，係亦可 碼。參考圖17，針對使用有此哈德瑪得碼的 說明。 圖17(a)，係爲由16碼片之碼列 瑪得矩陣。構成各碼列C i〜C· 1 6之各碼片的 者是+ 1。以下，將此碼列C ,〜C , 6稱爲哈德現 此哈德瑪得矩陣，由於1 6種之哈德瑪ί 相互具備有完全性的正交關係，因此，能夠 碼（^〜（：16與相關値演算用碼Cl，〜Cl6，設爲 ，進行相關演算之相關器，係可代替圖1 0中 34f!〜34f16而使用加算器。又，在使用有此 的情況時’當藉由相關器而檢測出來存在有 ’係如圖1 7 ( c )中所示一般，在存在有相 碼C x之相關演算的情況時，相關値係降低， 在該碼處之相關的存在。但是，就算是在存 況時，相關値之準位亦係爲較〇準位而更高纪 另外’在將此圖1 7 ( a )之哈德瑪得矩 明之指示體檢測裝置中的情況時，由於構成 之各哈德瑪得碼Cl〜Ci6，係全部的第1碼片 爲1 ’因此’若是藉由相關器而進行此碼片 供給至感測部 的展頻碼ck2 使用哈德瑪得 情況之例子作 〕1 6所成之哈德 値，係爲-1或 丨得碼。 1=碼C 1〜C 1 6係 將各哈德瑪得 相同之碼。又 所示之乘算器 哈德瑪得矩陣 相關的情況時 關之哈德瑪得 而能夠檢測出 在有相關的情 I準位。 陣使用在本發 哈德瑪得矩陣 的位元均係成 位置之相關演 -42- 201122922 算，則相關値係會顯著地變高。故而，在此圖1 7 ( b )之 例中’係將哈德瑪得碼藉由1 5碼片來構成。此藉由丨5碼片 之碼所形成的16種類之哈德瑪得碼Ci〜Cl6，如同與圖17 (a )作比較而能夠得知一般，係成爲將丨6碼片之哈德瑪 得碼的開頭之第1碼片作了除去的構成。 藉由使用於此圖17(b)中所示之藉由15碼片之碼所 形成的1 6種類之哈德瑪得碼C,〜C】6，如圖1 7 ( d )中所示 一般，作爲相關器之輸出訊號，當存在有相關時，係成爲 0準位以下之訊號’而當不存在有相關的情況時，則係成 爲0準位以上之特定準位，而能夠將振幅縮小。 〔位置檢測之處理程序〕 接著，參考圖1、圖6以及圖18之流程圖，針對在此第 1實施形態中之指示體檢測裝置1的動作作說明。 首先，展頻碼供給電路21之各展頻碼產生電路24，係 分別產生展頻碼(^〜0：16 (步驟S1)。接著，受訊部300之 受訊導體選擇電路3 1，係藉由開關3 1 a而在各檢測區塊36 內將特定之受訊導體14與I/V變換電路32a相連接（步驟 S2 ) 〇 接著，若是送訊導體選擇電路22在各送訊區塊25內而 對於供給展頻碼Ci〜C16之特定的送訊導體12作選擇（步 驟S3)，則係對於在各送訊區塊25處所被選擇了的特定之 送訊導體1 2而分別將相對應之展頻碼C ,〜C , 6同時性地作 供給（步驟S 4 )。 -43- 201122922 接著，受訊部3 00，係將由在步驟S2處而選擇了的各 檢測區塊36之特定的受訊導體14而來之輸出訊號Si同時性 地檢測出來（步驟S5)。具體而言，首先，放大電路32, 係將身爲從所選擇了的特定之受訊導體14 (合計16根之受 訊導體14)而來的輸出訊號之電流訊號，在I/V變換電路 3 2a處而變換爲電壓訊號並作放大，再將該放大訊號輸出 至A/D變換電路33處。接著，A/D變換電路33，係將被 輸入了的電壓訊號變換爲數位訊號，並將此數位訊號輸出 至相關値算出電路34處。 . 接著，相關値算出電路3 4，係針對被輸入了的數位訊 號和相關値演算用碼C , ’〜C , 6 ’而分別進行相關演算，並將 該値記憶在相關値記憶電路34d中（步驟S6 )。 接著，控制電路40，係對於在藉由步驟S4所選擇了的 受訊導體14處，是否對於全部的送訊導體12而結束了相關 演算一事作判定（步驟S7)。當並未對於選擇了的受訊導 體1 4而在全部的送訊導體1 2處結束位置檢測的情況時、亦 即是當步驟S7之判定結果係爲NO的情況時，係回到步驟 S3，並對於送訊導體選擇電路22內之各送訊區塊25的開關 22 a作切換，而對於與前一次相異之送訊導體12作選擇， 並反覆進行步驟S3〜S6。之後，反覆進行步驟S3〜S6，直 到對於所選擇了的受訊導體14而在全部的送訊導體12處之 位置檢測均結束爲止。 亦即是，如圖6中所示一般，若是假設最初係選擇了 受訊導體Xi、X9.....X12l，貝IJ展頻碼C,〜C16，係首先被 -44- 201122922 供給至送訊導體γ4、γ8.....Υ64處。接著 的受訊導體維持原狀，並將供給展頻碼Cr 體切換爲送訊導體Y3、Y7.....Y63而進行 的進行相關演算。若是反覆進行此處理，並 Υι ' Y2.....Y6I分別供給展頻碼c,〜c16， 算，則各送訊群組2 5內之送訊導體1 2的切換 環，對於受訊導體X!、x9.....XI2I之全部 位置檢測係結束（步驟S7之YES狀態）。如 在所選擇了的受訊導體14處之全部送訊導體 束，則係移行至步驟S8。 當對於在步驟S2中所選擇了的受訊導體 導體1 2處的相關演算均結束的情況時，亦即 判定結果係爲YES的情況時，控制電路40， 受訊導體1 4處之位置檢測是否均結束（步驟 部受訊導體1 4處之相關演算並未結束的情況 步驟S 8之判定結果係爲Ν Ο的情況時，係回 對於送訊導體選擇電路22內之各開關22a作 送訊導體1 2作選擇。而後，藉由展頻碼供給 於所選擇了的複數之送訊導體1 2而同時性地 〜C16。如此這般，而對於送訊導體12以及 切換並繼續進行相關演算。之後，反覆進行 直到對於全部受訊導體I4之在全部的送訊導 演算均結束爲止。 亦即是，如圖6中所示一般，例如在受 ，將被選擇了 〜C16之送訊導 供給，且同樣 對於送訊導體 而進行相關演 係被作了一循 送訊導體12的 此這般，若是 1 2的檢測均結 14之全部送訊 是當步驟S 7之 係判定在全部 S8 )。當在全 時、亦即是當 到步驟S 2，並 切換，而對於 電路21，來對 供給展頻碼C i 受訊導體1 4作 步驟S2〜S7， 體12處的相關 訊導體Xl、χ9 -45- 201122922 .....x , 2 ,被作了選擇的狀態下，而使各送訊群組2 5內之 送訊導體12作循環，並對於受訊導體X,、X9、…X121而進 行在全部送訊導體I2處之相關演算。接著，切換爲受訊導 體x2、X1().....Xi22，並使各送訊群組25內之送訊導體12 作循環。反覆進行此處理，並對於受訊導體1 4依序作切換 。而後，若是對於循環中之最後的受訊導體X8、Xl6、… 、X128而結束了相關演算，則係移行至步驟S9，或者是回 到最初之步驟S 2。 位置檢測電路3 5，係由被記憶在相關値算出電路3 4之 相關値記憶電路34d中的受訊導體Μ之交叉點處的訊號， 而將輸出了訊號準位有所減少的訊號之受訊導體1 4與其展 頻碼檢測出來。而後，根據由訊號準位而特定出來的受訊 導體14之索引標號m ( 1〜128)與供給了該展頻碼之送訊 導體12的索引標號n(l〜64)，來算出指示體之位置（步 驟S9 )。如此這般，而進行被配置在感測部1 〇〇上之指示 體的位置檢測。 如同上述一般，在此第1實施形態中，係對於各群組 之特定的送訊導體12而將碼互爲相異之展頻碼同時作供給 (多重送訊），並藉由特定之複數的受訊導體14而同時檢 測出指示體之位置。亦即是，係對於送訊導體1 2以及受訊 導體1 4間之複數的交叉點而同時地進行位置檢測處理。其 結果，係能夠將對於複數之交叉點的位置檢測中所耗費的 時間縮短’而成爲能夠更高速地進行指示體之位置檢測。 亦即是’在第1實施形態中，由於係將送訊導體群1 1 -46- 201122922 以及受訊導體群1 3分別區分爲1 6個的群組，並對於各群組 而進行平行處理，因此，例如，相較於如同先前技術一般 之對於所有交叉點而依序進行檢測處理的情況時之檢測時 間，係能夠將其之檢測時間縮短爲1 /( 1 6X 1 6 )。另外， 群組數係並非爲被限定於此例者，又，當然，就算是僅將 送訊導體群11或者是受訊導體群13之其中一者作群組化， 亦能夠得到檢測時間之縮短效果。 如同上述一般，本發明之指示體檢測裝置，由於係成 爲能夠在複數之交叉點處而同時地且高速度將指示體檢測 出來’因此，不但可以將由1個使用者之複數的指示體所 致的指示位置之檢測以高速來進行，並且亦能夠進行由複 數人的複數之手指等的指示體所致之指示位置的同時檢測 。由於不論使用者之多寡均能夠進行複數之指示體的同時 檢測，因此，係能夠對於各種之應用程式的發展有所助益 。另外，由於係能夠進行複數之指示體的同時檢測，因此 ，不用說，當然亦能夠進行由1個的指示體所致之位置指 示的檢測。 又，在此第1實施形態中，係以若是針對1個的受訊導 體而結束了在全部送訊導體處之檢測，則切換至其他之一 個的受訊導體並繼續進行位置檢測的情況而作了說明，但 是，本發明係並不被限定於此例。亦可設爲在對於1個的 受訊導體之全部送訊導體處的檢測結束之前，便切換至其 他之1個的受訊導體並繼續進行位置檢測，只要在最終能 夠使感測部1 〇 〇之全部交叉點處的位置檢測均被進行即可 -47- 201122922 又’在上述第1實施形態中’雖係針對檢測出指示體 之位置的例子而作了說明，但是，本發明係並不被限定於 此。例如’亦可將第1實施形態之指示體檢測裝置。作爲 由所得到之相關値來僅將指示體之存在與否檢測出來的裝 置而使用之。另外，於此情況’係亦可並不設置位置檢測 電路35。 <2、第2實施形態：使用被作了 PSK調變後之展頻碼的構成 例> 在上述第1實施形態中，雖係針對將展頻碼ck直接供 給至送訊導體群1 1處的例子而作了說明，但是，本發明係 並不被限定於此。例如，亦可對於展頻碼ck而施加特定之 調變，並將該調變後的訊號供給至送訊導體群1 1處。在第 2實施形態中，係對於將供給至送訊導體群1 1處的展頻碼 Ck作PSK ( Phase Shift Keying)調變的構成例作說明。 〔PSK調變〕 在圖19(a)以及（b)中，展示展頻碼之PSK調變前 後的波形。圖19 ( a )，係爲在PSK調變前的展頻碼之波形 ，圖19 ( b )，係爲PSK調變後的展頻碼之波形。 在此第2實施形態中，例如，係針對藉由調變前之展 頻碼Ck的時脈週期（碼片週期）之2倍的時脈週期之訊號 ，來對於展頻碼Ck作PSK調變之例，而進行說明。另外， -48- 201122922 本發明，係並不被限定於此，調變時之時脈週期與碼片週 期間的比’係可因應於用途而適宜作變更。此PSK調變， 例如’係於調變前之展頻碼（圖1 9(a))處，當訊號準位爲 High時’係在從Low而開始之時序處而將訊號作反轉，當 訊號準位爲Low時，係在從High而開始之時序處而將訊號 作反轉，藉由此，而得到調變訊號（圖1 9(b))。 〔指示體檢測裝置之構成〕 根據圖20，針對在第2實施形態中之指示體檢測裝置2 的構成作說明。此第2實施形態之指示體檢測裝置2，係由 感測部1 〇〇、和送訊部20 1、和受訊部3 0 1、以及控制電路 40所構成。此第2實施形態中之指示體檢測裝置2，與第1 實施形態中之指示體檢測裝置1 (參考圖1 )的相異之點， 係在於：送訊部201係爲藉由被設置有對於展頻碼Ck施加 PSK調變之PSK調變電路的展頻碼供給電路221、和時脈產 生電路23所構成，以及，受訊部301，係具備著設置有將 被作了 PSK調變後之展頻碼Ck作解調之PSK解調電路的相 關値算出電路3 04而被構成。此些以外之構成，由於係爲 與第1實施形態（圖1 )相同，因此，關於相同之構成’係 附加與圖1相同之號碼，並省略詳細之說明。另外’在此 第2實施形態中，例如係對於使用63碼片長度之展頻碼Ck ，並使用此展頻碼Ck2 2倍的時脈訊號來施加PSK調變’而 產生1 26時脈長之調變訊號的情況作例示說明。 接著，參考圖2 1，針對在第2實施形態中之展頻碼供 -49- 201122922 給電路20 1的構成作說明。展頻碼供給電路22 1，係由複數 之展頻碼產生電路24以及PSK調變電路26所構成。PSK調 變電路26，由於係將根據從時脈產生電路23所供給之相同 的時脈而相互同步產生的1 6種類之展頻碼C !、C2..... C, 6分別作PSK調變，因此，係被設置在各展頻碼產生電路 24之輸出端子處。亦即是，此PSK調變電路26，係被設置 有與展頻碼產生電路24相同之數量（16個）。而，各PSK 調變電路26，係分別將各展頻碼C,〜C16作PSK調變，並產 生16種類之PSK調變訊號C1P、C2P.....C16P。而後，此 PSK調變訊號C1P〜C16P係被供給至送訊導體12處。 接著，參考圖22，針對在此第2實施形態中之相關値 算出電路3 04的構成作說明。此圖22，係爲對於在第2實施 形態中之相關値算出電路304的電路構成、以及此相關値 算出電路304和I/V變換電路32a以及A/D變換電路33間 之連接關係作展示之圖》 相關値算出電路304，係由PSK解調電路126、和訊號 延遲電路304a、和16個的相關器304b,' 304b2、304b3、… 、3 04b16、和相關値演算用碼產生電路304Cl〜304c16、以 及相關値記憶電路304d所構成。 訊號延遲電路304a，係與上述之第1實施形態中的訊 號延遲電路34a相同的，爲用以將從A/ D變換電路33所輸 入而來之數位訊號暫時性地作保持，並將此被作了保持的 資料同時地供給至各相關器3 04b,〜304b16處之電路。此訊 號延遲電路304a，係由與展頻碼之碼長度.相同數量（63個 -50- 201122922 )的 D-正反器電路 304a丨、304a2、304a3 ..... 3 04a62、 3 04a63所構成。而，此D-正反器電路304a63、304a62、The Sclk rise timing U, t2, t4, ... is used as a reference, and is repeated. On the other hand, the correlation calculation circuit 134 is when the pulse of the signal loaded with the signal is HIGH level, and the clock signal is at the clock signal. Selk rises at the timing (in Figure 11, at time t3), and from the correlation 値 calculus code generation circuit 134cx, sequentially generates 16 types of correlation 値 calculus, ~C16, 'and supplies To the correlator 34b, at. The correlator 34bx is when the received signal Sr|Qad is at the HIGH level and is at the timing of the clock signal Selk -37-201122922, and the correlation calculus is started with the code cr~cie' and is set. The correlation between the signals in the register 1 34e (Fig. 1 1 (f)). Then, the correlator 3 4bx sequentially outputs the calculation result to the relevant 値 memory circuit 34d (Fig. 11(g)). Then, as shown in Figs. 1 1 (f) and (g), the same correlation calculation is performed for the spread codes C2 to C16, and the calculation result is output to the relevant memory circuit 34 (1 place). Correlation between the respective calculus codes C Γ to c 16 ' is obtained as described above. [Principle of Position Detection] Next, the principle of position detection of the pointer detecting apparatus 1 of the present invention is referred to 12 to 16. As described above, the general invention of the present invention is a cross-point electrostatic coupling method, and is based on a change in the electrostatic coupling state between the transmission conductor and the signal conductor of the sensing portion. First, referring to Fig. 12, the principle of detection of the pointer will be described. Here, Fig. 12 (a) and (b) are for the indicator of the finger or the like in the sensing unit 1 A cross-sectional view showing the state of the sputum and the electrostatic coupling state between the transmitting conductor 12 and the receiving conductor 并不 without being present on the sensing unit 100. When the indicator 19 does not exist in the sensing In the case of Department 1 00, as shown in Figure 12 (a) Generally, the communication conductor 12 disposed on the first substrate 15 and the signal conductor 14 disposed on the second substrate 17 are electrostatically coupled via the spacer 16 and are sent from each other. The electric field emitted by the conductor 12 is converged at the signal conductor 14 and as a result, all of the current flows from the signal conductor -38 - 201122922 body I2 toward the signal conductor !4. When the indicator 19 is present on the sensing portion 1 ,, as shown in FIG. 12 (b), the received conductor 14 is not only coupled to the transmitting conductor 12 but Also in a state of being electrostatically coupled to the ground via the indicator body 19. In this state, a portion of the electric field emitted from the transmitting conductor 12 is converged at the indicator body 19 and is transmitted. A portion of the current flowing through the conductor 12 toward the signal conductor 14 is shunted to the ground via the indicator 19. As a result, the current flowing into the signal conductor 14 is reduced. This current change is detected, and the indicated position caused by the indicator 19 is detected. Next, according to FIG. 13 and FIG. The calculation principle of the coordinates of the indicated position by the pointer will be described. In the following description, in order to be able to easily understand the principle, the signal conductor Y9 to which the spread code C2 is supplied is used. The intersection between the received conductors Xl24 (the position indicated by a white circle in Fig. 13(a). Hereinafter, simply referred to as the intersection) is noted, and at this intersection, due to the presence of the indicator 19 In addition, the other transmission conductors 12 that are crossed from the attention conductor X] 24 are supplied with other spreading codes (C! and (:3). ~(^6), and it is assumed that there is no indicator 19 at the intersection other than the intersection of the attention. First, referring to Fig. 13, a description will be given of the correlation obtained by the received conductor 14 in the case where the indicator 19 does not exist on the sensing unit 100. When the indicator 19 does not exist at this intersection, the signal conductor 14 is only electrostatically coupled to the signal conductor 12 (refer to Fig. 12(a)). As a result, since the current that should flow to the signal conductor 14 flows to the signal conductor 丨4 at -39-201122922, the correlation signal is obtained for the output signal from the signal conductor X! In the obtained correlation, the correlation between the output signal of the correlator and the code number of the spread spectrum code becomes a certain factor (refer to Figure 13 (b)). On the other hand, when the indicator 19 is present at the intersection, the reception conductor x9 is in a state of being electrostatically coupled to the ground via the pointer 19 (refer to Fig. 12(b)). As a result, as shown in Fig. 14 (a), a portion of the current which should originally flow to the signal conductor X9 is shunted to the ground via the indicator 19. As a result, if the output signal from the signal conductor X! 24 is correlated, the correlation between the output signal of the correlator and the code number of the spreading code is obtained at the spread code C2. The tether is smaller than the correlation obtained by the correlation calculations at other spreading codes (refer to Figure 14(b)). Therefore, according to the fact that the correlation characteristic shown in Fig. 14 (b) is the depression of the spread code of which one, the communication conductor constituting the intersection where the indicator 19 is placed can be specified. . In the example shown in FIG. 14, since the recessed area having a large correlation is reduced at the spread code C2, the signal conductor Y9 to which the spread code C2 is supplied can be specified. It is a signal conductor in which the indicator body 19 is placed. However, by specifying a region in which the correlation 値 is smaller than the specific threshold 在 in the spatial distribution of the correlation 记忆 memorized in the correlation 値 memory circuit 34d, the indicator portion of the sensing portion 1 can be displayed. The position (coordinate) of 1 9 is detected. Next, with reference to Figs. 15 and 16, the principle of position detection in the case where one finger 19 which is a pointer is placed at the intersection of the plurality of fingers of the sensing unit 100 will be described. In the following description, in order to be able to easily understand the principle of the position detection, it is assumed that each of the transmission conductors γ! to γ64 is supplied with each spreading code (^~(:16 (refer to FIG. 4). And consider the case where the finger 1 9 as shown in Fig. 15 is placed at the intersection of the complex number between the signal conductor X, 24 and the signal conductors Y i Υ 4 Further, at the signal conductors Yi to Υ4 where the indicator 19 is placed, the spread code C is supplied. In the state shown in Fig. 15, the signal conductor X! 24 is sent and sent. At the intersection of the complex numbers formed between the respective conductors Yi to Y4, the current flowing into the signal conductor X! 24 is reduced. Therefore, as shown in Fig. 16 (a), at the signal conductor XI24 The correlation between the output signal of the correlator and the code number of the spreading code is 4 4, and the correlation code obtained by the correlation algorithm in the spreading code C is compared with the other spreading code. The relevant calculus obtained at the relevant point is smaller. When the spread code C is supplied to the communication conductors Y2 to Υ4, The characteristics are the same as those of Fig. 16(a). On the other hand, at the intersection of the plurality of signal conductors Xi 24 and the receiving conductors Υ5 to Υ64, there is no indicator. Therefore, as shown in Fig. 16 (b), the correlation characteristic 6.5 is a certain degree. Thus, the present invention, even if the indicator is covered at the intersection of the plural, is placed. In addition, it is also possible to detect the presence or absence of the pointer. Further, if the interpolation processing circuit is provided in the position detecting circuit 35, the presence or absence of the pointer 19 between the intersections can be detected. Therefore, it is possible to estimate the shape of the pointer 19 placed on the sensing unit 100. -41 - 201122922 [Example of Hadmar Code] In the example of the first embodiment described above, An example of providing a code length with 211 chips in the signal of 100 is shown. In this spread code Ck, it can also be coded. Referring to FIG. 17, a description of the use of the Hadmar code is used. Figure 17(a) is a code of 16 chips. The matrix is composed of + 1 for each chip constituting each code column C i~C·16. Hereinafter, this code sequence C, ~C, 6 is called Harder and the Hadmade matrix, since 16 Hadmar ί has a complete orthogonal relationship with each other. Therefore, it is possible to code (^~(:16 and related calculus code Cl, ~Cl6, set to correlate with the relevant calculus). In Figure 10, 34f!~34f16 and the adder are used. Also, when using the case, 'when the correlator detects the presence exists', as shown in Figure 17 (c), there is In the case of the correlation calculus of the phase code C x , the correlation 降低 is reduced and the correlation exists at the code. However, even in the case of the situation, the relevant level of the 値 is also higher than the standard and the other is in the case of the indicator detection device of Hadma, which is shown in Figure 17 (a). At this time, since each of the Hadmar code C1 to Ci6 is composed, all the first chips are 1'. Therefore, if the chip is supplied to the sensing unit by the correlator, the spread code ck2 is used. The example of the situation of Ma De is made by the 1st of the 6th Had, which is -1 or the code. 1 = Code C 1~C 1 6 The code will be the same for each Harder. The multipliers shown in the Hadmade matrix are also related to Hadmade and can be detected in the relevant I level. The arrays used in the Harvard matrix of the local are all related to the position -42- 201122922, then the relevant 値 system will become significantly higher. Therefore, in the example of Fig. 17 (b), the Hadmar code is composed of 15 chips. The 16 types of Hadmar code Ci~Cl6 formed by the code of 5 chips are as compared with FIG. 17(a), and it is known that it is a Hadma with 6 chips. The first chip of the beginning of the code is removed. By using the 16-type Hadmar code C, ~C]6 formed by the 15-chip code shown in Fig. 17(b), as shown in Fig. 17 (d) Generally, the output signal of the correlator is a signal below the zero level when there is correlation, and when there is no correlation, it is a specific level above the zero level, and the amplitude can be Zoom out. [Processing Procedure of Position Detection] Next, the operation of the pointer detecting apparatus 1 in the first embodiment will be described with reference to the flowcharts of Figs. 1, 6, and 18. First, each of the spread spectrum code generating circuits 24 of the spread spectrum code supply circuit 21 generates a spread spectrum code (^~0:16 (step S1). Then, the received conductor selection circuit 31 of the signal receiving unit 300 is The specific signal conductor 14 is connected to the I/V conversion circuit 32a in each detection block 36 by the switch 31a (step S2). Next, if the transmission conductor selection circuit 22 is in each of the transmission blocks 25, for selecting the specific transmission conductor 12 to which the spread code Ci to C16 is supplied (step S3), respectively, for the specific transmission conductor 12 selected at each of the communication blocks 25, respectively The corresponding spreading codes C, ~C, and 6 are simultaneously supplied (step S4). -43- 201122922 Next, the receiving unit 300 is determined by the detecting blocks 36 selected at step S2. The output signal Si from the specific signal conductor 14 is simultaneously detected (step S5). Specifically, first, the amplifying circuit 32 is selected as the selected specific conductor 14 (total) The current signal of the output signal from the 16 signal conductor 14) is converted into a voltage signal at the I/V conversion circuit 32a And amplified, and then the amplified signal is output to the A/D conversion circuit 33. Then, the A/D conversion circuit 33 converts the input voltage signal into a digital signal, and outputs the digital signal to the relevant 値Then, the circuit 34 is calculated. Then, the correlation calculation circuit 34 performs correlation calculation on the input digital signal and the related 値 calculation code C, '~C , 6 ', and memorizes the correlation. In the memory circuit 34d (step S6). Next, the control circuit 40 determines whether or not the correlation calculation is completed for all of the transmission conductors 12 at the signal conductor 14 selected by the step S4 ( Step S7). When the position detection is not completed at all of the transmission conductors 1 for the selected signal conductors 1 4, that is, when the result of the determination in step S7 is NO, Returning to step S3, the switch 22a of each of the transmitting blocks 25 in the transmitting conductor selection circuit 22 is switched, and the transmitting conductor 12 is selected differently from the previous time, and steps S3 to S6 are repeatedly performed. After that, step S3 is repeated. S6, until the position detection at all the signal conductors 12 is completed for the selected signal conductor 14. That is, as shown in FIG. 6, if it is assumed that the signal conductor Xi is selected initially. , X9.....X12l, Bay IJ spread code C, ~C16, is first supplied to the signal conductor γ4, γ8.....Υ64 by -44- 201122922. The subsequent signal conductor remains as it is. The correlation calculation is performed by switching the supply of the spread code Cr body to the transmission conductors Y3, Y7, ..., Y63. If this process is repeated, and Υι 'Y2.....Y6I is supplied to the spread code c, ~c16, respectively, the switching ring of the transmitting conductor 12 in each transmitting group 2 5 is received. All the position detection systems of the conductors X!, x9, ..., XI2I are completed (YES state of step S7). If all of the signal conductor bundles at the selected signal conductor 14 are selected, the process proceeds to step S8. When the correlation calculation at the signal conductor conductor 12 selected in step S2 is completed, that is, when the determination result is YES, the control circuit 40 detects the position of the signal conductor 14 In the case where the correlation calculation at the step-receiving conductor 14 is not completed (when the result of the determination in step S8 is Ν ,), it is sent back to each switch 22a in the transmission conductor selection circuit 22. The conductor 1 2 is selected. Then, the spreading code is supplied to the selected plurality of transmitting conductors 12 and simultaneously to C16. Thus, for the transmitting conductor 12 and switching and continuing the correlation After the calculation, it is repeated until all the communication directors of all the received conductors I4 are finished. That is, as shown in FIG. 6, for example, in the acceptance, the transmission of ~C16 will be selected. The supply is also performed, and the same performance is also performed for the transmission conductor. The same is true for the transmission conductor 12. If all of the detections of the detection of 14 are 14, the decision is made at step S7. S8). When it is at full time, that is, when it is to step S2, and is switched, and for the circuit 21, the supply of the spread spectrum code C i the signal conductor 14 is performed as steps S2 S S7, the relevant signal conductor X1 at the body 12, Χ9 -45- 201122922 .....x , 2 , in the selected state, the transmission conductor 12 in each communication group 25 is circulated, and for the signal conductor X, X9, ...X121 performs the correlation calculation at all the signal conductors I2. Next, the signals are switched to the received conductors x2, X1(), ..., Xi22, and the signal conductors 12 in the respective communication groups 25 are cycled. This processing is repeated, and the received conductors 1 4 are sequentially switched. Then, if the correlation calculation is completed for the last received conductor X8, Xl6, ..., X128 in the loop, the process proceeds to step S9, or returns to the first step S2. The position detecting circuit 35 is a signal which is stored at the intersection of the received conductors 中 in the associated memory circuit 34d of the associated 値 calculating circuit 34, and outputs a signal whose signal level is reduced. The conductor 14 is detected with its spread code. Then, the index body is calculated based on the index number m (1 to 128) of the signal conductor 14 specified by the signal level and the index number n (l to 64) of the signal conductor 12 to which the spreading code is supplied. The position (step S9). In this manner, the position detection of the pointer placed on the sensing unit 1 is performed. As described above, in the first embodiment, the spreading codes having mutually different codes are simultaneously supplied (multiple transmission) for the specific transmission conductors 12 of the respective groups, and by the specific plural The signal conductor 14 is simultaneously detected to detect the position of the indicator. That is, the position detecting process is simultaneously performed on the intersection of the plurality of signal conductors 1 2 and the received conductors 14 . As a result, it is possible to shorten the time taken for detecting the position of the intersection of the plurality of points, and it is possible to perform position detection of the pointer at a higher speed. In other words, in the first embodiment, the group of the transmission conductor groups 1 1 - 46 to 201122922 and the group of the received conductor groups 13 are respectively divided into 16 groups, and parallel processing is performed for each group. Therefore, for example, the detection time in the case where the detection processing is sequentially performed for all the intersections as in the prior art can be shortened to 1 / (16×16). In addition, the number of groups is not limited to this example, and of course, even if only one of the transmission conductor group 11 or the signal conductor group 13 is grouped, the detection time can be obtained. Shorten the effect. As described above, the pointer detecting apparatus of the present invention is capable of detecting the indicator at the same time and at a high speed at the intersection of the plurality of numbers. Therefore, not only the plurality of indicators of one user can be caused. The detection of the indicated position is performed at a high speed, and simultaneous detection of the indicated position by the indicator of a plurality of fingers of a plurality of persons can also be performed. Since the number of users can be simultaneously detected by a plurality of indicators, it is possible to contribute to the development of various applications. Further, since it is possible to perform simultaneous detection of a plurality of pointers, it goes without saying that it is of course possible to detect the position indication by one indicator. Further, in the first embodiment, when the detection of all the transmission conductors is completed for one of the signal conductors, the signal is switched to the other received conductor and the position detection is continued. Although the description is made, the present invention is not limited to this example. It is also possible to switch to the other one of the received conductors and continue the position detection until the detection of all the signal conductors of one of the received conductors is completed, as long as the sensing unit 1 can be finally made. In the above-described first embodiment, the position detection is performed on the position where the indicator is detected. However, the present invention is Not limited to this. For example, the pointer detecting device of the first embodiment can also be used. It is used as a means for detecting the presence or absence of a pointer from the obtained correlation. Further, in this case, the position detecting circuit 35 may not be provided. <2. Second Embodiment: Configuration Example of Spreading Code Using PSK Modulation> In the first embodiment, the spread code ck is directly supplied to the transmission conductor group 1 The example of one is explained, but the present invention is not limited thereto. For example, a specific modulation may be applied to the spread spectrum code ck, and the modulated signal may be supplied to the transmission conductor group 1 1 . In the second embodiment, a configuration example in which the spread code Ck supplied to the transmission conductor group 1 1 is modulated by PSK (Phase Shift Keying) will be described. [PSK Modulation] In Figs. 19(a) and (b), the waveforms before and after the PSK modulation of the spread spectrum code are shown. Fig. 19 (a) shows the waveform of the spread spectrum code before the PSK modulation, and Fig. 19 (b) shows the waveform of the spread spectrum code after the PSK modulation. In the second embodiment, for example, the PSK tone is adjusted for the spread code Ck by the signal of the clock period twice the clock period (chip period) of the spread code Ck before the modulation. Change the example and explain. Further, the present invention is not limited thereto, and the ratio of the clock period to the chip circumference period at the time of modulation can be appropriately changed depending on the application. This PSK modulation, for example, is based on the spread spectrum code before the modulation (Fig. 19(a)). When the signal level is High, the signal is inverted at the timing starting from Low. When the signal level is Low, the signal is inverted at the timing starting from High, thereby obtaining a modulation signal (Fig. 19(b)). [Configuration of Indicator Detection Apparatus] A configuration of the pointer detection apparatus 2 according to the second embodiment will be described with reference to Fig. 20 . The pointer detecting device 2 of the second embodiment is composed of a sensing unit 1 and a transmitting unit 20 1 , a receiving unit 301, and a control circuit 40. The pointer detecting device 2 according to the second embodiment differs from the pointer detecting device 1 (refer to FIG. 1) in the first embodiment in that the transmitting unit 201 is provided with The spread spectrum code supply circuit 221 and the clock generation circuit 23 of the PSK modulation circuit to which the PSK modulation is applied to the spread spectrum code Ck are configured, and the reception unit 301 is provided with a PSK tone. The converted spread code Ck is configured as a correlation calculation circuit 307 for demodulating the PSK demodulation circuit. The configuration is the same as that of the first embodiment (Fig. 1), and the same reference numerals are attached to the same components as in Fig. 1, and the detailed description thereof will be omitted. Further, in the second embodiment, for example, the PSK modulation is applied to the spread code Ck of 63 chips length and the clock signal of 2 times the spread code Ck2 is used to generate a pulse length of 1 26 hours. The case of the modulated signal is exemplified. Next, a configuration of the circuit 20 1 for the spread spectrum code in the second embodiment will be described with reference to Fig. 2 1. The spread code supply circuit 22 1 is composed of a plurality of spread spectrum code generating circuits 24 and a PSK modulation circuit 26. The PSK modulation circuit 26 is made up of 16 types of spreading codes C!, C2..... C, 6 which are generated in synchronization with each other based on the same clock supplied from the clock generating circuit 23. The PSK is modulated, and therefore, is set at the output terminal of each spread code generating circuit 24. That is, the PSK modulation circuit 26 is provided in the same number (16) as the spread code generation circuit 24. Further, each PSK modulation circuit 26 performs PSK modulation on each of the spread codes C, C16, and generates 16 types of PSK modulation signals C1P, C2P, ..., C16P. Then, the PSK modulation signals C1P to C16P are supplied to the transmission conductor 12. Next, the configuration of the correlation 算出 calculation circuit 404 in the second embodiment will be described with reference to Fig. 22 . 22 is a diagram showing the circuit configuration of the correlation calculation circuit 304 in the second embodiment, and the connection relationship between the correlation calculation circuit 304, the I/V conversion circuit 32a, and the A/D conversion circuit 33. The correlation diagram calculation circuit 304 is composed of a PSK demodulation circuit 126, a signal delay circuit 304a, and 16 correlators 304b, '304b2, 304b3, ..., 3 04b16, and associated 値 calculation code generation circuit 304Cl. ~304c16, and associated memory circuit 304d. The signal delay circuit 304a is the same as the signal delay circuit 34a of the first embodiment described above, and is for temporarily holding the digital signal input from the A/D conversion circuit 33, and this is The held data is simultaneously supplied to the circuits at the respective correlators 3 04b, 304b16. The signal delay circuit 304a is composed of D-reactor circuits 304a, 304a2, 304a3 ..... 3 04a62, 3 04a63 of the same number (63-50-201122922) as the code length of the spread spectrum code. Composition. However, the D-reciprocator circuits 304a63, 304a62,
3〇4a61..... 3 0 4a3、3 04a2、3 04a丨，係依此順序而被從A / D變換電路33側作串聯連接所構成者。而，此些之D-正 反器電路3(Ma|〜304a63之各個的輸出端子，係被與相鄰接 之其他的D-正反器電路（例如，若是D-正反器電路3 04a63 ’則係爲D-正反器電路3 04a62)、以及各相關器3 041^〜 304bie作連接，從各D -正反器電路304ai〜304a63而來之輸 出訊號，係被輸入至所有的相關器3 041^- 3 041^6處。 PSK解調電路126，係爲用以將藉由送訊部201之PSK 調變電路26 (參考圖21)而作了 PSK調變的展頻碼Ck解調 爲原本之展頻碼匕的電路。如圖22中所示一般，此PSK解 調電路126’係被設置在A/D變換電路33與訊號延遲電路 3 04 a之間’並將藉由A/ D變換電路3 3而作了數位變換的輸 出訊號作PSK解調而輸出至後段之訊號延遲電路3 04a處。 具體而言’係爲將PSK調變訊號解調爲圖19(a)中所示之 調變前的·訊號（展頻碼Ck)者。另外，於此第2實施形態 中’雖係針對將PSK解調電路126設置在相關値算出電路 3 04中的情況（亦即是’對於被變換爲數位訊號後之輸出 訊號作解調的情況）而作了例示說明，但是，本發明係並 不被限定於此構成。由於只要是將身爲輸出訊號之電流訊 號變換成電壓訊號後之訊號，則均能夠進行PSK解調，因 此，此PSK解調電路126，係亦可設置在放大電路32 ( 1/ V 變換電路32a)與A/D變換電路33之間。 -51 - 201122922 而後，藉由此PSK解調電路126而被作了解調之輸出訊 號，係被供給至被作了複數段串聯連接之D-正反器電路 304a1〜 304a63處。以下，將由此63個的D -正反器電路 304ai〜 304a63而來之63碼片的輸出訊號，分別稱爲PS:、 P S 2 ' P S 3.....PS62、PS63° 此63碼片之輸出訊號PSt〜 PS 63，係同時地被供給至 16個的相關器304b|〜304bi6處。各相關器304b|〜304b16 ，係將此63碼片之輸出訊號PS !〜PS63，和從相關値演算 用碼產生電路3 04Cl〜304c16所供給而來之相關値演算用碼 C1P’〜C16P’作相關演算，而算出相關値。亦即是，例如， 相關器34bi，係爲了進行展頻碼C!之相關演算，而從相關 値演算用碼產生電路34Cl來接收63碼片之相關値演算用碼 C1P’（PN,’〜PN63’）之供給，並在每一碼片處而進行輸出 訊號與相關値演算用碼之間的相關演算，而將該相關値供 給至相關値記憶電路3 04d處並使其作記憶。 同樣的，相關器3 04b2〜3 04b16，係進行輸出訊號PSi 〜PS63與相關値演算用碼C2P’〜C16P’之間的相關演算，而 將身爲該演算結果之相關値供給至相關値記憶電路3 04d處 並使其作記憶。如此這般，而針對1 6個的展頻碼之全部， 來個別地進行相關演算，並將相關値記憶在相關値記憶電 路304d中。另外，在圖22之構成中，雖係針對使用與展頻 碼之種類相對應的數量之相關器的情況而作了例示，但是 ，本發明係並不被限定於此。例如，亦可將圖9中所示之 構成適用在相關値算出電路304中，並將相關値算出電路 -52- 201122922 藉由1個的相關器和能夠供給複數之相關値演算用碼的相 關値演算用碼產生電路來構成之，而構成爲藉由時間分割 來對於複數種類之相關値作演算。 如同上述一般，在此第2實施形態中，係將互爲相異 之展頻碼作PSK調變，並將此PSK調變後之展頻碼對於構 成送訊導體群之送訊導體同時作供給（多重送訊），而藉 由所選擇了的複數之受訊導體來同時檢測出指示體之位置 。其結果，在此第2實施形態中，係能夠得到與第1實施形 態相同之效果。 進而，在此第2實施形態中，當將供給至送訊導體處 之展頻碼作PSK調變時，係使用較展頻碼之碼片週期爲更 短之週期的時脈訊號。於此情況，當藉由受訊部而將展頻 碼作了解調時，能夠將解調後的展頻碼之上揚以及下挫時 之訊號遷移的頻度設爲更多。故而，在此第2實施形態中 ’係能夠將指示體之位置檢測的誤差更加縮小。又，藉由 對於展頻碼進行PSK調變’係能夠將雜訊耐性提升。 另外’在此第2實施形態中，雖係針對將被作了 p s K調 變後之展頻碼供給至送訊導體處的情況而作了例示說明， 但是’本發明係並不被限定於此。在第3實施形態中，針 對將展頻碼藉由其他之形態來作調變並作供給的情況作例 示說明。 <3、第3實施形態：使用被作了 FSK調變後之展頻碼的構成 例> -53- 201122922 在第3實施形態中，係對於將供給至送訊導體群1 1處 的展頻碼Ck作FSK( Frequency Shift Keying)調變的構成 例作說明。 〔FSK調變〕 在圖23中，展示展頻碼之FSK調變前後的波形。圖23 (a)，係爲在FSK調變前的展頻碼之波形，圖23(b)， 係爲FSK調變後的展頻碼之波形。 在此第3實施形態中，例如，係針對使用調變前之展 頻碼Ck的時脈週期（碼片週期）之2倍以及4倍的時脈週期 之訊號來進行FSK調變之情況，而進行例示說明。另外， 本發明，係並不被限定於此，調變時之時脈週期與碼片週 期間的比，係可因應於用途而適宜作變更。而，在此第3 實施形態之FSK調變中，係使調變前之展頻碼（圖23(a)) 中的High準位狀態之訊號，與調變前之展頻碼的4倍之週 期訊號相對應，並使Low準位狀態之訊號，與調變前之展 頻碼的2倍之週期訊號相對應，而得到調變訊號（圖2 3 (b) )。以下，在此第3實施形態中，係對於與上述之第2實施 形態相同的而使用63碼片長度之展頻碼，並對於2倍以及4 倍的時脈週期之訊號作切換，而對於此展頻碼來施加FSK 調變並產生FSK調變訊號的情況作例示說明。另外，在此 第3實施形態中之指示體檢測裝置的構成，由於若是與上 述第2實施形態中之指示體檢測裝置2作比較，則除了在展 頻碼供給電路221以及相關値算出電路304係分別成爲展頻 -54- 201122922 碼供給電路2U以及相關値算出電路3 1 4之點以外，係爲完 全相同，因此，針對相同之構成，係附加同樣的符號，並 省略其詳細說明。 首先，參考圖24，針對在此第3實施形態中之展頻碼 供給電路222的構成作說明。如同此圖24中所示一般，展 頻碼供給電路222，係由複數之展頻碼產生電路24以及FSK 調變電路27所構成。此展頻碼產生電路24以及FSK調變電 路27，由於係對於根據相同的時脈而相互同步產生的1 6種 類之展頻碼Ci、C2.....Ci 6分別作FSK調變，因此，係分 別各被設置有1 6個。而，各FSK調變電路27，係分別將各 展頻碼<^〜（：16作FSK調變，並將FSK調變訊號CIF、C2F、 …、C16F供給至送訊導體12處。 接著，參考圖25，針對在此第3實施形態中之相關値 算出電路314的構成作說明。此圖25，係爲對於在第3實施 形態中之相關値算出電路的電路構成、以及此相關値算出 電路和1/ V變換電路以及A/ D變換電路間之連接關係作 展示之圖。 相關値算出電路3 1 4，係由F S K解調電路1 2 7、和訊號 延遲電路3 04a、和16個的相關器3 04b,、3 04b2..... 3 04b16、和與此相關器3 04b !〜3 04b, 6相同數量之相關値演 算用碼產生電路3 04Cl、3 04c2 ..... 3 04c16、以及相關値 記憶電路3 04d所構成。 FSK解調電路127，係爲用以將藉由FSK調變電路27( 參考圖24 )而作了 FSK調變的展頻碼解調爲原本之展頻碼 -55- 201122922 的電路。此FSK解調電路127，係被設置在A/D變換電路 33與訊號延遲電路304a之間，並將藉由A/D變換電路33而 作了數位變換的輸出訊號作FSK解調。具體而言，例如係 爲將被調變爲圖23 ( b )中所示之狀態的訊號，解調爲與 圖23 ( a )中所示之調變前的訊號相同之狀態者。另外， 於此第3實施形態中，雖係針對將FSK解調電路127設置在 相關値算出電路3 1 4中的情況（亦即是，對於被變換爲數 位訊號後之輸出訊號作解調的情況）而作了例示說明，但 是，本發明係並不被限定於此構成。由於只要是將身爲輸 出訊號之電流訊號變換成電壓訊號後之訊號，則均能夠進 行FSK解調，因此，此FSK解調電路127，係亦可設置在放 大電路32與A/D變換電路33之間。 藉由FSK解調電路127而被作了解調的輸出訊號，係被 供給至被作了複數段串聯連接之D-正反器電路3 04ai〜 3〇4a63處，從各D-正反器電路3 04ai〜 3 04a63而來之輸出訊 號，係被輸入至全部的相關器3041^- 3041^6處》另外，其 他之構成以及處理，由於係爲與上述之第2實施形態的圖 22相同，因此，係附加與圖22相同之號碼，並省略其說明 〇 在此第3實施形態中，係將複數之展頻碼作F S K調變， 並將此FSK調變後之展頻碼對於構成送訊導體群11之複數 的送訊導體1 2同時作供給（多重送訊），而藉由所選擇了 的複數之受訊導體14來同時檢測出指示體之位置。其結果 ，在此第3實施形態中，亦能夠得到與第2實施形態相同之 -56- 201122922 效果。 又，藉由將展頻碼作F s κ調變，能夠將供給至 體群1 1處之訊號的帶域寬幅增廣’而能夠將雜訊耐 <4、第4實施形態：展頻碼之其他供給方法> 另外，在第1實施形態（參考圖4 )中，係針對 構成的情況而作了例示：亦即是，將構成送訊導體 各送訊導體12區分爲由相鄰接之4根的送訊導體Υ| 所成之複數的送訊區塊25，並對於此複數的送訊區 分別供給各展頻碼c 1〜c 16，而後，使各展頻碼C i -供給至構成此送訊區塊25之4根的送訊導體Yn〜γ 其中一根處。然而，本發明，係亦可並不將各展頻 C16供給至預先所制定了的送訊導體12處，而亦可 宜地供給至任意的送訊導體1 2處。 以下，參考圖26〜圖29，對於展頻碼之供給方 形例1〜3作說明。 〔變形例1〕 首先，根據圖26，對於在變形例1中之展頻碼 方法作說明。在此變形例1中，雖並未特別圖示， 例如，係在圖4中所示之送訊導體選擇電路22與展 給電路2 1之間而設置開關。而後，藉由此開關，來 從展頻碼供給電路2 1所供給而來之各展頻碼C ,〜（ 送訊導 性提高 下述之 群1 1之 丨〜Yn + 3 塊25而 - C 1 6 被 ,+ 3中之 碼C，~ 設爲適 法的變 的供給 但是， 頻碼供 設爲將 :16經由 -57- 201122922 此未圖示之開關來選擇性地供給至送訊導體選擇電路22處 之構成。另外，其他之構成，由於係成爲與圖1中所示之 第1實施形態相同之構成，因此，係適宜地參考圖1並將對 於相同構成之說明作省略。 而，送訊導體選擇電路22，係從送訊導體Yi〜Y64中 來以5根的間隔來選擇1 6根之送訊導體1 2。具體而言，送 訊導體選擇電路22，最初係對於送訊導體Υ,、Υ5..... Υ57、Y61作選擇，並供給各展頻碼C16。而後，於此狀 態下，在特定時間之間，而進行展頻碼之供給。 而後，送訊導體選擇電路22，係對於將送訊導體12之 索引標號η朝向增大的方向而橫移了一根的送訊導體12作 選擇。亦即是，係將前一次所選擇了的16根之送訊導體Υ, 、Υ5.....Υ57、Y61分別切換爲送訊導體Υ2、Υ6..... Υ5 8、Υ62。而後，從展頻碼供給電路21所供給而來之各展 頻碼α〜（：16，係分別被同時供給至此新選擇了的送訊導 體Υ2、Υ6.....Υ58、Υ62處。之後，係將上述之送訊導體 12的切換動作依序作反覆進行，而進行展頻碼之供給。 而，若是藉由送訊導體選擇電路22而將各展頻碼（：，〜 C16分別同時地供給至送訊導體Υ4、Υ8.....Υ6〇以及Υ64 處，則係藉由未圖示之開關來對於各展頻碼所被作供給之 送訊區塊25 (參考圖4)作切換，並反覆進行上述動作。 例如，若是對於由送訊導體Υ,〜Υ4所成之送訊區塊25作注 目，則首先，在此送訊區塊2 5處，係被供給有展頻碼C ,， 並從送訊導體起而依序被進行有展頻碼C,之供給。而後 -58- 201122922 ’如同上述一般，送訊導體選擇電路22,係對於展頻碼Ci 所被作供給之送訊導體經時性地作切換。而，在展頻碼C i 被供給至送訊導體Y4處之後，送訊導體選擇電路22，係將 供給展頻碼之送訊導體切換爲丫】，並且，未圖示之開關， 係將供給至送訊區塊25處之展頻碼C,切換爲展頻碼c2，並 反覆進行上述之切換動作。當再度將此展頻碼供給至送訊 導體Y4處之後’送訊導體選擇電路22，係再度將供給展頻 碼之送訊導體切換爲Y!，並且’未圖示之開關，係將展頻 碼C2切換爲展頻碼c3，之後，反覆進行上述動作。 另外’在此變形例1所示之例中，雖係針對使送訊導 體選擇電路22在每一特定時間中而將所連接之送訊導體12 朝向使其之索引標號η增大的方向來作切換之例子，而作 了說明’但是，本發明，係並不被限定於此。例如，亦可 將被連接於展頻碼供給電路21處之送訊導體12，朝向使其 之索引標號η減少的方向來作切換。進而，亦可將送訊導 體12依據特定之序列（sequence )來隨機地作選擇。又， 在至此爲止的說明中，係針對送訊導體1 2之切換而作了說 明，但是，針對受訊導體1 4，係亦可設爲根據特定之序列 來隨機性地作切換。 〔變形例2〕 在上述變形例1中，係對於：送訊導體選擇電路22, 係在每特定時間處，而從送訊導體Y,〜Y64之中來以5根間 隔而選擇16根之送訊導體12，並將此被選擇了的送訊導體 -59- 201122922 1 2 ’朝向使其之索引標號η增加的方式來作切換，並供給 展頻碼C k之例子’而作了展示。然而，供給展頻碼c k之送 訊導體12的選擇，係亦可並不設爲空出有特定之根數間隔 地來作選擇。 參考圖27以及圖28，針對變形例2作說明。首先，根 據圖27，對於在變形例2中之送訊導體選擇電路202的構成 作說明。在此變形例2中，送訊導體群1 1，係被區分爲由 相鄰接之16根的送訊導體Yn〜Yn+15所成的複數之送訊區塊 125。具體而言，由64根的送訊導體Υ,〜Υ64所成之送訊導 體群11，係被區分爲送訊導體Yi〜Y16、Υ17〜Υ32、Υ33〜 Υ48以及Υ49〜Υ64之4個的送訊區塊。 送訊導體選擇電路202，係由甩以將從展頻碼供給電 路21所供給而來之展頻碼（^〜（：16供給至各送訊區塊125處 之開關202a所構成。 此開關202a，係爲由16根的開關所成之開關群，此16 根的開關之各別的輸出端子2 02b，係被與相對應之各送訊 導體Yn〜Yn+15相連接，而各別的輸入端子202c，係被與相 對應之展頻碼供給電路21的各展頻碼產生電路24 (參考圖 1以及圖3 )相連接。而，藉由使此開關202a對於被連接於 展頻碼產生電路24處之送訊區塊125經時性地作切換，而 成爲能夠將各展頻碼C ,〜C , 6供給至全部的送訊導體1 2處 。另外，在此圖27中，係爲了避免成爲複雜，而將開關 2 02 a作省略記載。又，上述以外之其他構成，由於係爲與 第1實施形態（參考圖1等）成爲相同之構成，因此，在相 -60- 201122922 同之構成處，係附加相同之號碼’並省略其說明。 接著，根據圖2 8 ’對於在變形例2中之展頻碼的供給 方法作說明。首先，送訊導體選擇電路202 ’係對於由送 訊導體Y,〜Y16所成之送訊區塊125作選擇（圖28之狀態） 。接著，展頻碼供給電路21，係分別將展頻碼（^〜（：16同 時供給至構成送訊區塊125之各送訊導體Yi〜Yl6處。當在 此狀態下而於特定之時間的期間中而進行了展頻碼C ,〜 〇16之供給後，送訊導體選擇電路202，係將被連接於展頻 碼供給電路21處之送訊區塊125切換爲由送訊導體Υ17〜 Υ32所成之送訊區塊125，並將展頻碼Ci〜C16同時供給至 構成此送訊區塊125之各送訊導體Y17〜Y32處。之後，送 訊導體選擇電路202，係反覆進行此對於送訊區塊125作切 換之動作和將各展頻碼C ,〜C i 6同時作供給之動作。而後 ’若是送訊導體選擇電路202對於由送訊導體Y49〜Y64所 成之送訊區塊125作了選擇，並結束了從展頻碼供給電路 21而對於此些之送訊導體Υ49〜γ64所進行的展頻碼(^〜（：16 之供給’則送訊導體選擇電路202，係將被選擇之送訊區 塊回復至由送訊導體Υ,〜Υ16所成之送訊區塊125，並反覆 進行上述之切換動作與展頻碼之供給動作。 〔變形例3〕 在上述變形例2中，雖係針對構成由相鄰接之1 6根的 送訊導體Υπ〜Υη+15所成之送訊區塊125，並對於此送訊區 塊1 2 5來供給展頻碼C 1〜c , 6，且對於此送訊區塊1 2 5作切 -61 - 201122922 換，而將展頻碼（^〜（：16對於構成送訊導體群11之全部的 送訊導體1 2來作供給之情況，而作了例示說明（參考圖27 以及圖28 )’但是，送訊導體12之切換，係並不被限定爲 在每一送訊區塊中而進行的情況。 參考圖2 9，針對變形例3作說明。在此變形例3中，送 訊導體選擇電路，係對於構成送訊導體群11之送訊導體12 中的相鄰接之16根的送訊導體Yn〜Yn+15而供給展頻碼（：,〜 C 16，並且經時性地將此被送訊導體選擇電路202所選擇之 送訊導體Υη〜Υη+15朝向使索引標號η作增加的方向來一次 一根地作切換。具體而言，首先，送訊導體選擇電路2 02 ，例如係對於送訊導體Υ!〜Υ16作選擇（圖29之狀態）。 接著，展頻碼供給電路2 1，係分別將展頻碼C ,〜C , 6同時 供給至此送訊導體處。 在此狀態下，於特定時間之間而進行了展頻碼C ,〜 Ci 6之供給後，送訊導體選擇電路202，係將所選擇之送訊 導體12朝向使其之索引標號η增加的方向而作一根的切換 。亦即是，送訊導體選擇電路2〇2 ’係將前一次所選擇了 的16根之送訊導體Υ,-Υίδ切換爲送訊導體Υ2〜Υ17。而後 ，展頻碼供給電路2 1 ’係將展頻碼C !〜C , 6分別同時供給 至此新選擇了的送訊導體γ2〜γη處。之後’送訊導體選 擇電路2 02，係將上述之切換動作依序作反覆進行，而進 行展頻碼C,〜C16之供給》 另外，在變形例2以及3中’雖係針對使送訊導體選擇 電路2 0 2在每一特定時間中而將被連接於展頻碼供給電路 -62- 201122922 21處之送訊導體12朝向使其之索引標號n增加的方向來作 切換之例子，而作了說明，但是，本發明，係並不被限定 於此。亦可在每特定時間中，將被連接於展頻碼供給電路 21處之送訊導體12，朝向使其之索引標號n減少的方向來 作切換。進而，亦可將送訊導體1 2依據特定之序列來隨機 地作選擇。 <5、第5實施形態：受訊導體之選擇方法> 在上述第1實施形態中，係針對將受訊導體群1 3區分 爲檢測區塊3 6，而受訊導體選擇電路2 2係在每特定時間中 而對於檢測區塊3 6中之1根的受訊導體1 4作選擇的情況， 而作了例示說明（參考圖6 )，但是，本發明係並不被限 定於此。例如，亦可設爲在每一檢測區塊3 6中而整批地進 行相關演算，並在特定時間後，將檢測區塊切換爲其他的 檢測區塊，並進行相關演算。 〔變形例4〕 參考圖3 0以及圖3 1，針對變形例4作詳細說明。於此 ，圖3 0，係爲此變形例4中之受訊導體選擇電路以及放大 電路的電路構成圖。在此變形例4中，受訊導體群1 3，係 被區分爲由相鄰接之16根的送訊導體乂^〜Xm+15所成的複 數之檢測區塊1 36。具體而言，受訊導體群1 3，係被區分 爲受訊導體Xl〜Xl6、Xl7〜X32、X33〜X48、…、X|"〜 Xi28之8個的檢測區塊136。 -63- 201122922 受訊導體選擇電路131，係如圖30中所示一般，以由 1 6根之邏輯開關所成之開關1 3 1 a所構成。此1 6根的開關之 各別的輸出端子131c，係被與構成放大電路32之各I/V變 換電路32a相連接。而，開關131a之各輸入端子131b，係 被與相對應之受訊導體14相連接。另外，其他之構成，由 於係成爲與圖1中所示之第1實施形態（參考圖1以及圖6 ) 相同之構成，因此，針對相同之構成，係附加相同的號碼 ，並省略其說明。 接下來，參考圖31，對受訊導體選擇電路131之動作 作詳細說明。受訊導體選擇電路1 3 1，係選擇特定之檢測 區塊136，例如，最初係選擇由受訊導體X!〜乂16所成之檢 測區塊136 (圖31之狀態）。而後，相關値算出電路34， 係針對從構成此被選擇了的檢測區塊136之全部的受訊導 體X!〜Xl6所輸出之輸出訊號，而進行相關演算，並且， 將身爲此相關演算之結果的相關値，記憶在相關値記憶電 路34d (參考圖8 )中。 接著，在特定時間之後，受訊導體選擇電路131，係 將所選擇之檢測區塊136切換爲由受訊導體父|7〜\32所成 之檢測區塊1 3 6。而後，相關値算出電路3 4，係針對從構 成此新被選擇了的檢測區塊136之全部的受訊導體χ17〜 Χ3 2所輸出之輸出訊號，而進行相關演算，並且將相關値 記憶在相關値記憶電路34d中。之後，若是在每特定時間 處而反覆進行上述之切換動作，並結束了針對從由受訊導 體x113〜x128所成之檢測區塊136而來之輸出訊號的相關演 -64- 201122922 算與相關値的記憶，則係回到當初之由受訊導體χ 1〜X16 所成之檢測區塊1 3 6，之後，係進行相同的切換以及相關 演算。 <6、第6實施形態：感測部之其他構成例> 另外，在上述第1實施形態中，係針對如圖2中所示一 般的在第1基板15之其中一方的表面上而將受訊導體Μ與 送訊導體1 2隔著間隔物1 6來對向設置的感測部1 〇〇而作了 例示說明，但是，本發明係並不被限定於此。例如’亦可 將受訊導體14與送訊導體12分別形成在一枚之玻璃基板的 兩面處。以下，根據圖3 2，針對感測部之其他構成例作說 明。 〔變形例5〕 圖32，係爲此變形例5之感測部500的槪略剖面圖。此 感測部500，係具備有：例如被形成爲略平板狀且例如由 玻璃所成之基板501、和被形成在此基板501之其中一方的 表面（經由手指等的指示體1 9而被作指示之側的面）上的 複數之受訊導體514、和被形成在基板501之另外一方的表 面（圖32中之下側的面）上之複數的送訊導體512。 送訊導體5 1 2之表面，係經由以將基板5 0 1之其中一方 的表面全體作覆蓋的方式而形成了的第1保護層513而被作 了覆蓋。同樣的，受訊導體5 1 4，係經由以將基板5 0 1之另 外一面全體作覆蓋的方式而形成了的第2保護層5 1 5而被作 -65- 201122922 了覆蓋，此第2保護層515,係更進而被略平板狀之保護薄 片516所覆蓋。此保護薄片516’係爲爲了不會使受訊導體 5 1 4由於直接與指示體1 9相接觸而受到損傷等，而進行保 護者。 另外，在此變形例5中，基板501、送訊導體512以及 受訊導體514，係可藉由與上述第1實施形態相同的形成材 料而形成之。亦即是’在此變形例5中，係與第1實施形態 相同的’在基板5 0 1處，除了具備有透過性之週知的玻璃 基板以外’係亦可使用由合成樹脂所形成的薄片狀（薄膜 狀）基材。進而，第1保護層513以及第2保護層515，例如 ，係可藉由Si02膜或是合成樹脂膜等而形成之，在保護薄 片5 1 6處，例如係可使用由合成樹脂等所成之薄片構件。 又’在此變形例5中，雖係針對使第1保護層5 1 3 '第2保護 層5 1 5以及保護薄片5 1 6在基板5 0 1之兩面處而分別以將全 面作覆蓋的方式來作了形成的情況而作了例示，但是，本 發明係並不被限定於此。例如，保護薄片5 1 6，由於係只 要以不會使指示體19與受訊導體51 4直接作接觸的方式來 形成，便能夠達到其目的，因此，亦可將其之形狀形成爲 與受訊導體514之形狀略相同之形狀。 在此變形例5中所示之感測部5 00，相較於上述第1實 施形態（參考圖2 )的感測部1 00，由於係能夠將基板之枚 數減少，因此，係能夠將感測部之厚度設爲更薄。又，在 此變形例5之感測部5 00中，由於係能夠將基板之枚數減少 ，因此，係能夠提供更爲低價之感測部。 -66 - 201122922 〔變形例6〕 接下來’根據圖3 3，針對感測部之其他變 。在此變形例6中，例如，係針對在基板之其 形成送訊導體以及受訊導體之感測部的構成例 此，圖3 3 ( a )，係爲對於此變形例6之感測部 圖作展示，圖3 3 ( b )，係爲對於此變形例6之 體圖作展示。另外，在此圖33中，保護層以及 記載，係作省略。 此變形例6之感測部600，係如圖33 ( a ) ，具備有基板601、和以特定之圖案而被形成名 之其中一面上並具備有導電性之金屬層602、 此金屬層602上之絕緣層603、和複數之送訊_ 及複數之受訊導體6 1 4。而，在此變形例6中 601之其中一面上，具備有使送訊導體612與旁 相交叉的構造，在此送訊導體6 1 2與受訊導體6 場所處，係中介存在有用以將該些相互作電性 層 6 0 3 〇 金屬層602，係如圖33 ( b )中所示一般， 朝向與受訊導體6 1 4所延伸之方向相交叉的方 體6 1 2所延伸之方向）而作延伸並形成之略線 絕緣層6 0 3，係以將此金屬層6 0 2之一部分作覆 被形成。在此金屬層602之延伸方向的兩端處 有送訊導體612，被設置在此金屬層6 02之延伸 形例作說明 中一面上而 作說明。於 的槪略剖面 感測部的立 保護薄片之 中所示一般 E此基板601 和被形成在 裏體6 1 2、以 ，係在基板 色訊導體6 1 4 1 4相交叉的 絕緣之絕緣 例如，係爲 向（送訊導 狀的金屬。 蓋的方式而 ，係被設置 方向的兩端 -67- 201122922 處之各送訊導體61 2彼此，係藉由此金屬層602而被作電性 連接。而’受訊導體614，係被形成在絕緣層603上，並被 與金屬層602以及送訊導體614相互作電性絕緣。另外，送 訊導體612以及受訊導體614之配置，係亦可爲相反。又， 在此變形例6中，雖係在指示體1 9爲了進行位置指示而接 近基板601之其中一面上而配置有送訊導體612與受訊導體 61 4等，但是，亦可設爲在對向於此基板601之其中一面的 另外一面上，而配置送訊導體61 2與受訊導體61 4等。 進而，在此變形例6中，基板601、送訊導體612以及 受訊導體614，係可藉由與上述第1實施形態相同的材料而 形成之。亦即是，與第1實施形態相同的，基板60 1，除了 具備有透過性之週知的玻璃基板以外，係亦可使用由合成 樹脂所形成的薄片狀（薄膜狀）基材。 又，金屬層602，係可藉由具有高導電率之金屬材料 、例如藉由Mo (鉬）等來形成之。金屬層6〇2與送訊導體 6 1 2之間的接觸面積，由於係爲微小，因此，爲了將此些 之電阻縮小，係以在金屬層602中使用具有高導電率之金 屬材料爲理想。又，絕緣層603，例如，係可藉由抗蝕劑 等來形成之。 此變形例6之感測部600，相較於上述第1實施形態（ 圖2 )的感測部1 00，由於係能夠將玻璃基板之枚數減少， 因此，係能夠將感測部600之厚度設爲更薄。又，在此變 形例6之感測部600中，由於係能夠將基板之枚數減少，並 將送訊導體612以及受訊導體614實質性地藉由1層來構成 -68- 201122922 ，因此，係能夠提供更爲低價之感測部。 進而，此變形例6之感測部600中，當在對向於指示體 19爲了進行位置指示而接近基板601之其中一面的另外一 面上，而配置有送訊導體612與受訊導體614等的情況時， 由於係成爲在指示體與此些之導體間而中介存在有基板 60 1，因此，相較於變形例5之感測部5 00的情況，指示體 與各導體間之距離係變廣，從指示體而來之雜訊的影響係 被降低。 〔變形例7〕 在上述第1〜3實施形態以及變形例1〜6中，雖係針對 將送訊導體藉由在特定方向上而延伸之直線狀的導體而作 了形成的情況來作例示說明，但是，在此變形例7中，係 對於關於送訊導體之形狀的其他構成例作說明。 根據圖34，針對此變形例7作說明。於此，圖34 ( a ) 中，係爲對於在此變形例7之感測部處的送訊導體以及受 訊導體之槪略構成作展示，於圖34(b)中，係爲送訊導 體之島狀導體部的擴大圖。 在此變形例7中’如圖34 (a)中所示一般，受訊導體 7 1 4係藉由一定寬幅之直線形狀的導體而被形成。送訊導 體712，係具備有將在與受訊導體714所延伸之方向相正交 的方向上而延伸形成之線形狀的導體部722和寬幅爲較此 導體部722更廣之島狀導體部72 3作了電性連接之構成。而 後，至少受訊導體7 1 4與導體部722間之交叉點，係藉由使 -69- 201122922 絕緣層（未圖示）作中介存在，而相互被作電性絕緣。 如圖34 ( b )中所示一般，島狀導體部723，係由被形 成爲略相同形狀之第1以及第2島部723b、723c，和將此第 1以及第2島部723b、723 c彼此作電性連接之略直線狀的連 接部723d所構成《第1及第2島部723b、723c，係被形成爲 具備有頂部723 a之略三角形狀，並在該頂部723 a處而與導 體部722作電性連接。而，第1島部723b與第2島部723 c， 係在與頂部723a相對向之底部723e處，藉由連接部73d而 被作電性連接。 另外，在此圖34中，雖係針對使受訊導體714之延伸 方向與送訊導體712之延伸方向相正交的例子而作了展示 ，但是，本發明係並不被限定於此。兩導體之延伸方向， 係並非一定需要正交，只要以能夠產生用以進行位置檢測 之交叉點的方式，來使送訊導體712之延伸方向與受訊導 體714之延伸方向相交叉即可。 若是如同上述一般而形成島狀導體部723，則如圖34 (b)中所示一般，在島狀導體部723處，係沿著受訊導體 714之延伸存在方向而被形成有凹部723f。 藉由將送訊導體712之形狀設爲如同上述一般之形狀 ，能夠將交叉點近旁之送訊導體的面積增大。其結果，當 指示體接近感測部700時，從送訊導體712所發出之電場係 會更多量地在指示體處收斂，因此，係能夠使檢測感度提 升。 又，當藉由將適用有本發明之指示體檢測裝置和採用 -70- 201122922 有電磁感應方式（EMR: Electro Magnetic Resonance)之 指示體檢測裝置作重疊設置而構成將檢測出指示體之區域 作了共通化的輸入裝置的情況時，由於從電磁感應方式之 位置檢測裝置所發出之電場，在島狀導體部723處係會產 生渦電流，而此渦電流會對於電磁感應方式之位置檢測造 成不良影響（渦電流損失）。.相對於此，藉由如同此變形 例7—般地而在位置於交叉點近旁之島狀導體部723處形成 凹部723 f，就算是在將適用有本發明之指示體檢測裝置和 採用有電磁感應方式之指示體檢測裝置作重疊設置的情況 時，亦能夠藉由島狀導體部723而對於渦電流的產生作抑 制’而能夠消除上述一般之問題。 另外’此變形例7之構成，係並不被限定於交叉點靜 電耦合方式之指示體檢測裝置的感測部中，而亦可適用在 具備有與交叉點靜電耦合方式相同之導電圖案的投影型靜 電耦合方式的指示體檢測裝置中。亦即是，係亦可適用在 :具備有由被配置在第1方向上之複數的第1導體、和被配 置在相對於第1方向而相交叉的方向上之複數的第2導體所 成之導體圖案，且根據從被配設在各方向上之各個的導體 處所得到了的檢測訊號，來將在被配設於各方向上之導體 處的與指示位置相對應了之各個的導體特定出來，並從所 配設之位置被作了特定的該些之導體的各個所相交叉之位 置’來求取出指示體所指示之位置的投影型靜電耦合方式 之指示體檢測裝置的感測部等之中。 又’此變形例7之送訊導體712以及受訊導體714的構 -71 - 201122922 成，係亦可對於在第1實施形態（圖2 )、變形例5 (圖3 2 )以及變形例6 (圖3 3 )中所說明了的感測部作適用。進 而，當將指示體檢測裝置與液晶面板等之顯示裝置作了一 體化構成的情況時，爲了對於從起因於液晶面板之像素掃 描的訊號所受到之影響作抑制，較理想，受訊導體7 1 4係 將其延伸方向配置與液晶面板之像素掃描方向相交叉的方 向上。 〔變形例8〕 送訊導體之島狀導體部的形狀，係並不被限定於圖34 中所示之例。於圖35中，展示島狀導體部之形狀的其他構 成例（變形例8 )。在此變形例8之感測部800處的送訊導 體812，係與變形例7相同的，由導體部822與島狀導體部 823所構成。其與變形例7間之相異點，係在於：變形例7 中所示之島狀導體部723的第1及第2島部723b、723c，係 被形成爲略三角形狀，相對於此，在此變形例8中所示之 島狀導體部823的第1及第2島部823b、823c，係被形成爲 略梯形狀。而，在變形例8中，係在身爲與變形例7之第1 及第2島部723 b、723 c的頂部723 a相當之部分的上底部 823 a處，被與導體部822作電性連接。關於其他部分，由 於係與圖3 4中所示之變形例7共通，因此，係附加與圖3 4 相同之號碼，並省略其詳細說明。但是，在圖3 4與圖3 5中 ’就算是相同之部分’號碼之開頭的位置亦係設爲相異之 號碼，在圖3 4之變形例7中，係設爲7開頭，在圖3 5之變形 -72- 201122922 例8中，係設爲8開頭。 若是將此變形例8與變形例7作比較，則在此變形例8 之送訊導體812的島狀導體部823處，由於係爲並不存在有 島狀導體部823之頂部823a (不存在有銳角）的形狀，因 此，相較於導體部8 2 2，電流之流路係變廣。 其結果，在島狀導體部8 23與線形狀之導體部822間的 連接部分處，係難以發生電流之集中，而電流係擴散。亦 即是，由於在成爲島狀導體部823之兩端的上底部823a-823 a之間，電流係擴散流動，因此，此上底部8 2 3 a- 8 2 3 a間 之電阻値係不會變高。藉由具備有此種構造，相較於變形 例7，係能夠將島狀導體部823與導體部82 2之間的電流之 流路確保爲更廣。其結果，相較於變形例7，係能夠將電 傳導特性更進而提升。另外，此上底部8 2 3 a之形狀，係以 並不存在有銳角之部分爲理想，除了上述形狀之外，例如 亦可形成爲曲面狀。又，此變形例8之感測部800的送訊導 體812，雖係如同圖35中所示一般，而對於在島狀導體部 823處形成了 2個的凹部8 23 f之情況而作了圖示，但是，此 凹部823 f，係並不被限定於形成2個，例如，亦可僅形成1 個，或者是形成3個以上。 另外’此變形例8之構成，係並不被限定於交叉點靜 電耦合方式之指示體檢測裝置的感測部中，而亦可適用在 投影型靜電耦合方式的指示體檢測裝置之感測部等處。又 ’於此變形例8中，雖係針對僅將送訊導體藉由線形狀之 導體部與在其之中央部具備有凹部之島狀導體部來構成之 -73- 201122922 例子而作了說明，但是，亦可將受訊導體設爲與送訊導體 相同之構成。 又，此變形例8之送訊導體812以及受訊導體814的構 成，係可對於在第1實施形態（圖2 )、變形例5 (圖32 ) 以及變形例6 (圖3 3 )中所說明了的感測部作適用。進而 ，當將指示體檢測裝置與液晶面板等之顯示裝置作了一體 化構成的情況時，爲了對於從液晶面板所受到之影響作抑 制，如同已述一般，較理想，係將受訊導體7 1 4配置在與 液晶面板之像素掃描方向相交叉的方向上。 〔變形例9〕 另外，在採用了交叉點靜電耦合方式的指示體檢測裝 置中，通常，當從對於指示體作操作之面側（亦即是上方 )來對於感測部作了觀察的情況時，複數之受訊導體與送 訊導體係相交叉，並有著存在有導體圖案之區域與不存在 有導體圖案之區域。各導體，雖係藉由ITO膜等之透明電 極膜而被形成，但是，存在有導體圖案之區域的透過率， 相較於不存在有導體圖案之區域的透過率，係會降低。其 結果，在感測部上，係會產生透過率之不均。依存於使用 者個人差，亦會有對於此透過率之不均有所在意的情況。 因此，在變形例9中，係對於用以消除此種在感測部上之 透過率的不均之構成作說明。 於圖3 6中，展示此變形例9之感測部的槪略構成。另 外，於此，係針對適用在變形例5 (圖32 )之感測部5 00處 -74- 201122922 的例子而作說明。於此變形例9之感測部5 1 0中，在不存在 有送訊導體5 1 2以及受訊導體5 1 4的區域中，係設置例如由 與導體相同之材料所成的第1透明電極膜517以及第2透明 電極膜518»上述以外之構成，由於係爲與變形例5 (圖32 )之感測部500成爲相同之構成，因此，在相同之構成處 ，係附加相同之號碼，並省略其說明。 於圖37 (a)中，對於感測部510之被形成在基板的其 中一面（下面）處之送訊導體512以及第1透明電極膜517 的構成作展示。於此變形例9中，係在與送訊導體5 1 2相同 之面上，而於相互被配置在近旁之2個的送訊導體512之間 來配置矩形狀的第1透明電極膜5 1 7。此第1透明電極膜5 1 7 ’係爲了不會與送訊導體512相接觸，而具備有相較於送 訊導體512間之尺寸而若干小的尺寸，其與送訊導體512之 間’係隔著若干的空隙而相互分離。另一方面，關於第1 透明電極膜517之在送訊導體512的延伸方向上之尺寸，係 被設定爲相較於在相互被配置在近旁之受訊導體5 1 4間的 尺寸上而加算了 1根的受訊導體514之導體寬幅之後的尺寸 而更若千小，並具備有在相互位置在近旁之2根的受訊導 體514之間而一直延伸至各個的受訊導體514之導體寬幅的 略1 / 2之位置處的位置關係地而被作配置。 又，於圖3 7 ( b )中，對於感測部5 1 0之被形成在基板 的另外一面（上面）處之受訊導體514以及第2透明電極膜 518的構成作展示。於此變形例9中，第2透明電極膜518, 係被配置在與受訊導體5 1 4所被配置之面相同的面上，關 -75- 201122922 於其之尺寸，係可適用與對於第1透明電極膜517之尺寸作 規定的情況時相同之途徑來決定之。亦即是，第2透明電 極膜518，係爲了不會與受訊導體514相接觸，而具備有相 較於受訊導體514間之尺寸而若干小的尺寸’其與受訊導 體514之間，係隔著若干的空隙而相互分離。另一方面， 關於第2透明電極膜518之在受訊導體514的長度方向上之 尺寸，係被設定爲將相互在近旁而被作配置之送訊導體 512作部分性的覆蓋。關於第1透明電極膜517以及第2透明 電極膜5 1 8的尺寸以及配置，例如當從對於指示體作操作 之面側（上方側）來觀察感測部5 1 0時，係成爲使送訊導 體512、受訊導體514、第1透明電極膜517、第2透明電極 膜518的重疊關係，在維持電性絕緣的同時，亦能夠盡可 能地成爲均質的方式來作設定並作配置，而成爲能夠對於 感測部510全體來將透過率之不均作抑制並保持均質的光 學特性。 若是將感測部510之被形成在基板的各面上之導體以 及透明電極膜分別如同圖3 7 ( a )以及（b )—般地來作配 置，則當從上方來對於感測部5 1 〇作觀察時，如圖36中所 示一般，在並不存在有導體圖案之區域處，亦係被形成有 由與導體相同之材料所成的第1透明電極膜51 7以及第2透 明電極膜5 1 8。其結果，在感測部5 1 0上之透過率的不均係 被作抑制。 另外，用以對於透過率之不均作抑制的第1透明電極 膜517以及第2透明電極膜518的形狀，係並不被限定於矩 -76- 201122922 形。只要在從上方而對於感測部5 1 0作觀察時’由送訊導 體512以及受訊導體514所成之導體圖案與第1透明電極膜 5 1 7以及第2透明電極膜5 1 8之間的重疊關係成爲光學性均 質即可，第1透明電極膜51 7以及第2透明電極膜518之形狀 ，係關連於由送訊導體512與受訊導體514所成之導體圖案 的形狀而被適宜作決定。例如，在此變形例9中，雖係設 爲將矩形狀之複數的透明電極膜沿著送訊導體512或是受 訊導體5 1 4所延伸之方向而以特定間隔來作配置的例子， 但是，亦可將該複數之透明電極膜作爲1枚的電極膜而形 成之。 又，此變形例9之構成，係亦可對於在第1實施形態（ 圖2 )以及變形例6〜8 (圖3 3〜3 5 )中所說明了的感測部 作適用。進而，例如，亦可另外準備在特定區域處而被形 成有透過率不均防止用之透明電極膜的基板，並將該基板 追加設置於感測部處。又，如同上述一般，亦可採用薄膜 狀之基材。 〔變形例1 〇〕 在上述第1〜3實施形態中，雖係針對將送訊導體以及 受訊導體均形成爲線形狀的情況而作了例示說明，但是， 本發明係並不被限定於此。例如，亦可將送訊導體以及受 訊導體之至少其中一方藉由形成爲曲線狀或者是同心圓狀 的導體來構成之。 以下，參考圖38，針對將複數之送訊導體形成爲直徑 -77- 201122922 互爲相異之圓形狀，並將此配置爲同心圓狀的情況作說明 。此圖3 8，係爲對於在變形例1 〇中之感測部4 0 0的送訊導 體群411與受訊導體群413的配置圖案作展示之圖。於此變 形例1 0中，送訊導體群4 1 1 ’係爲將直徑相異之複數的送 訊導體4 1 2配置爲同心圓狀而構成之。而，被配置爲同心 圓狀之各送訊導體4 1 2，例如，係以使在半徑方向上相鄰 之送訊導體41 2間之間隔成爲等間隔的方式而被作配置。 另一方面，受訊導體群413，例如，係藉由從送訊導 體群4 1 1之中心起而以輻射狀來延伸的直線形狀之複數的 受訊導體41 4而構成之。而，複數之受訊導體414，係在週 方向上而以等間隔來作配置。藉由設爲此種構成，而使送 訊導體412之週方向與受訊導體414之延伸方向上相互交叉 ，並產生交叉點。 圖38中所示之感測部400，例如，當感測部400之位置 檢測區域爲圓形的情況時，係爲合適。另外，於此變形例 10中，雖係針對將構成送訊導體群411之複數的送訊導體 4 1 2以在半徑方向上而成爲等間隔的方式來作了配置的情 況作了例示說明’但是，本發明係並不被限定於此，送訊 導體4 1 2間之間隔，係亦可適宜設定爲所期望之間隔。同 樣的’於此變形例1 〇中，雖係針對將構成受訊導體群4 i 3 之複數的受訊導體414以在送訊導體412之周方向上而作了 等間隔配置的情況作了例示，但是，受訊導體4 1 4間之間 隔’係亦可適宜設定爲所期望之間隔。 又’在上述變形例丨〇中，雖係針對將送訊導體4丨2形 -78- 201122922 成爲略圓形並將受訊導體4 1 4形成爲直線狀的情況而作了 例示說明，但是，本發明係並不被限定於此。例如，亦可 將送訊導體412以及受訊導體414之至少其中一方設爲相對 於其之延伸方向而作蛇行的形狀。 <7、第7實施形態：放大電路之其他構成例> 另外，在上述第1〜3實施形態中，係對於在放大電路 32 (參考圖1)內的放大器處而使用1輸入1輸出之放大器 的例子而作了說明，但是，本發明係並不被限定於此。例 如，代替放大器，係亦可使用差動放大器。以下，參考圖 39〜圖55，針對在放大電路中使用2輸入1輸出或者是4輸 入1輸出之差動放大器的情況（變形例1 1〜1 8 )作說明。 又，當在此放大電路中使用差動放大電路的情況時之受訊 導體群13，係由129根之受訊導體Μ所構成。此些以外之 構成，由於係爲與第1實施形態（圖1 )成爲相同之構成， 因此，關於相同之構成，係附加與圖1相同之號碼，並省 略詳細之說明。 〔變形例1 1〕 參考圖3 9，針對變形例1 1之構成作說明。此圖3 9 ,係 爲在放大電路中使用2輸入1輸出之差動放大器的情況時之 受訊部的槪略構成圖。 首先，受訊導體群13，係被區分爲Ιό個的檢測區塊 2 3 6。此檢測區塊2 3 6，係藉由相鄰接（索引標號m爲連續 -79- 201122922 )之9根的受訊導體xm〜Xm + 8所構成。而，構成各檢測區 塊236之受訊導體Xm〜Xm + 8中的索引標號m最大之受訊導 體Xm + 8 ’係被與相鄰接之其他的檢測區塊23 6作共用。具 體而言’在此變形例1 1中，受訊導體群1 3，係被分割爲檢 測區塊{ X ,〜X 9 } 、{ X 9 〜X , 7 } ..... { X 1 1 3 〜X 1 2 1 }以 及{ Xl21 〜Xl29)。 受訊導體選擇電路23 1，係由與檢測區塊23 6相同數量 之一對的開關2 3 1 a、2 3 1 b所構成。而，此一對之開關2 3 1 a 、231b’係在此兩開關231a、231b處而具備有共通之9個 的輸入端子23 1 c。此輸入端子23 1 c，係分別被與相對應之 受訊導體Xm相連接。一對之開關231a、231b的各別之輸出 端子231d、231e，係分別被與後述之I/v變換電路 23 2a之 輸入端子相連接。而後，此一對之開關2 3 1 a、2 3 1 b，係以 特定之時間間隔，來對於與I/V變換電路232a相連接之受 訊導體14依序作切換。具體而言，最初，若是假設開關 23 la係與受訊導體X!相連接，而開關23 lb係與受訊導體X2 作連接（圖3 9中所示之狀態），則在下一個的特定時間間 隔中，係以使開關23 la與受訊導體X2相連接，並使開關 23 lb與受訊導體X3作連接的方式，來依序作切換並作連接 。之後，係以特定之時間間隔來依序對於被與1/ V變換電 路232a連接的受訊導體Xm作切換，並在開關231a係與受訊 導體X8相連接，而開關23 lb係與受訊導體X9作連接之後， 再度以使開關23 la與受訊導體X,相連接’並使開關23 lb與 受訊導體X2作連接的方式，來作切換並作連接。 -80- 201122922 受訊部310，係如圖39中所示一般，由受訊導體選擇 電路231、和放大電路232、和A/D變換電路33、和相關 値算出電路34、以及位置算出電路35所構成。 放大電路23 2，係由，1/ V變換電路23 2 a、和差動放 大器2 50、以及切換開關23 2d所構成。1/ V變換電路23 2a ，係被設置有與開關231a、23 lb之總數相同數量個，亦即 是被設置有32個，其之輸入端子231c，係分別被與相對應 之各受訊導體14作連接，一對之開關231a、23 lb的各別之 輸出端子23 1 d、23 1 e，係分別被與相對應之1/ V變換電路 232a相連接。而，被與一對之開關231a、23 lb中的開關 23 la相連接了的1/ V變換電路23 2a之輸出端子，係被連接 於差動放大器250之極性爲「-」的輸入端子處，被與開關 23 lb相連接了的1/ V變換電路23 2a之輸出端子，係被連接 於差動放大器25 0之極性爲「+」的輸入端子處。 差動放大器250，係爲2輸入1輸出之差動放大器。此 差動放大器2 5 0，係將從被連接於兩輸入端子處之I / V變 換電路23 2a而來的輸出訊號作差動放大並作輸出。從此差 動放大器250所輸出之輸出訊號，係在未圖示之放大器處 而被放大爲特定之訊號準位，之後，係經由切換開關232d 而被輸出至A/D變換電路33處。 藉由設爲上述一般之構成，在從各受訊導體14而來之 輸出訊號處而重疊了的雜訊，由於係在放大電路232之差 動放大器250處，藉由差動放大而被除去，因此，係能夠 使指示體檢測裝置之雜訊耐性提升。 -81 - 201122922 〔變形例1 2〕 在上述變形例11中，雖係針對使經由1 / V變換電路 23 2a而被連接於差動放大器25〇的各個之輸入端子處的受 訊導體1 4之根數成爲1根的情況而作了例示說明’但是’ 被連接於差動放大器之各輸入端子處的受訊導體14之根數 ，係亦可設爲複數根。於圖40中，展示其中一例。 圖40，係爲此變形例12之放大電路的槪略構成。於此 圖40中，雖並未特別圖示，但是，在變形例1 1中，雖然受 訊導體選擇電路231係藉由設置複數對之對於2根的受訊導 體14作選擇的一對之開關231a、231b而被構成（參考圖39 )，但是，在此變形例1 2中，代替此一對之開關23 1 a、 2 3 1 b，係設置5個開關，並構成爲藉由此5個開關來適宜地 將相鄰接之5根的受訊導體Xm.2〜Xm + 2分別與差動放大器 3 5 0之輸入端子相連接。 受訊導體選擇電路23 1 (參考圖39 )，例如，係將相 鄰接之任意的5根之受訊導體Xm-2〜Xm + 2中的位置在兩側 處之4根的Xm-2、Xm-I以及Xm+l、Xm + 2與差動放大器350之 任一者的輸入端子作連接。另外，在此變形例1 2中，亦同 樣的，從藉由受訊導體選擇電路231而被作了選擇之受訊 導體Xm-2〜Xm + 2而來之輸出訊號，係在ΐ/v變換電路23 2a 處而被變換爲電壓訊號，並被供給至差動放大器350之各 輸入端子處，但是，由於係成爲與圖3 9中所示之變形例1 1 相同之構成，因此，爲了避免圖面變得複雜，在圖40中， -82- 201122922 係將受訊導體選擇電路23 1以及1/ V變換電路2 3 2 a的記載 省略。 具體而言，係將被此受訊導體選擇電路231所選擇了 的5根之受訊導體Xm_2〜Xm + 2中之受訊導體Xm_2以及Xd與 差動放大器3 5 0之極性爲「-」的輸入端子相連接，而將受 訊導體Xm + 2以及Xm+1與差動放大器3 50之極性爲「+」的輸 入端子相連接。而，位置在中央之受訊導體Xm，係被與接 地相連接。另外，亦可將此位置在中央之受訊導體Χπ，連 接於在差動放大器350之內部而被設定爲特定之參考電壓 準位（例如參考準位或者是供給電壓準位：Vcc )的輸入 端子處。 若是設爲此種構成，則從複數之受訊導體Xm.2〜Xm + 2 而來的輸出訊號，係同時地被輸入至差動放大器350處。 其結果’由於從差動放大器3 5 0所輸出之差動訊號係增加 ’因此，係能夠使檢測感度提升。又，由於同時被連接於 差動放大器3 5 0處之受訊導體1 4的根數係增加，因此，亦 能夠將指示體之檢測區域增廣。進而，於此變形例1 2中’ 由於係在放大電路232 (參考圖39)中使用有差動放大器 3 5 0 ’因此’與變形例1 1相同的，係亦能夠將雜訊耐性提 升。 另外’在此變形例I2中，將位置於中央的受訊導體Xm 設定爲接地或者是特定之參考電壓準位的理由，係如下所 述。如同在上述第1實施形態中所說明了一般，在交叉點 靜電耦合方式之指示體檢測裝置中，係將由於電流經由指 -83- 201122922 示體19而被分流至接地處一事所導致的交叉點處之電流的 變化檢測出來（參考圖13)。然而，若是指示體19並未被 充分地作接地，則在交叉點處之電流的分流係成爲不充分 。於此情況，在交叉點處之電流變化係變小，檢測感度係 降低。 相對於此，若是如同此變形例1 2 —般，而以使連接於 差動放大器350處之複數的受訊導體Xm_2〜Xm + 2中之位置 在中央的受訊導體Xm的電壓準位成爲接地或者是參考電壓 準位（例如，電源電壓準位或者是接地電壓準位）的方式 來作構成，則就算是在指示體1 9並未被充分地作接地的情 況下，藉由使指示體19與受訊導體作接觸，係能夠將電 流的一部份經由指示體以及受訊導體乂>„來作分流。其結果 ，能夠對於上述之感度的降低作抑制。 在變形例1 1以及1 2中，雖係針對藉由在放大電路中使 用差動放大器而使檢測感度作了提升的情況作了例示說明 ，但是，亦可設爲藉由將展頻碼供給至複數之送訊導體處 ，來更進一步地使檢測感度提升。 〔變形例1 3〕 參考圖4 1，針對變形例1 3作說明。於此變形例1 3中， 如圖41 (a)中所示一般’係對於將相同之展頻碼供給至 相鄰接之2根的送訊導體處之例作展示。另外’除了圖41 中所示者以外的構成’由於係成爲與變形例1 1 (參考圖1 、圖39等）相同之構成’因此’針對相同之構成’係將其 -84- 201122922 之說明以及圖示省略。 如圖41中所示一般，藉由構成展頻碼供給電路21之複 數的展頻碼產生電路24所產生了的16種類之展頻碼 C16，係分別被供給至相鄰接的2根之送訊導體12處。具體 而言，展頻碼Ci係被供給至送訊導體Y!以及丫2處，展頻碼 C2係被供給至送訊導體Y5以及Y6處，…，展頻碼C15係被 供給至送訊導體Y57以及Y58處，展頻碼C! 6係被供給至送訊 導體γ61以及Υ62處。而，雖並未特別圖示，但是，藉由使 送訊導體選擇電路22對於被連接於展頻碼產生電路24處之 送訊導體12經時性地作切換，展頻碼Ci〜C16係被供給至 構成送訊導體群11之全部的送訊導體12處" 於此，例如，若是對於未圖示之任意一個的受訊導體 1 4作注目，則若是相同之展頻碼被供給至複數之送訊導體 處，則在該受訊導體1 4處，相較於第1實施形態中之受訊 導體1 4，由於係被供給有2倍之展頻碼，因此，從此任意 一個的受訊導體1 4而來之輸出訊號，亦係成爲2倍。故而 ，係能夠使檢測感度提升。進而，若是將相同之展頻碼同 時地供給至3根以上之送訊導體1 2處，則亦能夠與將相同 的展頻碼同時地作了供給的量成正比的而使在任意一個的 受訊導體1 4處之檢測感度提升。 〔變形例1 4〕 另外，當如同上述變形例1 3 —般（參考圖4 1 )而對於 相鄰之複數的送訊導體1 2供給相同之展頻碼的情況時，較 -85- 201122922 理想’係設爲將從與被供給有相同之展頻碼的送訊導體12 之根數相同數量的受訊導體14而來之輸出訊號作放大的構 成。 參考圖42，針對變形例1 4之槪略構成作說明。此圖42 ’係爲將相同之展頻碼Ck對於相鄰接之2根的送訊導體γη 、Yn+ i作供給的情況時之放大電路的槪略構成圖。另外， 除了圖42中所示者以外的構成，由於係成爲與上述變形例 11相同之構成，因此，爲了避免圖面的複雜化，係將其之 記載以及相關於此些之構成的說明作省略。 當如同上述變形例1 3 —般，而將相同之展頻碼Ck對於 相鄰之2根的送訊導體Yn以及γη+ ,作供給的情況時，在受 訊部3 10之放大電路2 3 2處，係使用具備有與被供給相同之 展頻碼Ck的送訊導體12之根數相同數量並且爲同一極性之 輸入端子的放大器，例如，係使用具備有2個的「+」端子 之2輸入1輸出的放大器360。而，在受訊部310之放大器 360之2個的輸入端子處，係被連接有相鄰之2個的受訊導 體 Xm、Xm+丨。 當如同上述一般地對於相鄰之2根的送訊導體Yn、 Υη+1供給相同之展頻碼Ck，並且將從相鄰之2根的受訊導 體Xm' Xm+1而來之輸出訊號作放大的情況時，不僅是能夠 使從放大電路3 60所輸出之輸出訊號的訊號準位增加，亦 能夠將指示體之檢測範圍增廣。其結果，由於係能夠使在 感測部1 00 (參考圖1 )之全體的檢測中所需要的時間縮短 ，因此，該種實施形態，係適合於使用在位置檢測區域爲 -86- 201122922 大之感測部的情況中。另外，在此變形例 將被同時連接於放大器3 6 0處之受訊導體1 根的情況而作了說明，但是，本發明，係 。例如，亦可設爲將3根以上之受訊導體 種情況中，係能夠更進一步地將在感測音丨 中所需要的時間縮短，並且，係能夠使從 之輸出訊號的訊號準位增加。 另外，若是如同上述一般，而將供給 送訊導體12之根數與被同時作選擇之受訊 爲相同，則係可得到下述一般之優點。以 及圖43作比較參考並作說明。於此，圖43 同之展頻碼Ck供給至2根的送訊導體丫„以 於從任意一個的受訊導體Xm而來之輸出訊 時之最小檢測區域S m i n作展不的槪念圖。 當被供給有相同之展頻碼的送訊導體 受訊導體選擇電路而被同時作選擇的受訊 亦即是被連接於放大器361處的受訊導體 相異的情況時，如圖43中所示一般，在感 檢測區域Smin，係成爲長方形狀，並在感 異性。於此情況，例如，若是檢測出與感 (以下，單純稱作對向面）爲圓形狀的指 體之對向面，係會有並不被檢測爲圓形狀 匱1形狀等之變形了的形狀之情形。相對於 形例14一般，使被供給有相同之展頻碼Ck 1 4中，雖係針對 4的根數設爲了 2 並不被限定於此 1 4作連接。於該 5 1〇〇全體之檢測 放大電路所輸出 相同展頻碼c k之 導體Μ的根數設 下，對於圖42以 ，係爲對於將相 及Υη+1處，並對 號作放大的情況 1 2之根數與藉由 導體14之根數（ 1 4之根數）係爲 測部上之最小的 度分布上產生向 測部相對向之面 示體，則該指示 而是被檢測爲橢 此，當如同此變 的送訊導體12之 -87- 201122922 根數與被連接於放大器361處的受訊導體14之根數爲相同 的情況時，如圖42中所示一般，在感測部上之最小的檢測 區域Smin，係成爲正方形狀，並能夠得到等向性之感度分 布。於此情況，就算是在感測部上被配置有對向面爲圓形 狀之指示體，亦能夠將該指示體之對向面檢測爲圓形狀。 另外，在此變形例1 4中，雖係針對將被供給有相同之 展頻碼Ck的送訊導體12之根數以及被連接於放大器360處 的受訊導體1 4之根數各設爲了 2根的情況而作了例示說明 ，但是，本發明係並不被限定於此。被供給有相同之展頻 碼Ck的送訊導體12之根數以及被連接於放大器360處的受 訊導體14之根數，係亦可爲3根以上。 接著，參考圖44以及圖45，針對在上述變形例14中之 被供給有相同之展頻碼的2根之送訊導體的切換作說明。 另外，在以下之說明中，係適宜參考圖1而作說明。 圖44，係對於被同時供給有展頻碼Ck2 2根的送訊導 體之切換的其中一例作展示。在此圖44 (a)以及（b)中 所示之切換例，假設，首先，係在某一時刻處，將展頻碼 Ck供給至送訊導體¥„以及Yn+1處（圖44(a)之狀態）。而， 在經過了特定時間後，展頻碼Ck係被供給至送訊導體Υη + 2 以及Υη + 3處（圖44(b)之狀態）之後，雖並不特別作圖示， 但是，係依序將被供給有展頻碼Ck之送訊導體12切換爲送 訊導體Yn + 4以及Yn + 5、送訊導體Yn + 6以及Υη + 7·"，而若是 —直供給至了特定之導體處，則係回到最初之送訊導體Υ, 以及γη +丨，之後，反覆進行上述之切換。 -88- 201122922 接者’參考圖45’對於將送訊導體12一次—根地作切 換之其中—例作說明。具體而言，如圖45 ( a )〜（c )中 所不一般，假設，首先’係在某—時刻處，將展頻碼^供 給至送訊導體γη以及γη+ι處（圖45(a)之狀態）。而，在經 過了特定時間後’展頻碼Ck係被供給至送訊導體Υη+|以及 Υη + 2處（圖45(b)之狀態）進而，在經過了特定時間後，展 頻碼Ck係被供給至送訊導體Υη + 2以及Υη + 3處（圖45(c)之狀 態）之後，雖並不特別作圖示，但是，係依序將被供給有 展頻碼ck之送訊導體12切換爲送訊導體八+3以及Υη + 4、送 訊導體Υη + 4以及Υη”…’而若是展頻碼（^被供給至了特定 之導體處’則係回到最初之送訊導體Υη以及γη+ι，之後， 反覆進行上述之切換。亦即是，在圖45(a)〜（c)中所 示之切換例中’係於每一特定時間處，而以特定之根數（ 於此例中係爲2根）單位來對於供給相同之展頻碼c k的送 訊導體12作選擇。而’係以使在前一次之選擇動作中所被 作選擇之複數的送訊導體12中之一部分（於圖45所示之例 中，係爲1根）的送訊導體12在下一次之選擇動作中亦被 作爲複數之送訊導體I2而選擇的方式，來進行控制。 〔變形例1 5〕 在上述變形例1 3以及1 4中，雖係針對對於相鄰之2根 的送訊導體而供給相同之展頻碼，並藉由1個的放大器來 將相鄰之2根的受訊導體之輸出訊號作放大的情況，而作 了例示說明，但是，本發明係並不被限定於此。例如，亦 -89- 201122922 可設爲下述之構成：亦即是，送訊部，係對於以特定根數 間隔而被作了配置的複數根之送訊導體而供給相同之展頻 碼’且受訊部亦同樣的，藉由放大器來將從以特定根數間 隔而被作了配置的複數根之受訊導體所輸出的輸出訊號作 放大。於圖46中，展示其中一例（變形例1 5 )。 在此變形例1 5中，代替在圖3 9中所示之放大電路2 3 2 處所被設置之差動放大器250，在受訊部310之放大電路 232處，係使用具備有與被供給相同之展頻碼（^的送訊導 體I2之根數相同數量並且爲同一極性之輸入端子的放大器 ，例如，係使用具備有2個的「+」端子之2輸入1輸出的放 大器3 6 1。另外，其他之構成，由於係成爲與上述變形例 14相同之構成，因此，係適宜地參考圖1以及圖39來作說 明，並且，針對共通之構成，係省略其說明。 圖46，係模式性地展示有下述情況之構成：亦即是， 在被供給有相同之展頻碼匕的2根之送訊導體之間，係位 置有被與接地作了連接的送訊導體，而受訊部，係藉由1 個的放大器來將從2根的受訊導體而來之輸出訊號作放大 ，在此2根的受訊導體之間，係位置有被與接地作了連接 的受訊導體。具體而言，如圖46中所示一般，送訊導體選 擇電路22 (參考圖1)，係對於任意之2根的送訊導體Yn + 1 以及Υη + 3作選擇。而’送訊部200之展頻碼產生電路2 1， 係對於此被選擇了的2根之送訊導體Υη+1、Υη + 3而供給相同 之展頻碼Ck。同時，送訊導體選擇電路22 ’係將被供給有 此展頻碼Ck之2根的送訊導體Yn+1、Yn + 3以外之送訊導體12 -90- 201122922 (亦即是送訊導體Yn ' Υη + 2以及剩餘之送訊導體 地相連接。 同樣的，受訊部310之受訊導體選擇電路23】 39 )，係將2根的受訊導體Xm、Xm + 2與1個的放〕 輸入端子相連接’放大器361 ’係將從此被連接' 受訊導體Xm、Xm + 2而來的輸出訊號作放大。同時 被與此放大器361相連接了的受訊導體Xm、Xm + 2 訊導體（具體而言’受訊導體Xm+l、Xm + 3以及剩 導體14)與接地相連接。另外，由上述送訊導體 22以及受訊導體選擇電路23 1而分別所致之送訊 及受訊導體14之切換’例如’係與在上述變形例 以及圖4 5 )中所示之切換相同地而進行。 如此這般，在變形例1 5中，由於係與變形例 ，對於複數根之送訊導體12而供給相同之展頻碼 放大器361來將從複數根之受訊導體14而來的輸 加算，因此，能夠將檢測範圍增廣，並能夠使所 訊號準位增加，並且亦能夠使檢測感度提升。又 形例1 5中，由於係能夠將最小之檢測範圍Smin擴 ，當感測部上之位置檢測區域爲大的情況時，係 適。 進而，在此變形例1 5中，係與上述之變形例 ，藉由將供給相同之展頻碼的送訊導體之根數與 選擇的受訊導體之根數設爲相同數量，能夠將在 之最小檢測區域Smin設爲正方形狀。其結果，與 12 )與接 (參考圖 ζ器361之 /的2根之 ，將除了 以外之受 餘之受訊 選擇電路 導體1 2以 1 4 (圖 44 1 3相同的 ，並藉由 出訊號作 檢測出之 ，於此變 廣，因此 爲特別合 1 3相同的 同時被作 感測部上 變形例1 3 -91 - 201122922 相同的，在感測部上之最小檢測區域中，係能夠得到等向 性之感度分布。於此情況’例如就算是在感測部上被配置 有對向面爲圓形狀之指示體’亦能夠將該指示體之對向面 檢測爲圓形狀。 〔變形例1 6〕 另外，由被供給至送訊導體群11處之展頻碼Ck所致的 電流，相較於藉由當將指示體1 9放置在交叉點上時而經由 此指示體1 9所流動至接地處之電流而產生的輸出訊號之變 化量，係爲極大。如上述變形例1 1〜1 5中所示一般，若是 使輸出訊號之訊號準位增加，則雖然檢測感度係會提升， 但是，將輸出訊號之變化量檢測出來的精確度係會下降。 爲了維持此檢測精確度，係有必要將受訊部3 0 0之A/ D變 換電路33的解析力提升（參考圖1)。 但是，若是使此A / D變換電路3 3之解析力提升，則 會產生新的問題’亦即是，A / D變換電路3 3之規模係變 大，而設計係成爲困難。特別是，當將相同之展頻碼供給 至複數之送訊導體12處的情況時，此一問題係會更加顯著 化。 因此，參考圖47〜圖49，針對身爲用以解決上述之課 題的實施形態之變形例16作說明。於此，圖47，係爲此變 形例1 6之槪略構成圖以及從差動放大器所輸出之輸出訊號 的波形圖’圖48’係對於在此變形例16中之送訊導體選擇 電路的內部構成之其中—例作展示的圖，圖49，係爲在此 -92- 201122922 變形例1 6中之受訊導體選擇電路的構成圖。另外，在此變 形例1 6之說明中，係對於當指示體1 9 (同圖中之以實線所 示的指示體19)被放置在送訊導體Yn + 2與Xm+1之間的交叉 點上的情況時之輸出訊號的變化作例示說明。 首先，參考圖47 ( a )，針對此變形例1 6中之槪略構 成作說明。於此，在變形例11與此變形例1 6之間的相異點 ，係在於：在供給展頻碼Ck之展頻碼供給電路2 1與將展頻 碼Ck選擇性地供給至送訊導體群1 1處之送訊導體選擇電路 382之間，係被設置有2個的碼反轉器381，以及，在放大 電路處係使用4輸入1輸出之差動放大器3 8 6，並對於從4根 的受訊導體14而來之輸出訊號作差動放大。其他之構成， 由於係爲與變形例1 1 (參考圖1以及圖39 )成爲相同之構 成，因此，在相同之構成處，係附加相同之號碼，並省略 其說明。另外，在以下之說明中，係將對於展頻碼Ck而作 了反轉後之碼，記載爲反轉碼〔Ck(反轉）〕。 2個的碼反轉器3 8 1，係爲將從展頻碼供給電路2 1所供 給之展頻碼Ck作碼反轉並作輸出者。從展頻碼供給電路2 1 所供給而來之展頻碼Ck、和從碼反轉器3 8 1所輸出之反轉 碼〔Ck(反轉）〕，係經由送訊導體選擇電路3 8 2而被供給至 相鄰之4根的送訊導體γη〜γη + 4處。具體而言，從展頻碼 產生電路2 1所供給而來之展頻碼Ck，係經由送訊導體選擇 電路3 8 2而被供給至2根的送訊導體Yn + 2以及Yn + 3處，並且 ’該展頻碼Ck’係在碼反轉器381處而被碼反轉爲反轉碼 〔Ck(反轉）〕’之後經由送訊導體選擇電路3 8 2而被供給至 -93- 201122922 送訊導體Υη以及丫^+1處。另外，在以下之說明中，此圖47 中所示之展頻碼的供給形態，係將被供給有展頻碼Ck之送 訊導體標記爲「+」，並將被供給有反轉碼〔Ck(反轉）〕 之送訊導體標記爲「-」。亦即是，如同此圖47中所示一 般之訊號的供給形態，係被標記爲「…+ +」。 接下來，參考圖48，對送訊導體選擇電路382之詳細 內容作說明。 送訊導體群1 1，係被區分爲由相鄰接之7根的送訊導 體Yn〜Yn + 6作爲1個群組的16個送訊區塊383。送訊導體選 擇電路382，例如，係爲週知之邏輯電路，並由與各送訊 區塊383的數量同數量（16個）之開關群382 a所構成。各 送訊區塊3 8 3，係成爲將構成該送訊區塊3 8 3之7根的送訊 導體Yn〜Yn + 6中之索引標號η爲最大的3根之送訊導體12與 相鄰之其他的送訊區塊作共有的構成。具體而言，如同此 圖48中所示一般，係成爲將構成各送訊區塊383之送訊導 體Υη~ Υπ + 6中之索引標號η爲最大的3根之送訊導體Υη + 4〜 Υη + 6與相鄰之送訊區塊作共有的構成。 各開關群3 82a，係由4個的開關3 82a,、3 82a2、3 8 2a3 以及3 82a4所構成。各開關群3 82a之輸出側之7個的端子 3 8 2b，係分別被與相對應之送訊導體Yn〜Yn + 6相連接。而 ，在4個的開關3 82ai、3 8 2a2、3 82a3以及3 82a4之中，開關 3 8 2 a >以及3 8 2 a2之輸入端子3 8 2 c，係經由碼反轉器3 8 1而被 與展頻碼供給電路21之各展頻碼產生電路24 (參考圖1以 及圖4)相連接，開關3 8 2a3以及3 8 2 a4之輸入端子3 82c，係 -94- 201122922 被與展頻碼供給電路21之各展頻碼產生電路24相連接 而後’如同此圖4 8中所示一般，例如，被供給有 碼c k以及此展頻碼C k之反轉碼〔c k (反轉）〕的開關群 ，係將展頻碼ck供給至送訊導體Yn + 2以及Yn+3處，並 將反轉碼〔Ck(反轉）〕供給至送訊導體Υη以及Υη+1處 ’在將此展頻碼ck以及反轉碼〔Ck(反轉）〕作了特定 之供給後，對於被與展頻碼供給電路2 1相連接之送訊 12作切換，而將展頻碼（^供給至送訊導體γη + 3以及γ ’並且將反轉碼〔Ck(反轉）〕供給至送訊導體γη+1 Υη + 2處。之後’經時性地對於被與展頻碼供給電路2 1 接之送訊導體作切換，並在將展頻碼Ck供給至送訊 Yn + 5以及Yn + 6處，且將反轉碼〔Ck(反轉）〕供給至送 體Yn + 3以及Yn + 4處之後，再度地將展頻碼匕供給至送 體Υη + 2以及Υη + 3處，並且將反轉碼〔Ck(反轉）〕供給 訊導體γη以及Yn+1處，之後，反覆進行上述動作。如 述一般，而將從展頻碼供給電路2 1所供給而來之展頻 以及其之反轉碼〔Ck(反轉）〕供給至構成送訊導體群 全部的送訊導體12處。 接下來，參考圖47 ( a )以及圖49，針對在變形 中之受訊導體選擇電路3 8 4之詳細內容作說明。 如同圖49中所示一般，受訊導體選擇電路3 84， ，係具備有由4個的開關所成之開關群3 84a。此開 3 84a之輸入端子3 8 4b，係分別被與相對應之受訊導體 連接。又，開關群3 84a之各開關的輸出端子3 84c，係 展頻 3 8 2a 且， 。而 時間 導體 η + 4處 以及 相連 導體 訊導 訊導 至送 同上 碼C )c 11之 例16 例如 關群 14相 被與 -95- 201122922 放大電路385的相對應之一個的Ι/V變換電路385a之輸入 端子相連接。進而，開關群3 84a，係成爲以特定之時間間 隔，來對於與1/V變換電路3 8 5 a相連接之受訊導體14作切 換。而後，從各受訊導體14而來的輸出訊號，係在Ι/V變 換電路385 a處而被變換爲電壓訊號，並被輸入至後述之差 動放大器386中。另外，在圖49中，爲了避免圖面的複雜 化，係將複數之1/V變換電路3 85a以及開關群3 84a的記載 省略。 放大電路385，係由4個的Ι/V變換電路385 a和差動放 大器3 86所構成。如圖49中所示一般，1/ V變換電路3 8 5a ，係將其之輸入端子與構成開關群3 84a之各開關的輸出端 子3 84c相連接，而其之輸出端子，係被與後述之差動放大 器3 8 6的各輸入端子作連接。 差動放大器386，係爲4輸入1輸出之差動放大器。此 差動放大器386，係被設置在Ι/V變換電路385a與A/D變 換電路33(參考圖1)之間，其之4個的輸入端子中，左側 之2個的輸入端子之極性係成爲「+」，而右側之2個的輸 入端子之極性係成爲「-」。亦即是，在藉由受訊導體選 擇電路3 84而被作了選擇之4根的受訊導體X,n〜Xm + 3中，索 引標號m爲小之2根的受訊導體Xm以及Xm+1所被作連接之 輸入端子的極性係被設定爲「+」，而索引標號m爲大之2 根的受訊導體Xm + 2以及Xm + 3所被作連接之輸入端子的極性 係被設定爲「-」。而後，差動放大器3 86，係將在Ι/V變 換電路3 8 5 a處而被變換爲電壓訊號後之輸出訊號作差動放 -96 - 201122922 大並作輸出。 而，受訊導體選擇電路3 84，係進行與變形例4 (參考 圖31)相同之選擇切換。具體而言’首先’此受訊導體選 擇電路3 84之開關群3 84a，係從最小索引標號之受訊導體 X!〜X4起，而依序將受訊導體Xm〜Xm + 3與差動放大器386 之「+」端子以及「-」端子作連接（圖4 9之狀態）。亦即 是，將差動放大器386之2個的「+」端子分別與受訊導體 Xi以及X2作連接，並將2個的「-」端子分別與受訊導體X3 以及x4作連接。接著，若是經過特定之時間，則受訊導體 選擇電路384之開關群384a，係將被連接於放大電路386處 之受訊導體14，切換爲位置在使其索引標號m增加之方向 上的受訊導體，亦即是，將受訊導體以及X3與差動放大 器386之「+」端子作連接，並且將受訊導體X4以及X5與差 動放大器3 8 6之「-」端子作連接。而，在此切換後，從被 連接於開關群3 82a處之受訊導體X2〜X5而得到新的輸出訊 號。之後，受訊導體選擇電路3 84之開關群3 84a，係以特 定之時間間隔，而依序對於被連接於差動放大器3 86處之 受訊導體14作切換，並在將身爲最後被作連接之4根的受 訊導體X128〜Xl31與差動放大器3 86作了連接後，再度回到 最初之狀態、亦即是回到此圖49中所示之狀態，之後，反 覆進行上述動作。3〇4a61..... 3 0 4a3, 3 04a2, 3 04a丨, which are connected in series from the A/D conversion circuit 33 side in this order. However, the output terminals of the D-reactor circuits 3 (Ma|~304a63) are connected to other adjacent D-reactor circuits (for example, if the D-reciprocator circuit 3 04a63) 'The D-reciprocator circuit 3 04a62'), and the correlators 3 041^~ 304bie are connected, and the output signals from the D-reverse circuit circuits 304ai~304a63 are input to all relevant The PSK demodulation circuit 126 is a spreading code for PSK modulation by the PSK modulation circuit 26 (refer to FIG. 21) of the transmitting unit 201. Ck is demodulated into a circuit of the original spread spectrum code. As shown in Fig. 22, the PSK demodulation circuit 126' is disposed between the A/D conversion circuit 33 and the signal delay circuit 384a' and The output signal digitally converted by the A/D conversion circuit 33 is demodulated by PSK and output to the signal delay circuit 310a of the subsequent stage. Specifically, the PSK modulation signal is demodulated into FIG. 19 ( In the second embodiment, the PSK demodulation circuit 126 is provided in the correlation calculation circuit 3 0. The case of 4 (that is, the case where the output signal after being converted into a digital signal is demodulated) is exemplified, but the present invention is not limited to this configuration. The signal after the current signal of the output signal is converted into a voltage signal can be demodulated by PSK. Therefore, the PSK demodulation circuit 126 can also be disposed in the amplifying circuit 32 (1/V conversion circuit 32a) and A/D. Between the conversion circuits 33. -51 - 201122922 Then, the output signals demodulated by the PSK demodulation circuit 126 are supplied to the D-reactor circuits 304a1 to 304a63 which are connected in series in a plurality of stages. In the following, the output signals of 63 chips from the 63 D-reactor circuits 304ai to 304a63 are respectively referred to as PS:, PS 2 'PS 3.....PS62, PS63° 63 The chip output signals PSt~PS 63 are simultaneously supplied to the 16 correlators 304b|~304bi6. Each correlator 304b|~304b16 is the 63 chip output signal PS!~PS63, and Relevant performance from the relevant 値 calculus code generation circuit 3 04Cl~304c16 The correlation calculus is calculated by using the codes C1P' to C16P' as the correlation calculations. That is, for example, the correlator 34bi receives the correlation calculation code generation circuit 34Cl for the correlation calculation of the spread spectrum code C! The correlation of the 63 chips is calculated by the supply of the code C1P' (PN, '~PN63'), and the correlation calculation between the output signal and the associated 値 calculation code is performed at each chip, and the correlation is performed. It is supplied to the relevant memory circuit 3 04d and made to be memorized. Similarly, the correlator 3 04b2 to 3 04b16 performs correlation calculation between the output signals PSi to PS63 and the related calculus codes C2P' to C16P', and supplies the correlation 身 which is the result of the calculation to the relevant memory. Circuit 3 04d is placed and remembered. In this way, the correlation calculation is performed individually for all of the 16 spread codes, and the correlation is stored in the associated memory circuit 304d. Further, in the configuration of Fig. 22, although the number of correlators corresponding to the types of the spreading codes is used, the present invention is not limited thereto. For example, the configuration shown in FIG. 9 can also be applied to the correlation calculation circuit 304, and the correlation calculation circuit-52-201122922 can be supplied with a correlator and a correlation coefficient capable of supplying a plurality of correlations. The 値 calculation is constructed by a code generation circuit, and is configured to perform calculation on the correlation of the plural types by time division. As described above, in the second embodiment, the spread spectrum codes which are mutually different are subjected to PSK modulation, and the spread spectrum code modulated by the PSK is simultaneously made for the transmission conductors constituting the transmission conductor group. Supply (multiple transmission), and the position of the indicator is simultaneously detected by the selected plurality of received conductors. As a result, in the second embodiment, the same effects as those of the first embodiment can be obtained. Further, in the second embodiment, when the spreading code supplied to the transmission conductor is PSK modulated, a clock signal having a shorter chip period than the spread spectrum code is used. In this case, when the spread spectrum code is demodulated by the receiving unit, the frequency of the signal spread after the demodulated spread spectrum code is raised and dropped can be set to be more. Therefore, in the second embodiment, the error in detecting the position of the pointer can be further reduced. Moreover, the noise tolerance can be improved by performing PSK modulation on the spreading code. In addition, in the second embodiment, the case where the spread code obtained by ps K modulation is supplied to the transmission conductor is exemplified, but the present invention is not limited to this. In the third embodiment, a case where the spread spectrum code is modulated and supplied by another form will be exemplified. <3. Third embodiment: Configuration example using a spread spectrum code subjected to FSK modulation> -53- 201122922 In the third embodiment, it is supplied to the transmission conductor group 1 1 The spread code Ck is described as an example of a configuration of FSK (Frequency Shift Keying) modulation. [FSK Modulation] In Fig. 23, the waveforms before and after the FSK modulation of the spread spectrum code are shown. Figure 23 (a) shows the waveform of the spread spectrum code before the FSK modulation, and Figure 23 (b) shows the waveform of the spread spectrum code after the FSK modulation. In the third embodiment, for example, the FSK modulation is performed by using a signal of twice the clock period (chip period) and four times the clock period of the spread code Ck before the modulation. For illustrative purposes. Further, the present invention is not limited thereto, and the ratio of the clock period at the time of modulation to the chip circumference period can be appropriately changed depending on the application. However, in the FSK modulation of the third embodiment, the signal of the High level state in the spread spectrum code before the modulation (Fig. 23(a)) is four times that of the spread spectrum code before the modulation. The period signal corresponds to each other, and the signal of the Low level state corresponds to the period signal of twice the spreading code before the modulation, and the modulation signal is obtained (Fig. 23 (b)). In the third embodiment, the spread code of 63 chips length is used in the same manner as the second embodiment described above, and the signals of the clock cycles of 2 times and 4 times are switched, and This spread code is used to illustrate the case where FSK modulation is applied and the FSK modulation signal is generated. In addition, the configuration of the pointer detecting device in the third embodiment is compared with the pointer detecting device 2 in the second embodiment, except that the spreading code supply circuit 221 and the associated parameter calculating circuit 304 are provided. The same applies to the same components as those of the first embodiment of the present invention. Therefore, the same reference numerals will be given to the same components, and detailed description thereof will be omitted. First, the configuration of the spread spectrum code supply circuit 222 in the third embodiment will be described with reference to Fig. 24 . As shown in Fig. 24, the spread code supply circuit 222 is composed of a plurality of spread spectrum code generating circuits 24 and an FSK modulation circuit 27. The spread code generation circuit 24 and the FSK modulation circuit 27 are respectively subjected to FSK modulation for the 16 types of spread codes Ci, C2.....Ci 6 which are generated in synchronization with each other according to the same clock. Therefore, each of them is set to 16 each. However, each FSK modulation circuit 27 separately has a respective spreading code. <^~(:16 is used for FSK modulation, and the FSK modulation signals CIF, C2F, ..., C16F are supplied to the transmission conductor 12. Next, with reference to Fig. 25, related to the third embodiment. The configuration of the calculation circuit 314 will be described. Fig. 25 shows the circuit configuration of the correlation calculation circuit in the third embodiment, and the correlation calculation circuit and the 1/V conversion circuit and the A/D conversion circuit. The connection relationship is shown in the figure. The correlation calculation circuit 3 1 4 is composed of the FSK demodulation circuit 1 27, the signal delay circuit 3 04a, and the 16 correlators 3 04b, 3 04b2..... 3 04b16, and the correlator 3 04b !~3 04b, 6 with the same number of correlations calculus code generation circuit 3 04Cl, 3 04c2 ..... 3 04c16, and related memory circuit 3 04d. FSK solution The adjustment circuit 127 is a circuit for demodulating the spread spectrum code FSK modulated by the FSK modulation circuit 27 (refer to FIG. 24) into the original spread code -55-201122922. This FSK solution The adjustment circuit 127 is disposed between the A/D conversion circuit 33 and the signal delay circuit 304a, and is made by the A/D conversion circuit 33. The digitally converted output signal is subjected to FSK demodulation. Specifically, for example, a signal to be modulated into the state shown in FIG. 23(b) is demodulated to be modulated as shown in FIG. 23(a). In the third embodiment, the FSK demodulation circuit 127 is provided in the correlation calculation circuit 3 1 4 (that is, the signal is converted into a digital signal). The latter output signal is exemplified, but the present invention is not limited to this configuration. As long as the current signal as the output signal is converted into a voltage signal, FSK demodulation can be performed. Therefore, the FSK demodulation circuit 127 can also be disposed between the amplifying circuit 32 and the A/D conversion circuit 33. The output signal demodulated by the FSK demodulation circuit 127 is It is supplied to the D-reactor circuit 3 04ai~ 3〇4a63 which is connected in series in a plurality of stages, and the output signals from the respective D-reciprocator circuits 3 04ai to 3 04a63 are input to all of them. Correlator 3041^- 3041^6" In addition, other components and processing Since it is the same as FIG. 22 of the second embodiment described above, the same reference numerals as in FIG. 22 are attached, and the description thereof is omitted. In the third embodiment, the plurality of spreading codes are FSK-adjusted. And the spread spectrum code modulated by the FSK is simultaneously supplied (multiple transmission) to the plurality of transmission conductors 12 constituting the transmission conductor group 11, and the selected plurality of signal conductors 14 are selected. To detect the position of the indicator at the same time. As a result, in the third embodiment, the same effect as the -56-201122922 of the second embodiment can be obtained. Moreover, by adjusting the spreading code as F s κ , it is possible to widen the band of the signal supplied to the body group 1 1 and to be able to withstand noise. <4, Fourth Embodiment: Other Supply Method of Spreading Code> In addition, in the first embodiment (refer to FIG. 4), the configuration is exemplified: that is, the transmission is constituted. Each of the conductors of the conductors 12 is divided into a plurality of transmitting blocks 25 formed by four adjacent transmitting conductors ,|, and each of the plurality of transmitting regions is supplied with respective spreading codes c 1 to c 16. Then, the spread code C i - is supplied to one of the four signal conductors Yn to γ constituting the four of the communication blocks 25. However, in the present invention, the spread spectrum C16 may not be supplied to the previously prepared transmission conductor 12, but may be supplied to any of the transmission conductors 12. Hereinafter, the supply pattern examples 1 to 3 of the spread spectrum code will be described with reference to Figs. 26 to 29 . [Modification 1] First, the spread spectrum code method in Modification 1 will be described with reference to Fig. 26 . In the first modification, although not specifically shown, for example, a switch is provided between the transmission conductor selection circuit 22 and the extension circuit 2 1 shown in Fig. 4 . Then, by means of the switch, the spread codes C, which are supplied from the spread code supply circuit 21, are increased (the transmission directivity is improved by the following group 1 1 to Yn + 3 blocks 25 - C 1 6 is, + 3 code C, ~ is set to a suitable variable supply. However, the frequency code is set to be: 16: via -57- 201122922 This switch is not shown to be selectively supplied to the transmission conductor. The configuration of the circuit 22 is selected. The other configuration is the same as that of the first embodiment shown in Fig. 1. Therefore, the description of the same configuration will be omitted as appropriate. The transmission conductor selection circuit 22 selects 16 transmission conductors 1 from the transmission conductors Yi to Y64 at intervals of five. Specifically, the transmission conductor selection circuit 22 is initially sent. The signal conductor Υ, Υ5..... Υ57, Y61 are selected and supplied to each spread code C16. Then, in this state, the spread code is supplied between specific times. Then, the message is sent. The conductor selection circuit 22 traverses a direction in which the index mark η of the transmission conductor 12 is oriented in an increasing direction. The transmission conductor 12 is selected. That is, the 16 transmission conductors Υ, Υ5.....Υ57, Y61 selected in the previous time are respectively switched to the transmission conductors Υ2, Υ6.... Υ5 8 and Υ62. Then, the respective spreading codes α~(:16, which are supplied from the spreading code supply circuit 21, are simultaneously supplied to the newly selected transmission conductors Υ2, Υ6.... Υ58, Υ62. Thereafter, the switching operation of the above-described transmission conductor 12 is sequentially performed in reverse, and the spreading code is supplied. However, if the transmission conductor selection circuit 22 is used, each spreading code is used. (:, ~ C16 are simultaneously supplied to the transmission conductors Υ4, Υ8.....Υ6〇 and Υ64, respectively, and the communication area for which the respective spreading codes are supplied by a switch (not shown) Block 25 (refer to Fig. 4) is switched, and the above operation is repeated. For example, if attention is made to the transmitting block 25 formed by the transmitting conductor Υ, Υ4, first, the transmitting block 2 5 At the same time, the spread code C is supplied, and the spread code C is supplied from the transmission conductor in sequence, and then -58-201122922 'like the above one The transmission conductor selection circuit 22 switches the transmission conductor supplied with the spread code Ci for a time-lapse manner, and after the spread code C i is supplied to the transmission conductor Y4, the transmission conductor The selection circuit 22 switches the transmission conductor to which the spread spectrum code is supplied, and the switch (not shown) switches the spread code C supplied to the transmission block 25 to the spread code c2. And repeating the above switching operation. When the spreading code is again supplied to the transmitting conductor Y4, the 'sending conductor selection circuit 22 switches the transmission conductor supplied to the spreading code to Y! again, and 'not The switch shown in the figure switches the spread code C2 to the spread code c3, and then repeats the above operation. Further, in the example shown in the first modification, the direction in which the transmission conductor 12 is connected to the indexing element η is increased in each specific time by the transmission conductor selection circuit 22. The example of the switching has been described. However, the present invention is not limited thereto. For example, the signal conductor 12 connected to the spread spectrum code supply circuit 21 may be switched in a direction in which the index number η is decreased. Further, the transmission conductor 12 can also be randomly selected in accordance with a specific sequence. Further, in the description so far, the switching of the transmission conductor 12 has been described. However, the signal conductor 14 may be randomly switched in accordance with a specific sequence. [Variation 2] In the first modification, the transmission conductor selection circuit 22 selects 16 of the transmission conductors Y, Y64 at intervals of 5 at predetermined intervals. The transmission conductor 12 is shown by switching the selected transmission conductor -59-201122922 1 2 'to the way that the index number η is increased, and supplying the example of the spread spectrum code C k ' . However, the selection of the transmission conductor 12 to which the spread spectrum code c k is supplied may not be selected to be vacant with a specific number of intervals. The second modification will be described with reference to Figs. 27 and 28 . First, the configuration of the transmission conductor selection circuit 202 in the second modification will be described based on Fig. 27 . In the second modification, the transmission conductor group 11 is divided into a plurality of transmission blocks 125 formed by the adjacent 16 transmission conductors Yn to Yn+15. Specifically, the transmission conductor group 11 formed by the 64 transmission conductors Υ, Υ 64 is divided into four of the transmission conductors Yi to Y16, Υ17 to Υ32, Υ33 to Υ48, and Υ49 to Υ64. Sending block. The transmission conductor selection circuit 202 is composed of a spreading code (^~(:16) supplied from the spreading code supply circuit 21 to the switch 202a supplied to each of the transmission blocks 125. This switch 202a is a switch group formed by 16 switches, and the respective output terminals 202b of the 16 switches are connected to corresponding communication conductors Yn~Yn+15, and respectively The input terminal 202c is connected to each of the spreading code generating circuits 24 (refer to Figs. 1 and 3) of the corresponding spreading code supply circuit 21. However, by connecting the switch 202a to the spread spectrum The transmission block 125 at the code generation circuit 24 is switched over time, so that the spread codes C, C, and 6 can be supplied to all of the transmission conductors 12. Further, in Fig. 27 In order to avoid complexity, the switch 02 a is omitted. The other configuration is the same as the first embodiment (see FIG. 1 and the like). Therefore, the phase is 60. - 201122922 The same structure is attached with the same number 'and its description is omitted. Next, according to Figure 2 8' is a description of the method of supplying the spread spectrum code in Modification 2. First, the transmission conductor selection circuit 202' selects the transmission block 125 formed by the transmission conductors Y, YY16 (Fig. 28). Then, the spread code supply circuit 21 separately supplies the spread code (^16 (: 16) to the respective transmission conductors Yi to Y16 which constitute the transmission block 125. When in this state After the supply of the spread code C, ~ 〇16 is performed for a certain period of time, the transmission conductor selection circuit 202 switches the transmission block 125 connected to the spread code supply circuit 21 to The transmitting conductors Υ 17 to Υ 32 form a transmitting block 125, and simultaneously supply the spreading codes Ci to C16 to the respective transmitting conductors Y17 to Y32 constituting the transmitting block 125. Thereafter, the transmitting conductor selection circuit 202, repeating the action of switching between the transmitting block 125 and the simultaneous feeding of the spreading codes C, ~C i 6. Then, if the transmitting conductor selection circuit 202 is connected to the transmitting conductor Y49~ The transmitting block 125 formed by Y64 is selected, and the slave spreading code supply circuit 21 is ended. The spreading code (^~(:16 supply') of the transmission conductors Υ49 to γ64 is returned to the transmission conductor by the transmission conductor block. </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> </ RTI> The transmitting conductor Υπ~Υn+15 is formed by the transmitting block 125, and the spreading block C 1~c , 6 is supplied to the transmitting block 1 2 5 , and for the transmitting block 1 2 5 In the case of cutting -61 - 201122922, the spreading code (^~(:16) is supplied for the case where all of the transmission conductors 12 constituting the transmission conductor group 11 are supplied (refer to FIG. 27 and Figure 28) 'However, the switching of the transmission conductor 12 is not limited to being performed in each of the communication blocks. Referring to Fig. 2, a modification 3 will be described. In the third modification, the transmission conductor selection circuit supplies the spread spectrum code to the adjacent 16 communication conductors Yn to Yn+15 of the transmission conductors 12 constituting the transmission conductor group 11 (: And C16, and the transmission conductors Υn to Υn+15 selected by the signal conductor selection circuit 202 are switched over and over one by one in a direction in which the index number η is increased. First, the transmission conductor selection circuit 202, for example, selects the transmission conductors Υ!~Υ16 (the state of Fig. 29). Next, the spreading code supply circuit 2 1, respectively, spreads the code C, ~ C 6 is simultaneously supplied to the transmission conductor. In this state, after the supply of the spreading code C, ~ Ci 6 is performed between the specific times, the transmission conductor selection circuit 202 selects the selected transmission conductor. 12 is switched toward a direction in which the index number η is increased. That is, the transmission conductor selection circuit 2〇2' switches the 16 selected transmission conductors of the previous time, -Υίδ switching For the transmission conductor Υ2~Υ17. Then, the spread spectrum code supply circuit 2 1 'will spread the code C!~C And 6 are simultaneously supplied to the newly selected transmission conductors γ2 to γη. Then, the 'send conductor selection circuit 202 performs the above-mentioned switching operation in reverse, and performs the spreading code C, C16 In addition, in Modifications 2 and 3, 'the transmission conductor for connecting the transmission conductor selection circuit 220 to the spread spectrum code supply circuit-62-201122922 21 for each specific time is used. 12 is described as an example of switching the direction in which the index number n is increased. However, the present invention is not limited thereto. It may be connected to the spreading code every specific time. The transmission conductor 12 at the supply circuit 21 is switched in a direction in which the index n is reduced. Further, the transmission conductor 12 can be randomly selected in accordance with a specific sequence. <5. Fifth Embodiment: Method of Selecting Received Conductor> In the first embodiment, the received conductor group 13 is divided into the detection block 36, and the received conductor selection circuit 2 2 The description is made by referring to the case where one of the detection conductors 14 of the detection block 36 is selected in each specific time (refer to FIG. 6), but the present invention is not limited thereto. . For example, it is also possible to perform correlation calculations in batches in each detection block 36, and after a certain time, switch the detection blocks to other detection blocks and perform related calculations. [Modification 4] A modification 4 will be described in detail with reference to FIGS. 30 and 3 . Here, Fig. 30 is a circuit configuration diagram of the received conductor selection circuit and the amplifying circuit in the fourth modification. In the fourth modification, the received conductor group 13 is divided into a plurality of detection blocks 136 formed by 16 adjacent transmission conductors 〜^ to Xm+15. Specifically, the received conductor group 13 is divided into eight detection blocks 136 of the received conductors X1 to X16, Xl7 to X32, X33 to X48, ..., X|" to Xi28. The -63-201122922 received conductor selection circuit 131 is generally constituted by a switch 1 31 a formed by 16 logical switches as shown in FIG. The respective output terminals 131c of the 16 switches are connected to the respective I/V conversion circuits 32a constituting the amplifier circuit 32. Further, each input terminal 131b of the switch 131a is connected to the corresponding signal conductor 14. In addition, the other configurations are the same as those of the first embodiment (see FIG. 1 and FIG. 6) shown in FIG. 1. Therefore, the same components are denoted by the same reference numerals, and the description thereof will be omitted. Next, the operation of the received conductor selection circuit 131 will be described in detail with reference to FIG. The received conductor selection circuit 133 selects a specific detection block 136. For example, the detection block 136 (state of Fig. 31) formed by the signal conductors X! to 乂16 is initially selected. Then, the correlation calculation circuit 34 performs correlation calculation on the output signals output from the received conductors X! to Xl6 constituting all of the selected detection blocks 136, and calculates the correlation calculation for this purpose. The correlation of the result is stored in the correlation memory circuit 34d (refer to Fig. 8). Next, after a certain time, the received conductor selection circuit 131 switches the selected detection block 136 to the detection block 136 formed by the received conductor parent |7~\32. Then, the correlation calculation circuit 34 performs correlation calculation on the output signals output from the received conductors χ17 to Χ3 2 constituting all of the newly selected detection blocks 136, and stores the correlation 在 in Corresponding to the memory circuit 34d. Thereafter, if the above-described switching operation is repeated at every specific time, the correlation signal for the output signal from the detection block 136 formed by the signal conductors x113 to x128 is terminated. The memory of the 値 is returned to the detection block 163 formed by the signal conductors χ 1 to X16, and then the same switching and related calculations are performed. <6. Sixth Embodiment: Other Configuration Example of Sensing Unit> In the first embodiment, the surface of one of the first substrates 15 is generally used as shown in Fig. 2 Although the receiving conductor Μ and the transmitting conductor 1 2 are exemplified by the sensing unit 1 disposed opposite to the spacer 16 , the present invention is not limited thereto. For example, the signal conductor 14 and the signal conductor 12 may be formed on both sides of a single glass substrate. Hereinafter, another configuration example of the sensing unit will be described based on Fig. 3-2. [Variation 5] FIG. 32 is a schematic cross-sectional view of the sensing unit 500 according to the modification 5 of the present invention. The sensor unit 500 includes, for example, a substrate 501 which is formed in a substantially flat shape and is formed of, for example, glass, and a surface formed on one of the substrates 501 (via a pointer 19 such as a finger or the like) A plurality of signal conductors 514 on the surface on the side indicated, and a plurality of signal conductors 512 formed on the other surface (the surface on the lower side in FIG. 32) of the substrate 501. The surface of the transmission conductor 5 1 2 is covered by the first protective layer 513 which is formed so as to cover the entire surface of one of the substrates 50 1 . Similarly, the signal conductor 5 1 4 is covered by the second protective layer 5 1 5 which is formed by covering the entire other surface of the substrate 510 , and is covered by -65-201122922. The protective layer 515 is further covered by a slightly flat protective sheet 516. The protective sheet 516' is protected so that the received conductor 5 14 is not damaged by contact with the indicator 19 directly. Further, in the fifth modification, the substrate 501, the transmission conductor 512, and the signal conductor 514 can be formed by the same material as that of the first embodiment. In other words, in the fifth modification, the same as in the first embodiment, a substrate made of synthetic resin can be used in addition to a well-known glass substrate. A flaky (film-like) substrate. Further, the first protective layer 513 and the second protective layer 515 can be formed, for example, by a SiO 2 film or a synthetic resin film, and the protective sheet 5 16 can be formed, for example, of a synthetic resin or the like. Sheet member. Further, in the fifth modification, the first protective layer 5 1 3 'the second protective layer 5 15 and the protective sheet 5 16 are respectively covered on both sides of the substrate 510. The manner in which the method is formed is exemplified, but the present invention is not limited thereto. For example, since the protective sheet 516 is formed so as not to directly contact the indicator 19 and the received conductor 51 4, the object can be achieved, and therefore, the shape can be formed and received. The conductors 514 are shaped to have the same shape. In the sensing unit 500 shown in the fifth modification, the number of the substrates can be reduced as compared with the sensing unit 100 of the first embodiment (see FIG. 2). The thickness of the sensing portion is set to be thinner. Further, in the sensing unit 500 of the fifth modification, since the number of substrates can be reduced, it is possible to provide a sensing portion which is more inexpensive. -66 - 201122922 [Modification 6] Next, according to Fig. 3, other changes to the sensing unit are made. In the sixth modification, for example, a configuration of a sensing portion for forming a signal conductor and a signal conductor on a substrate is shown in FIG. 3 ( a ) as a sensing portion for the modification 6. The figure is shown in Fig. 3 3 (b), which is shown for the body diagram of this modification 6. In addition, in this FIG. 33, a protective layer and description are abbreviate|omitted. The sensing unit 600 according to the sixth modification, as shown in FIG. 33(a), includes a substrate 601 and a metal layer 602 having a conductive metal layer 602 formed on one surface of a specific pattern. The upper insulating layer 603, and the plurality of transmitting signals _ and the plurality of signal conductors 6 1 4 . On the other hand, in one of the 601 of the sixth modification, the transmitting conductor 612 and the side intersecting each other are provided, and the communication conductor 6 1 2 and the signal receiving conductor 6 are intervening to provide The mutually electrically conductive layer 6 0 3 〇 metal layer 602 extends as shown in FIG. 33( b ) toward a square body 61 intersecting the direction in which the signal conductor 6 14 extends. The direction line) is formed by extending and forming a portion of the insulating layer 603, which is formed by coating a portion of the metal layer 602. A signal conductor 612 is provided at both ends of the extending direction of the metal layer 602, and is disposed on one side of the extended shape of the metal layer 602. The substrate 601 is generally shown in the vertical protective sheet of the sensing section of the schematic section and is insulated from the insulating body formed by the substrate chrominance conductor 6 1 4 1 4 . For example, in the manner of the metal of the transmission guide metal, the cover conductors 61 2 at both ends of the set direction -67-201122922 are electrically connected by the metal layer 602. The conductors 614 are formed on the insulating layer 603 and electrically insulated from the metal layer 602 and the signal conductor 614. In addition, the configuration of the signal conductor 612 and the signal conductor 614 are In the sixth modification, the signal conductor 612 and the signal conductor 614 are disposed on the one side of the substrate 601 for indicating the position of the indicator 19, but the signal conductor 612 and the signal conductor 614 are disposed. Alternatively, the signal conductor 61 2 and the signal conductor 61 4 may be disposed on the other surface facing one of the substrates 601. Further, in the modification 6, the substrate 601 and the transmission conductor 612 and the signal conductor 614 can be compared with the first embodiment described above. In other words, in the same manner as in the first embodiment, the substrate 60 1 may have a sheet-like shape (film shape) formed of a synthetic resin in addition to a well-known glass substrate having permeability. Further, the metal layer 602 can be formed by a metal material having high conductivity, for example, by Mo (molybdenum), etc. Contact between the metal layer 6〇2 and the signal conductor 6 1 2 The area is small, and therefore, in order to reduce the resistance, it is preferable to use a metal material having high conductivity in the metal layer 602. Further, the insulating layer 603, for example, may be made of a resist. The sensor unit 600 of the sixth modification is capable of reducing the number of glass substrates compared to the sensor unit 100 of the first embodiment (FIG. 2). The thickness of the sensing portion 600 is made thinner. Further, in the sensing portion 600 of the sixth modification, since the number of substrates can be reduced, the transmitting conductor 612 and the signal conductor 614 are substantially borrowed. It consists of 1 layer -68- 201122922, so it can provide In the sensor unit 600 of the sixth modification, the sensor unit 600 is disposed on the other side of the substrate 601 in order to perform the position indication. In the case of the conductor 612 and the signal conductor 614, etc., since the substrate 601 is interposed between the indicator and the conductors, the indication is compared with the case of the sensing unit 500 of the modification 5 The distance between the body and each of the conductors is widened, and the influence of the noise from the indicator is reduced. [Modification 7] In the first to third embodiments and the modifications 1 to 6, The case where the transmission conductor is formed by a linear conductor extending in a specific direction is exemplified. However, in the seventh modification, another configuration example of the shape of the transmission conductor will be described. . This modification 7 will be described based on Fig. 34. Here, in FIG. 34(a), the schematic configuration of the transmission conductor and the signal conductor at the sensing portion of the modification 7 is shown, and in FIG. 34(b), the transmission is performed. An enlarged view of the island-shaped conductor portion of the conductor. In the modification 7, as shown in Fig. 34 (a), the signal conductor 714 is formed by a conductor having a wide linear shape. The signal conductor 712 is provided with a conductor portion 722 having a line shape extending in a direction orthogonal to the direction in which the signal conductor 714 extends, and an island conductor having a wider width than the conductor portion 722. The portion 72 3 is electrically connected. Then, at least the intersection between the received conductor 714 and the conductor portion 722 is electrically insulated from each other by interposing an insulating layer (not shown) of -69-201122922. As shown in FIG. 34(b), the island-shaped conductor portion 723 is formed of first and second island portions 723b and 723c which are formed in substantially the same shape, and the first and second island portions 723b and 723 are formed. The first and second island portions 723b and 723c, which are formed by the substantially linear connecting portions 723d that are electrically connected to each other, are formed in a slightly triangular shape having a top portion 723a, and are formed at the top portion 723a. The conductor portion 722 is electrically connected. On the other hand, the first island portion 723b and the second island portion 723c are electrically connected to each other at the bottom portion 723e facing the top portion 723a by the connecting portion 73d. Further, although FIG. 34 shows an example in which the extending direction of the signal conductor 714 is orthogonal to the extending direction of the transmission conductor 712, the present invention is not limited thereto. The extending direction of the two conductors does not necessarily have to be orthogonal, and the extending direction of the transmitting conductor 712 may be crossed with the extending direction of the received conductor 714 so that the intersection for detecting the position can be generated. When the island-shaped conductor portion 723 is formed as described above, as shown in Fig. 34 (b), in the island-shaped conductor portion 723, a concave portion 723f is formed along the extending direction of the signal conductor 714. By setting the shape of the transmission conductor 712 to the above-described general shape, the area of the transmission conductor near the intersection can be increased. As a result, when the pointer approaches the sensing unit 700, the electric field emitted from the transmitting conductor 712 converges more at the indicator, so that the detection sensitivity can be improved. Further, when the pointer detecting device to which the present invention is applied and the pointer detecting device using the electromagnetic sensing method (EMR: Electro Magnetic Resonance) of -70-201122922 are overlapped, the region where the pointer is detected is configured In the case of a common input device, an eddy current is generated at the island-shaped conductor portion 723 due to an electric field generated by the electromagnetic induction type position detecting device, and the eddy current is caused by the position detection of the electromagnetic induction mode. Adverse effects (eddy current loss). On the other hand, by forming the concave portion 723 f at the island-shaped conductor portion 723 located near the intersection as in the above-described modification 7, even if the indicator detecting device to which the present invention is applied is used, When the pointer detecting device of the electromagnetic induction type is disposed in an overlapping manner, the generation of the eddy current can be suppressed by the island-shaped conductor portion 723, and the above-described general problem can be eliminated. Further, the configuration of the seventh modification is not limited to the sensing unit of the pointer detecting device of the cross-point electrostatic coupling type, and may be applied to a projection having the same conductive pattern as that of the intersection. In the indicator detection device of the electrostatic coupling type. In other words, the first conductor may be formed of a plurality of first conductors arranged in the first direction and a plurality of second conductors arranged in a direction intersecting with the first direction. a conductor pattern, and according to the detection signals obtained from the conductors disposed in the respective directions, the conductors corresponding to the respective positions corresponding to the indicated positions at the conductors arranged in the respective directions are specified. A sensing unit of the pointer type detecting device of the projection type electrostatic coupling type that seeks to extract the position indicated by the pointer from the position where the specified positions of the conductors are intersected Waiting for it. Further, in the first embodiment (FIG. 2), the fifth modification (FIG. 3 2), and the modification 6, the transmission conductor 712 and the reception conductor 714 of the modification 7 can be configured as -71 - 201122922. The sensing unit described in (Fig. 3 3) is applicable. Further, when the indicator detecting device and the display device such as a liquid crystal panel are integrally formed, it is preferable to suppress the influence of the signal from the scanning of the pixel caused by the liquid crystal panel. The 1 4 system has a direction in which the extending direction is arranged to intersect the pixel scanning direction of the liquid crystal panel. [Modification 8] The shape of the island-shaped conductor portion of the transmission conductor is not limited to the example shown in FIG. In Fig. 35, another configuration example of the shape of the island-shaped conductor portion (Modification 8) is shown. The transmission conductor 812 at the sensing portion 800 of the modification 8 is the same as the modification 7, and is composed of the conductor portion 822 and the island-shaped conductor portion 823. The difference from the modification 7 is that the first and second island portions 723b and 723c of the island-shaped conductor portion 723 shown in the modification 7 are formed in a slightly triangular shape. The first and second island portions 823b and 823c of the island-shaped conductor portion 823 shown in the modification 8 are formed in a substantially trapezoidal shape. In the eighth modification, the upper bottom portion 823a of the portion corresponding to the top portion 723a of the first and second island portions 723b and 723c of the seventh modification is electrically connected to the conductor portion 822. Sexual connection. The other parts are the same as the modification 7 shown in Fig. 34, and therefore, the same reference numerals as in Fig. 34 are attached, and the detailed description thereof will be omitted. However, in Fig. 34 and Fig. 35, the position of the beginning of the 'the same part' number is also a different number. In the seventh modification of Fig. 34, the figure is set to the beginning of 7, in the figure. 3 5 deformation -72- 201122922 In Example 8, the system is set to start with 8. When the modification 8 is compared with the modification 7, the island-shaped conductor portion 823 of the transmission conductor 812 of the modification 8 is such that the top portion 823a of the island-shaped conductor portion 823 does not exist (there is no The shape of the acute angle is therefore wider than that of the conductor portion 8 2 2 . As a result, at the connection portion between the island-shaped conductor portion 823 and the linear conductor portion 822, concentration of current is less likely to occur, and current is diffused. That is, since the current flows and flows between the upper bottom portions 823a to 823a which are the both ends of the island-shaped conductor portion 823, the resistance between the upper bottom portions 8 2 3 a - 8 2 3 a does not occur. Becomes high. With such a structure, the flow path of the current between the island-shaped conductor portion 823 and the conductor portion 82 2 can be made wider than in the seventh modification. As a result, compared with the modification 7, the electric conduction characteristics can be further improved. Further, the shape of the upper bottom portion 8 2 3 a is preferably a portion having no acute angle, and may be formed into a curved shape in addition to the above shape. Moreover, the transmission conductor 812 of the sensing unit 800 of the modification 8 is similar to that shown in FIG. 35, and the two concave portions 8 23 f are formed in the island-shaped conductor portion 823. Although the concave portion 823 f is not limited to two, for example, one or only three or more may be formed. In addition, the configuration of the eighth modification is not limited to the sensing unit of the pointer detecting device of the cross-point electrostatic coupling type, and may be applied to the sensing unit of the projection type detecting device of the projection type electrostatic coupling type. Wait. Further, in the eighth modification, the case where the conductor conductor is formed of a linear conductor portion and an island-shaped conductor portion having a concave portion at a central portion thereof is described in the example of -73-201122922. However, the received conductor may be configured to be the same as the transmission conductor. Further, the configuration of the transmission conductor 812 and the signal conductor 814 of the eighth modification can be applied to the first embodiment (Fig. 2), the modification 5 (Fig. 32), and the modification 6 (Fig. 3). The sensing unit described is applicable. Further, when the indicator detecting device and the display device such as a liquid crystal panel are integrally formed, in order to suppress the influence on the liquid crystal panel, as described above, it is preferable to receive the conductor 7 1 4 is disposed in a direction crossing the pixel scanning direction of the liquid crystal panel. [Variation 9] In the indicator detecting device using the cross-point electrostatic coupling method, generally, the sensing portion is observed from the surface side (that is, the upper side) that operates on the indicator. At the time, the plurality of signal conductors intersect the transmission guide system and have a region where the conductor pattern exists and a region where the conductor pattern does not exist. Each of the conductors is formed by a transparent electrode film such as an ITO film. However, the transmittance of the region in which the conductor pattern exists is lower than that in the region where the conductor pattern is not present. As a result, unevenness in transmittance occurs in the sensing portion. Depending on the user's personal disparity, there will be situations where the rate of transmission is not the same. Therefore, in the ninth modification, a configuration for eliminating the unevenness of the transmittance on the sensing portion will be described. In Fig. 36, the schematic configuration of the sensing portion of this modification 9 is shown. Here, the description will be made with respect to an example applied to the sensing unit 500 of the modification 5 (Fig. 32) at -74 to 201122922. In the sensing portion 510 of the ninth modification, in the region where the transmission conductor 5 1 2 and the signal conductor 5 1 4 are not present, for example, the first transparent material made of the same material as the conductor is provided. The electrode film 517 and the second transparent electrode film 518» are configured in the same manner as the sensing unit 500 of the fifth modification (Fig. 32). Therefore, the same number is attached to the same configuration. And omit its description. In Fig. 37 (a), the configuration of the signal transmission conductor 512 and the first transparent electrode film 517 formed on one surface (lower surface) of the substrate of the sensing portion 510 is shown. In the ninth modification, the first transparent electrode film 5 1 having a rectangular shape is disposed between the two communication conductors 512 disposed adjacent to each other on the same surface as the transmission conductor 5 1 2 . 7. The first transparent electrode film 5 17 ' is provided with a small size smaller than the size between the signal transmission conductors 512 so as not to be in contact with the transmission conductor 512, and is between the transmission conductor 512 and the transmission conductor 512. It is separated from each other by a number of gaps. On the other hand, the size of the first transparent electrode film 517 in the extending direction of the transmission conductor 512 is set to be larger than the size between the received conductors 5 1 4 disposed adjacent to each other. The length of the conductor of the signal conductor 514 of one of the conductors 514 is more than a small size, and is provided between the signal conductors 514 which are adjacent to each other at two positions and extends to the respective signal conductors 514. The position of the conductor width is slightly 1/2 position and is arranged. Further, in Fig. 37 (b), the configuration of the signal conductor 514 and the second transparent electrode film 518 formed on the other surface (upper surface) of the substrate by the sensing portion 510 is shown. In the ninth modification, the second transparent electrode film 518 is disposed on the same surface as the surface on which the signal conductor 5 14 is disposed, and the size of the -75-201122922 is applicable to The size of the first transparent electrode film 517 is determined by the same method as the case of the predetermined size. That is, the second transparent electrode film 518 is provided with a small size smaller than the size between the received conductors 514 so as not to be in contact with the signal conductor 514, and between the signal conductor 514 and the signal conductor 514. , separated from each other by a number of gaps. On the other hand, the size of the second transparent electrode film 518 in the longitudinal direction of the signal conductor 514 is set to partially cover the signal transmission conductors 512 disposed adjacent to each other. When the size and arrangement of the first transparent electrode film 517 and the second transparent electrode film 518 are observed from the surface side (upper side) on the surface of the indicator, for example, when the sensor portion 5 1 0 is viewed, The overlapping relationship between the conductor 512, the signal conductor 514, the first transparent electrode film 517, and the second transparent electrode film 518 can be set and arranged as homogeneous as possible while maintaining electrical insulation. In addition, it is possible to suppress the unevenness of the transmittance and maintain the uniform optical characteristics for the entire sensing unit 510. If the conductors and the transparent electrode films of the sensing portion 510 formed on the respective faces of the substrate are arranged as shown in FIGS. 37 (a) and (b), respectively, when the sensing portion 5 is provided from above. In the case of observation, as shown in Fig. 36, in the region where the conductor pattern is not present, the first transparent electrode film 51 7 and the second transparent layer formed of the same material as the conductor are formed. Electrode film 5 18 . As a result, the unevenness of the transmittance at the sensing portion 510 is suppressed. Further, the shapes of the first transparent electrode film 517 and the second transparent electrode film 518 for suppressing variations in transmittance are not limited to the shape of the moment -76-201122922. The conductor pattern formed by the transmission conductor 512 and the signal conductor 514 and the first transparent electrode film 517 and the second transparent electrode film 5 1 8 are observed when the sensor portion 510 is viewed from above. The overlapping relationship may be optically uniform, and the shapes of the first transparent electrode film 51 7 and the second transparent electrode film 518 are related to the shape of the conductor pattern formed by the signal conductor 512 and the signal conductor 514. It is appropriate to make a decision. For example, in the ninth modification, the rectangular transparent electrode film is disposed at a specific interval along the direction in which the transmission conductor 512 or the signal conductor 5 14 extends. However, the plurality of transparent electrode films may be formed as one electrode film. Further, the configuration of the ninth modification can be applied to the sensing unit described in the first embodiment (Fig. 2) and the modifications 6 to 8 (Figs. 3 to 3). Further, for example, a substrate in which a transparent electrode film for preventing transmittance unevenness is formed in a specific region may be separately prepared, and the substrate may be additionally provided in the sensing portion. Further, as in the above, a film-like substrate can also be used. [Modification 1] In the above-described first to third embodiments, the case where the transmission conductor and the signal conductor are both formed in a line shape is exemplified. However, the present invention is not limited to this. For example, at least one of the transmission conductor and the signal conductor may be formed by a conductor formed in a curved shape or a concentric shape. Hereinafter, with reference to Fig. 38, a case will be described in which a plurality of transmission conductors are formed in a circular shape having a diameter of -77 to 201122922, and the arrangement is concentric. Fig. 3 is a diagram showing the arrangement pattern of the transmission conductor group 411 and the received conductor group 413 in the sensing unit 400 in the modification 1A. In the modification 10, the transmission conductor group 4 1 1 ' is configured by arranging a plurality of communication conductors 4 1 2 having different diameters in a concentric shape. Further, the respective transmission conductors 4 1 2 arranged in a concentric shape are arranged such that the intervals between the transmission conductors 41 2 adjacent in the radial direction are equally spaced. On the other hand, the signal conductor group 413 is constituted by, for example, a plurality of signal conductors 41 4 having a linear shape extending from the center of the transmission conductor group 4 1 1 in a radial shape. Further, the plurality of signal conductors 414 are arranged at equal intervals in the circumferential direction. With such a configuration, the circumferential direction of the transmission conductor 412 and the direction in which the conductor 414 is extended intersect with each other to form an intersection. The sensing unit 400 shown in Fig. 38 is suitable, for example, when the position detecting area of the sensing unit 400 is circular. In addition, in the modification 10, the case where the plurality of transmission conductors 4 1 2 constituting the transmission conductor group 411 are arranged at equal intervals in the radial direction is exemplified. However, the present invention is not limited thereto, and the interval between the transmission conductors 41 and 12 may be appropriately set to a desired interval. In the same manner, in the first modification, the plurality of signal conductors 414 constituting the signal conductor group 4 i 3 are arranged at equal intervals in the circumferential direction of the transmission conductor 412. For example, the interval between the received conductors 4 1 4 may be appropriately set to a desired interval. Further, in the above-described modification, the case where the transmission conductor 4丨2-shaped -78-201122922 is slightly circular and the received conductor 4 14 is formed in a straight line is exemplified, but The present invention is not limited thereto. For example, at least one of the transmission conductor 412 and the signal conductor 414 may be serpentine in a direction in which it extends. <7, the seventh embodiment: another configuration example of the amplifier circuit> In the first to third embodiments, the input and output are used for the amplifier in the amplifier circuit 32 (refer to FIG. 1). The example of the amplifier is described, but the present invention is not limited thereto. For example, instead of an amplifier, a differential amplifier can also be used. Hereinafter, a case (variation 1 1 to 1 8) in which a differential amplifier of 2 input 1 output or 4 input 1 output is used in the amplifying circuit will be described with reference to Figs. 39 to 55 . Further, when the differential amplifying circuit is used in the amplifying circuit, the received conductor group 13 is composed of 129 received conductor turns. The configuration of the first embodiment (Fig. 1) is the same as that of the first embodiment (Fig. 1). Therefore, the same components as those in Fig. 1 are denoted by the same reference numerals, and detailed description thereof will be omitted. [Modification 1 1] A configuration of Modification 1 1 will be described with reference to Fig. 3 . Fig. 39 is a schematic diagram of the signal receiving portion in the case where a 2-input 1-output differential amplifier is used in the amplifying circuit. First, the received conductor group 13 is divided into a plurality of detection blocks 2 36. The detection block 2 3 6 is composed of nine received conductors xm to Xm + 8 adjacent to each other (index number m is continuous -79-201122922). Further, the received conductor Xm + 8 ' having the largest index number m among the received conductors Xm to Xm + 8 constituting each detection block 236 is shared with the other detected blocks 23 6 adjacent thereto. Specifically, in the modified example 11, the received conductor group 13 is divided into detection blocks { X , ~X 9 } , { X 9 〜 X , 7 } ..... { X 1 1 3 ~ X 1 2 1 } and { Xl21 ~ Xl29). The received conductor selection circuit 23 1 is composed of switches 2 3 1 a, 2 3 1 b of the same number as the detection block 23 6 . Further, the pair of switches 2 3 1 a and 231b' are provided at the two switches 231a and 231b, and have nine common input terminals 23 1 c. The input terminals 23 1 c are respectively connected to the corresponding received conductors Xm. The respective output terminals 231d and 231e of the pair of switches 231a and 231b are respectively connected to input terminals of an I/V conversion circuit 23 2a which will be described later. Then, the pair of switches 2 3 1 a, 2 3 1 b are sequentially switched to the signal conductors 14 connected to the I/V conversion circuit 232a at specific time intervals. Specifically, initially, if it is assumed that the switch 23 la is connected to the signal conductor X! and the switch 23 lb is connected to the signal conductor X2 (the state shown in FIG. 39), at the next specific time In the interval, the switch 23 la is connected to the signal conductor X2, and the switch 23 lb is connected to the signal conductor X3 to be sequentially switched and connected. Thereafter, the signal conductor Xm connected to the 1/V conversion circuit 232a is sequentially switched at a specific time interval, and the switch 231a is connected to the signal conductor X8, and the switch 23 lb is connected and received. After the conductor X9 is connected, the switch 23 la is connected to the signal conductor X again, and the switch 23 lb is connected to the signal conductor X2 to be switched and connected. -80-201122922 The receiving unit 310, as shown in FIG. 39, generally includes a signal receiving conductor selection circuit 231, an amplifying circuit 232, an A/D converting circuit 33, an associated chirp calculating circuit 34, and a position calculating circuit. 35 constitutes. The amplifying circuit 23 2 is composed of a 1/V converting circuit 23 2 a, a differential amplifier 205, and a changeover switch 23 2d. The 1/V conversion circuit 23 2a is provided in the same number as the total number of the switches 231a, 23 lb, that is, 32, and the input terminals 231c thereof are respectively associated with the respective signal conductors 14 is connected, and the respective output terminals 23 1 d and 23 1 e of the pair of switches 231a and 23 lb are respectively connected to the corresponding 1/V conversion circuit 232a. The output terminal of the 1/V conversion circuit 23 2a connected to the switch 23 la of the pair of switches 231a and 23 lb is connected to the input terminal of the polarity of the differential amplifier 250 which is "-". The output terminal of the 1/V conversion circuit 23 2a connected to the switch 23 lb is connected to the input terminal of the polarity of the differential amplifier 25 0 which is "+". The differential amplifier 250 is a 2-input 1-output differential amplifier. The differential amplifier 250 is differentially amplified and outputted from the output signal from the I/V conversion circuit 23 2a connected to the two input terminals. The output signal output from the differential amplifier 250 is amplified to a specific signal level at an amplifier (not shown), and then output to the A/D conversion circuit 33 via the changeover switch 232d. With the above-described general configuration, the noise superimposed on the output signal from each of the received conductors 14 is removed by differential amplification at the differential amplifier 250 of the amplifier circuit 232. Therefore, the noise resistance of the pointer detecting device can be improved. -81 - 201122922 [Modification 1 2] In the above-described modification 11, the signal conductor 14 is connected to each input terminal of the differential amplifier 25A via the 1 / V conversion circuit 23 2a. The number of the received conductors 14 connected to the respective input terminals of the differential amplifier may be exemplified as the case where the number of roots is one. In Fig. 40, an example is shown. Fig. 40 is a schematic configuration of the amplifying circuit of the modification 12 of the present invention. Although not shown in FIG. 40, in the modification 1, the signal conductor selection circuit 231 is a pair that selects two pairs of the signal conductors 14 by a plurality of pairs. The switches 231a and 231b are configured (refer to FIG. 39). However, in the modification 12, five switches are provided instead of the pair of switches 23 1 a and 2 3 1 b, and Five switches are used to appropriately connect the adjacent five received conductors Xm.2 to Xm + 2 to the input terminals of the differential amplifier 350. The received conductor selection circuit 23 1 (refer to FIG. 39 ) is, for example, Xm-2 of four of the five received conductors Xm-2 to Xm + 2 adjacent to each other at positions on both sides The Xm-I and Xm+1, Xm+2 are connected to the input terminals of any of the differential amplifiers 350. Further, in the modification 12, the output signal from the selected conductor Xm-2 to Xm + 2 selected by the signal conductor selection circuit 231 is also used in ΐ/v. The conversion circuit 23 2a is converted into a voltage signal and supplied to each input terminal of the differential amplifier 350. However, since it has the same configuration as the modification 11 shown in Fig. 39, therefore, In the case of FIG. 40, -82-201122922 omits the description of the received conductor selection circuit 23 1 and the 1/V conversion circuit 2 3 2 a. Specifically, the polarity of the signal conductors Xm_2 and Xd and the differential amplifier 350 in the five signal conductors Xm_2 to Xm + 2 selected by the signal conductor selection circuit 231 is "-". The input terminals are connected, and the received conductors Xm + 2 and Xm+1 are connected to the input terminals of the differential amplifier 350 having a polarity of "+". However, the signal conductor Xm positioned at the center is connected to the ground. Alternatively, the center of the signal conductor Χπ can be connected to an input that is set to a specific reference voltage level (for example, a reference level or a supply voltage level: Vcc) inside the differential amplifier 350. At the terminal. According to this configuration, the output signals from the plurality of received conductors Xm.2 to Xm + 2 are simultaneously input to the differential amplifier 350. As a result, since the differential signal output from the differential amplifier 350 is increased, the detection sensitivity can be improved. Further, since the number of the received conductors 14 connected to the differential amplifier 350 is increased at the same time, the detection area of the pointer can be widened. Further, in the first modification of the present invention, since the differential amplifier 232 (refer to Fig. 39) is used in the differential amplifier 232 (refer to Fig. 39), the same as the modification 11 can be used to improve the noise resistance. Further, in the modification I2, the reason why the signal conductor Xm positioned at the center is set to be ground or a specific reference voltage level is as follows. As described in the above-described first embodiment, in the pointer detecting device of the cross-point electrostatic coupling type, the cross current is caused by the current being shunted to the ground via the finger-83-201122922. The change in current at the point is detected (refer to Figure 13). However, if the indicator 19 is not sufficiently grounded, the shunting of the current at the intersection becomes insufficient. In this case, the current change at the intersection becomes small, and the detection sensitivity is lowered. On the other hand, as in the above-described modification 1, the voltage level of the signal conductor Xm at the center of the plurality of received conductors Xm_2 to Xm + 2 connected to the differential amplifier 350 is set. By grounding or by reference voltage level (for example, power supply voltage level or ground voltage level), even if the indicator body 19 is not sufficiently grounded, The body 19 is in contact with the signal conductor, and a part of the current can be shunted by the indicator and the signal conductor 乂>. As a result, the above-described sensitivity reduction can be suppressed. In addition, although the case where the detection sensitivity is improved by using the differential amplifier in the amplifying circuit is exemplified, it is also possible to provide the spreading code by supplying the spreading code to the plurality of transmitting signals. At the conductor, the detection sensitivity is further improved. [Modification 1 3] With reference to Fig. 4 1, a description will be given of Modification 13. In this modification 1, 3, as shown in Fig. 41 (a), generally ' For supplying the same spread code An example of the two adjacent communication conductors is shown. The configuration other than the one shown in Fig. 41 is the same as the modification 1 1 (refer to Fig. 1, Fig. 39, etc.). Therefore, the description of the same composition is omitted, and the illustration is omitted as shown in Fig. 41. Generally, the spread code generation circuit 24 constituting the plurality of spread code supply circuits 21 is generated. The 16 types of spread code C16 are respectively supplied to two adjacent transmission conductors 12. Specifically, the spread code Ci is supplied to the transmission conductors Y! and 丫2. The frequency code C2 is supplied to the transmission conductors Y5 and Y6, ..., the spread code C15 is supplied to the transmission conductors Y57 and Y58, and the spread code C! 6 is supplied to the transmission conductors γ61 and Υ62. However, although not specifically illustrated, the spreading conductors Ci to C16 are switched over by the transmission conductor selection circuit 22 for the transmission conductor 12 connected to the spread spectrum code generating circuit 24 over time. Is supplied to the transmission conductor 12 constituting all of the transmission conductor group 11 " here, for example, if When attention is paid to the signal conductor 14 of any one of the figures, if the same spread code is supplied to the plurality of signal conductors, the signal conductor 14 is compared with the first embodiment. The signal conductor 14 in the middle is supplied with twice the spreading code, so that the output signal from any of the received conductors 14 is doubled. Therefore, the detection sensitivity can be made. Further, if the same spread code is simultaneously supplied to the three or more transmission conductors 12, it can be proportional to the amount of the same spread code simultaneously supplied. The detection sensitivity of one of the received conductors 14 is increased. [Modification 14] Further, when the same spread code is supplied to the adjacent plurality of transmission conductors 12 as in the above-described modification 13 (refer to FIG. 4 1 ), it is more than -85- 201122922 The ideal ' is configured to amplify the output signal from the same number of the received conductors 14 as the number of the signal conductors 12 to which the same spread code is supplied. Referring to Fig. 42, a schematic configuration of Modification 14 will be described. This figure 42' is a schematic configuration diagram of an amplifying circuit when the same spreading code Ck is supplied to two adjacent transmitting conductors γη and Yn+i. In addition, the configuration other than that shown in FIG. 42 is the same as that of the above-described modification 11, and therefore, in order to avoid complication of the drawing, the description thereof and the description related to the configuration are made. Omitted. When the same spread code Ck is supplied to the adjacent two transmission conductors Yn and γη+ as in the above-described modification 13, the amplifying circuit 23 in the receiving unit 3 10 In two places, an amplifier having the same number of input conductors as the number of the transmission conductors 12 to be supplied with the same spread code Ck and having the same polarity input terminal is used, for example, two "+" terminals are used. 2 Input 1 output amplifier 360. On the other hand, at the input terminals of the amplifier 360 of the receiving unit 310, two adjacent received conductors Xm and Xm+丨 are connected. When the same spread spectrum code Ck is supplied to the adjacent two transmission conductors Yn, Υn+1 as described above, and the output signals from the adjacent two received conductors Xm' Xm+1 are outputted In the case of amplification, not only the signal level of the output signal output from the amplifier circuit 366 can be increased, but also the detection range of the pointer can be widened. As a result, since the time required for the detection of the entire sensing unit 100 (refer to FIG. 1) can be shortened, this embodiment is suitable for use in the position detection area of -86-201122922. In the case of the sensing unit. Further, in the case where this modification is simultaneously connected to the signal conductor 1 at the amplifier 360, the present invention is described. For example, in the case where three or more received conductors are used, it is possible to further shorten the time required for sensing the sound, and to increase the signal level of the output signal from the signal. . Further, if the number of the supply conductors 12 is the same as that of the simultaneous selection as in the above, the following general advantages can be obtained. And Figure 43 for comparison and explanation. Here, FIG. 43 is the same as the transmission conductor of the spread code Ck supplied to the two transmission conductors for the minimum detection area S min of the output signal from any one of the received conductors Xm. When the signal transmitted by the transmission conductor receiving conductor selection circuit having the same spreading code is simultaneously selected, that is, the received conductor connected to the amplifier 361 is different, as shown in FIG. Generally, the sense detection region Smin has a rectangular shape and is inductive. In this case, for example, the direction of the finger with the sense of the sense (hereinafter referred to simply as the opposite surface) is round. In the case of the surface, there is a case where the shape is not detected as a deformed shape such as a circular shape 匮1 shape. In general, the same spread code Ck 1 4 is supplied to the surface, although it is for 4 The number of roots is set to 2 and is not limited to this connection. The number of conductors of the same spread spectrum code ck outputted by the detection amplifier circuit of the entire 51 设 is set, and for Fig. 42, For the case where the phase and Υη+1 are enlarged, and the number of the number is 1 2 The number of the conductors 14 (the number of the roots of 14) is the surface of the smallest degree distribution on the measuring portion, and the indicator is detected as an ellipse. When the number of the signal conductors -87 - 201122922 is the same as the number of the received conductors 14 connected to the amplifier 361, as shown in FIG. 42, the smallest detection area on the sensing portion Smin has a square shape and can obtain an isotropic sensitivity distribution. In this case, even if a pointing body having a circular facing shape is disposed on the sensing portion, the indicator can be oriented. The surface is detected as a circular shape. In the modification 14, the number of the signal conductors 12 to be supplied with the same spread code Ck and the signal conductor 14 connected to the amplifier 360 are used. The case where the number of roots is set to two is exemplified, but the present invention is not limited thereto. The number of the signal conductors 12 to which the same spread code Ck is supplied is connected to the amplifier. The number of the signal conductors 14 at 360 may be three or more. Referring to FIG. 44 and FIG. 45, the switching of the two transmission conductors to which the same spreading code is supplied in the above-described modification 14 will be described. In the following description, reference is made to FIG. 1 as appropriate. For the sake of explanation, Fig. 44 shows an example of the switching of the transmission conductors to which the spreading code Ck2 is simultaneously supplied. The switching examples shown in Figs. 44(a) and (b) are assumed. First, at a certain time, the spread code Ck is supplied to the transmission conductors ¥ and Yn+1 (the state of Fig. 44 (a)). However, after a certain period of time has elapsed, the spread spectrum code Ck is supplied to the transmission conductors Υn + 2 and Υη + 3 (the state of FIG. 44(b)), and is not particularly illustrated, but The transmission conductor 12 supplied with the spread spectrum code Ck is sequentially switched to the transmission conductors Yn + 4 and Yn + 5, the transmission conductors Yn + 6 and Υη + 7·", and if it is - directly supplied to the specific At the conductor, it returns to the original signal conductor Υ, and γη + 丨, and then the above switching is repeated. -88- 201122922 The pick-up is described with reference to Fig. 45' for the case where the signal conductor 12 is switched one at a time. Specifically, as shown in Fig. 45 (a) to (c), it is assumed that first, at a certain time, the spread spectrum code is supplied to the transmission conductors γη and γη+ι (Fig. 45 ( a) state). However, after a certain period of time has elapsed, the spread spectrum code Ck is supplied to the transmission conductors Υn+| and Υη+2 (the state of FIG. 45(b)), and after a lapse of a certain time, the spread code Ck After being supplied to the transmission conductors Υn + 2 and Υη + 3 (the state of FIG. 45(c)), although not specifically illustrated, the transmission of the spread spectrum code ck is sequentially supplied. The conductor 12 is switched to the transmission conductor eight +3 and Υη + 4, the transmission conductor Υη + 4 and Υη"...', and if the spreading code (^ is supplied to the specific conductor), the system returns to the original transmission. The conductor Υη and γη+ι are then repeatedly switched as described above, that is, in the switching example shown in Figs. 45(a) to (c), 'at each specific time, with a specific root The number (in this case, 2) units are selected for the signal conductor 12 that supplies the same spread code ck, and 'is used to make a plurality of transmissions selected in the previous selection action. The signal conductor 12 of one of the conductors 12 (one in the example shown in Fig. 45) is also used as the next selection operation. The number of the transmission conductors I2 is selected and controlled. [Modification 1 5] In the above-described Modifications 1 and 3, the same exhibition is provided for the adjacent two transmission conductors. The frequency code is exemplified by the case where one amplifier amplifies the output signals of the adjacent two received conductors. However, the present invention is not limited thereto. For example, -89-201122922 can be configured as follows: that is, the transmitting unit supplies the same spreading code to the plurality of transmitting conductors arranged at a specific number of intervals and receives the signal Similarly, the output signal output from a plurality of signal conductors arranged at a specific number of intervals is amplified by an amplifier. One example is shown in FIG. 46 (Modification 15) In the modification 15 described above, instead of the differential amplifier 250 provided at the amplifying circuit 2 3 2 shown in FIG. 39, at the amplifying circuit 232 of the receiving unit 310, the use and supply are provided. The same spread spectrum code (^ the number of the transmission conductors I2 is the same and For the amplifier of the input terminal of the same polarity, for example, an amplifier 316 having two inputs and one output having two "+" terminals is used. The other configuration is the same as that of the above-described modification 14. Therefore, the description will be made with reference to Fig. 1 and Fig. 39 as appropriate, and the description of the common configuration will be omitted. Fig. 46 is a view schematically showing a configuration in which the following is provided: Between the two transmission conductors of the same spread spectrum code, there is a transmission conductor connected to the ground, and the receiver receives the signal from the two by one amplifier. The output signal from the conductor is amplified, and between the two signal conductors, there is a signal conductor connected to the ground. Specifically, as shown in Fig. 46, the transmission conductor selection circuit 22 (refer to Fig. 1) selects any two of the transmission conductors Yn + 1 and Υ η + 3 . On the other hand, the spread code generating circuit 2 1 of the transmitting unit 200 supplies the same spreading code Ck to the selected two transmitting conductors Υη+1 and Υη + 3 . At the same time, the transmission conductor selection circuit 22' is to be supplied with the transmission conductors other than the transmission conductors Yn+1, Yn+3 of the spread code Ck 12-90-201122922 (that is, the transmission conductor) Yn ' Υ η + 2 and the remaining signal conductors are connected. Similarly, the received conductor selection circuit 23 of the signal receiving unit 310 is a pair of two received conductors Xm, Xm + 2 and one. The input terminal is connected to the 'amplifier 361' to amplify the output signal from the connected conductor Xm, Xm + 2 . At the same time, the received conductor Xm, Xm + 2 conductors (specifically, the received conductors Xm+l, Xm + 3 and the remaining conductor 14) connected to the amplifier 361 are connected to the ground. Further, the switching between the transmission and reception conductors 14 caused by the transmission conductor 22 and the reception conductor selection circuit 23, respectively, is the same as the switching shown in the above modification and FIG. Conducted in the ground. As described above, in the first modification, in the modification and the modification, the same spread-spectrum code amplifier 361 is supplied to the plurality of transmission conductors 12, and the input from the plurality of signal conductors 14 is added. Therefore, the detection range can be broadened, and the signal level can be increased, and the detection sensitivity can also be improved. Further, in the case of the fifth aspect, since the minimum detection range Smin can be expanded, it is suitable when the position detection area on the sensing portion is large. Further, in the first modification, in the above-described modification, the number of the transmission conductors that supply the same spread code and the number of selected signal conductors are equal to each other. The minimum detection area Smin is set to a square shape. As a result, it is connected with 12) (refer to the two of the figure 361//, and the other received signal selection circuit conductor 1 2 is the same as 1 4 (Fig. 44 1 3, and by Since the signal is detected, it is widened. Therefore, it is the same as the special modification of the sensing unit. The same as in the first modification of the sensing unit, in the minimum detection area on the sensing unit, The sensitivity distribution of the isotropic property is obtained. In this case, the opposing surface of the pointer can be detected as a circular shape even if the indicator body having a circular counter face is disposed on the sensing portion. Example 1 6] In addition, the current caused by the spread code Ck supplied to the signal conductor group 11 is compared with the current through the indicator body 19 when the pointer 19 is placed at the intersection. The amount of change in the output signal generated by the current flowing to the ground is extremely large. As shown in the above-mentioned Modifications 1 1 to 15 5, generally, if the signal level of the output signal is increased, the detection sensitivity system will Boost, however, the accuracy of detecting the amount of change in the output signal In order to maintain the accuracy of the detection, it is necessary to increase the resolution of the A/D conversion circuit 33 of the receiving unit 300 (refer to FIG. 1). However, if the A/D conversion circuit 3 is made When the resolution is improved, a new problem arises. That is, the scale of the A/D conversion circuit 3 is large, and the design system becomes difficult. In particular, when the same spread code is supplied to the plurality of transmissions. In the case of the conductor 12, this problem is more remarkable. Therefore, a modification 16 which is an embodiment for solving the above-described problems will be described with reference to Figs. 47 to 49. Here, Fig. 47, The schematic diagram of the modified example 16 and the waveform of the output signal output from the differential amplifier 'FIG. 48' are examples of the internal configuration of the transmission conductor selection circuit in the modification 16 of this modification. FIG. 49 is a diagram showing the configuration of the signal conductor selection circuit in the modification of the present invention. In the description of the modification 16, the indicator body is used as the indicator body. (The indicator 19 shown by the solid line in the figure) is placed in the transmission The change of the output signal in the case of the intersection between the conductors Yn + 2 and Xm+1 is exemplified. First, referring to Fig. 47 (a), the schematic configuration in the modification 16 is explained. Therefore, the difference between the modification 11 and the modification 16 is that the spread code supply circuit 2 1 that supplies the spread code Ck and the spread code Ck are selectively supplied to the transmission conductor. Two code invertors 381 are provided between the transmission conductor selection circuits 382 at the group 1 and a differential amplifier 386 with a 4-input and 1-output is used in the amplification circuit. The output signals from the four received conductors 14 are differentially amplified. The other configurations are the same as those of the modification 1 1 (refer to FIG. 1 and FIG. 39). Therefore, the same reference numerals are given to the same components, and the description thereof will be omitted. In the following description, the code inverted for the spread code Ck is described as the inverted code [Ck (reverse)]. The two code invertors 381 are code inverted from the spread code Ck supplied from the spread code supply circuit 2 1 and output as an output. The spread code Ck supplied from the spread code supply circuit 2 1 and the inverted code [Ck (reverse) output from the code inverter 381 are transmitted through the transmission conductor selection circuit 3 8 2 is supplied to the adjacent four communication conductors γn to γη + 4 . Specifically, the spread spectrum code Ck supplied from the spread spectrum code generating circuit 2 is supplied to the two signal conductors Yn + 2 and Yn + 3 via the transmission conductor selection circuit 382. And the 'spreading code Ck' is supplied to the -93 via the transmission conductor selection circuit 382 after being inverted by the code invertor 381 to the inverted code [Ck (reverse)]'. - 201122922 The transmission conductor Υη and 丫^+1. In addition, in the following description, the supply mode of the spread spectrum code shown in FIG. 47 is marked as "+" by the transmission conductor to which the spread code Ck is supplied, and will be supplied with the inverted code [ The signal conductor of Ck (reverse) is marked as "-". That is, the supply form of the signal as shown in Fig. 47 is marked as "...+ +". Next, the details of the transmission conductor selection circuit 382 will be described with reference to FIG. The transmission conductor group 1 is divided into 16 communication blocks 383 which are one group of 7 adjacent transmission conductors Yn to Yn + 6. The transmission conductor selection circuit 382 is, for example, a well-known logic circuit and is constituted by the same number (16) of switch groups 382a as the number of each transmission block 383. Each of the transmission blocks 3 8 3 is a transmission conductor 12 and a phase of three of the transmission conductors Yn to Yn + 6 constituting the seven of the transmission blocks 838 The other communication blocks in the neighborhood are shared. Specifically, as shown in FIG. 48, generally, three transmission conductors Υn + 4 to which the index number η of the transmission conductors Υn to Υπ + 6 constituting each of the transmission blocks 383 are the largest are obtained. Υη + 6 is shared with adjacent communication blocks. Each switch group 3 82a is composed of four switches 3 82a, 3 82a2, 3 8 2a3 and 3 82a4. The seven terminals 3 8 2b on the output side of each switch group 3 82a are connected to the corresponding signal conductors Yn to Yn + 6, respectively. However, among the four switches 3 82ai, 3 8 2a2, 3 82a3, and 3 82a4, the switches 3 8 2 a > and the input terminals 3 8 2 c of 3 8 2 a2 are via the code inverter 3 8 1 is connected to each of the spread code generation circuits 24 (refer to FIGS. 1 and 4) of the spread code supply circuit 21, and the input terminals 3 82c of the switches 3 8 2a3 and 3 8 2 a4 are -94-201122922 Connected to each of the spread code generation circuits 24 of the spread code supply circuit 21, and as shown in Fig. 48, for example, is supplied with the code ck and the inverted code of the spread code C k [ck ( Inverting the switch group, the spread code ck is supplied to the signal conductors Yn + 2 and Yn+3, and the inverted code [Ck (reverse)] is supplied to the signal conductor Υη and Υη+1. After the specific supply of the spread code ck and the inverted code [Ck (reverse)] is made, the broadcast 12 connected to the spread code supply circuit 21 is switched, and the spread spectrum is spread. The code (^ is supplied to the transmission conductors γη + 3 and γ ' and the inversion code [Ck (reverse)] is supplied to the transmission conductor γη+1 Υη + 2. Then, it is time-lapsed to be spread and spread. Code for The circuit 2 1 is connected to the transmission conductor for switching, and supplies the spread code Ck to the transmissions Yn + 5 and Yn + 6 and supplies the inverted code [Ck (reverse)] to the carrier Yn + 3 And after Yn + 4, the spread spectrum code is again supplied to the donors Υ η + 2 and Υ η + 3, and the inverted code [Ck (reverse)] is supplied to the signal conductors γη and Yn+1, after which The above operation is repeated. As described above, the spread spectrum supplied from the spread spectrum code supply circuit 21 and the inverted code [Ck (reverse)] are supplied to all of the transmission conductor groups. Next, referring to Fig. 47 (a) and Fig. 49, the details of the received conductor selection circuit 384 in the deformation will be described. As shown in Fig. 49, the received conductor selection circuit is generally shown. 3 84, , is provided with a switch group 3 84a formed by four switches. The input terminals 3 8 4b of the open 3 84a are respectively connected to the corresponding signal conductors. Further, the switch group 3 84a The output terminal 3 84c of each switch is spread over 3 8 2a and , and the time conductor η + 4 and the connected conductor signal guide For example, the example 16 of the same code C)c 11 is connected to the input terminal of the Ι/V conversion circuit 385a of the corresponding one of the -95-201122922 amplifier circuit 385. Further, the switch group 3 84a switches the signal conductor 14 connected to the 1/V conversion circuit 3 8 5 a at a specific time interval. Then, the output signal from each of the received conductors 14 is converted into a voltage signal by the Ι/V conversion circuit 385a, and is input to a differential amplifier 386 which will be described later. Further, in Fig. 49, in order to avoid complication of the drawing, the description of the plural 1/V conversion circuit 3 85a and the switch group 3 84a is omitted. The amplifying circuit 385 is composed of four Ι/V converting circuits 385a and a differential amplifier 386. As shown in Fig. 49, in general, the 1/V conversion circuit 3 8 5a connects its input terminal to the output terminal 3 84c of each switch constituting the switch group 3 84a, and its output terminal is described later. The input terminals of the differential amplifier 386 are connected. The differential amplifier 386 is a 4-input 1-output differential amplifier. The differential amplifier 386 is provided between the Ι/V conversion circuit 385a and the A/D conversion circuit 33 (refer to FIG. 1). Among the four input terminals, the polarity of the two input terminals on the left side is It becomes "+", and the polarity of the two input terminals on the right side is "-". That is, in the four received signal conductors X, n to Xm + 3 selected by the signal conductor selection circuit 384, the index marks m are two smaller signal conductors Xm and Xm. The polarity of the input terminal to which +1 is connected is set to "+", and the polarity of the input terminal of the connected conductor Xm + 2 and Xm + 3 to which the index number m is two is connected. set as"-". Then, the differential amplifier 3 86 is converted into a voltage signal at the Ι/V conversion circuit 3 8 5 a and is output as a differential signal -96 - 201122922. Further, the received conductor selection circuit 3 84 performs the same selection switching as that of the modification 4 (refer to Fig. 31). Specifically, the switch group 3 84a of the received conductor selection circuit 3 84 is firstly transmitted from the signal conductors X! to X4 of the minimum index number, and sequentially receives the signal conductors Xm to Xm + 3 and the differential. The "+" terminal and the "-" terminal of the amplifier 386 are connected (the state of Fig. 49). That is, the "+" terminals of the two differential amplifiers 386 are connected to the signal conductors Xi and X2, respectively, and the two "-" terminals are connected to the signal conductors X3 and x4, respectively. Then, if a specific time elapses, the switch group 384a of the received conductor selection circuit 384 switches the signal conductor 14 connected to the amplifier circuit 386 to the position in the direction in which the index mark m increases. The conductor, that is, the signal conductor and X3 are connected to the "+" terminal of the differential amplifier 386, and the signal conductors X4 and X5 are connected to the "-" terminal of the differential amplifier 386. However, after this switching, a new output signal is obtained from the received conductors X2 to X5 connected to the switch group 3 82a. Thereafter, the switch group 3 84a of the signal conductor selection circuit 384 is switched at a specific time interval to the signal conductor 14 connected to the differential amplifier 386, and is finally After the four connected signal conductors X128 to Xl31 are connected to the differential amplifier 386, they return to the initial state, that is, return to the state shown in FIG. 49, and then repeat the above operation. .
而，差動放大器386，係在上述之每一切換時，對於 所輸入之從受訊導體14而來的輸出訊號作差動放大，並輸 出至後段之A/D變換電路33處（參考圖1)。之後，在A -97- 201122922 /D變換電路33中而被作了數位變換之輸出訊號，係在相 關値算出電路34中而被作相關演算，並將身爲此相關演算 之結果的相關値記憶在相關値記憶電路34d中（參考圖8 ) 。另外，在以下之說明中，係對於此圖49中所示之差動放 大電路3 8 6的受訊形態，而將被與差動放大電路之「+」端 子作連接的受訊導體標記爲「+」，並將被與「-」端子作 連接的受訊導體標記爲「- j 。亦即是，如同此圖49中所 示一般之訊號的受訊形態，係被標記爲「+ + --」。 接著，參考圖47(b)，針對當如同上述一般而對於 被與差動放大器3 86之4個的輸入端子相連接之受訊導體作 了切換的情況時之輸出訊號的位移作說明。於此，此圖47 (b )中之以點線所表示的曲線3 80，係爲當對於被與差動 放大器3 86之4個的輸入端子相連接之受訊導體從索引標號 m爲最小的受訊導體起而依序作了切換時，從差動放大器 3 8 6所輸出之輸出訊號的波形，曲線3 8 0X，係爲對於從差 動放大器386而來之輸出訊號作了積分後之波形。另外， 以下，爲了方便說明，係將差動放大器3 8 6之4個的輸入端 子，從被與受訊導體之索引標號爲大之側相連接之輸入端 子起來依序稱爲輸入端子386a〜386d。 若是如同上述一般，而使受訊導體選擇電路384對於 被與差動放大器386之輸入端子386a〜386d相連接之受訊 導體14作切換，則，首先，當被連接在差動放大器386之 輸入端子386a〜386d處之受訊導體14係存在於完全不會受 到指示體19之影響的位置處時，從差動放大器3 86而來之 -98 - 201122922 輸出訊號係成爲0 (圖47(b)之380a)。 接著，由於係從被與差動放大器386之輸入端子386a 作了連接的受訊導體14起而接近指示體19’因此’輸入至 差動放大器386之「-」端子處的訊號係逐漸地減少。其結 果，從差動放大器3 86而來之輸出訊號’係朝向正側而震 盪（圖47(b)之3 80b)。之後，若是受訊導體選擇電路384 對於被與差動放大器3 8 6作連接之受訊導體14作切換’則 由於被連接於差動放大器386之輸入端子386a以及38 6b處 的受訊導體係接近指示體19，因此，從差動放大器386而 來之輸出訊號係更進而朝向正側震盪。而，從此差動放大 器386而來之輸出訊號的訊號準位，係當指示體19所被放 置之位置成爲位置在被連接於差動放大器3 86之輸入端子 3 86c以及3 8 6d處的受訊導體之間時，而成爲最大（圖47(b) 之 3 8 0c )。 接著，若是受訊導體選擇電路3 84對於被與差動放大 器3 86之輸入端子3 86a〜3 86d作連接之受訊導體14作切換 ，則由於被連接於差動放大器3 86之輸入端子3 8 6a以及 3 86b處的受訊導體14係逐漸遠離指示體19，並且，被連接 於差動放大器386之輸入端子386c以及386d處的受訊導體 係接近指示體19，因此，被輸入至差動放大器386之「+」 端子處的訊號係逐漸地減少，並且，被輸入至「-」端子 處之訊號係逐漸地增加。其結果，從差動放大器3 8 6而來 之輸出訊號，係朝向負側而震盪（圖47(b)之3 80d )。 而，差動放大器386之輸出訊號，當指示體19位置在 -99 - 201122922 被連接於輸入端子386c處之受訊導體與被連接於輸入端子 38 6b處之受訊導體之間時’被輸入至差動放大器386之「+ 」端子處的訊號係最爲減少。其結果，從差動放大器3 8 6 而來之輸出訊號，係最爲減少（圖47(b)之3 80e )。 而後，若是進而使受訊導體選擇電路3 8 4進行被與差 動放大器386之輸入端子386a〜386d相連接之受訊導體14 的切換，則被與差動放大器386之輸入端子3 86a〜3 8 6d相 連接之受訊導體14，由於係均爲逐漸遠離指示體19，因此 ，被輸入至差動放大器386之「+」端子處的訊號係逐漸地 增加，故而，從差動放大器3 86而來之輸出訊號亦逐漸地 增加（圖47(b)之38 Of)，而若是被與差動放大器386之輸 入端子3 8 6a〜3 8 6d相連接之受訊導體14係被切換至位於不 會受到指示體1 9之影響的位置處之受訊導體，則從差動放 大器386而來之輸出訊號係成爲0 (圖47(b)之380g)。 若是對於從以上之差動放大器386而來的輸出訊號之 準位位移作圖示，則係成爲如同圖47 ( b )中之以點線所 示的曲線380 —般。而，若是對於此差動放大器386而來的 輸出訊號作積分，則係得到如同此圖47 ( b )中之以實線 所示的曲線3 80X。而後，藉由對於此曲線3 80X之凹陷部 分的重心作演算，指示體1 9之位置係被檢測出來。 另外，此圖47 ( b )中所展示之從差動放大器3 86而來 的輸出訊號以及對於此輸出訊號作了積分後之値，係爲當 指示體19被放置在正被供給有展頻碼Ck之送訊導體12與受 訊導體1 4之間的交叉點處的情況時之輸出特性，當此指示 -100- 201122922 體1 9係被放置在正被供給有反轉碼〔Ck(反轉）〕的送訊導 體1 2與受訊導體1 4之間的交叉點處的情況時（例如，在圖 47 ( a )中以點線所示之指示體19所被放置的送訊導體Yn 與受訊導體Xm+1之間的交叉點），從差動放大器3 8 6而來 之輸出訊號，係成爲與上述之輸出特性相反的特性。 在使用有此變形例1 6中所示之構成例的情況時，係能 夠並不使電路規模變大地而將檢測精確度作維持，並且， 能夠使從差動放大器3 80所輸出之差分訊號增大，並且， 同時性檢測出之範圍亦變廣，因此，亦能夠使檢測感度提 升。又，於此變形例16中，由於係設爲將展頻碼Ck及其之 反轉碼〔Ck(反轉）〕供給至送訊導體I2處之構成，因此， 當並不存在有指示體19的狀況下，由於此展頻碼Ck及反轉 碼〔Ck(反轉）〕係相互抵消，因此，能夠抑制差動放大器 386之輸出訊號以及A/D變換電路之輸入訊號的動態範圍 ，進而，亦能夠將雜訊抵消，故而，係能夠將雜訊耐性提 升。 又’此變形例1 6，係與變形例1 4相同的，將被供給有 相同之展頻碼Ck的送訊導體12以及被供給有將此展頻碼Ck 作了碼反轉的反轉碼〔Ck(反轉）〕之送訊導體12的總數， 設爲與被連接於差動放大器386處之受訊導體14的根數相 同。其結果’在此變形例1 6之構成中，在感測部上之最小 的檢測區域Smin ’亦係成爲正方形狀。其結果，與變形例 1 4相同的’在感測部上之最小檢測區域中，係能夠得到等 向性之感度分布。於此情況，例如就算是在感測部上被配 201122922 置有對向面爲圓形狀之指示體，亦能夠將該指 面檢測爲圓形狀。 另外，在上述變形例1 6中，雖係針對將被 放大器3 8 6處之受訊導體的根數設爲了 4根（偶 作了例示說明，但是，此被作連接之受訊導體 並不被限定於4根。例如，此被作連接之受訊 ，係亦能夠以3根或者是5根（奇數）作爲單位 ，如同上述變形例1 2中所示一般，以將被選擇 之受訊導體中的被配置在中央之送訊導體連接 是參考電壓處爲理想。此係因爲，藉由此，就 體並未被作充分之接地的情況時，亦能夠經由 中央之受訊導體來將電流的一部份作分流，而 度的降低作抑制之故。 進而，在此變形例1 6中，雖係針對在索弓 之送訊導體12處供給反轉碼〔Ck(反轉）〕，並] 較大之送訊導體處供給展頻碼的情況而作了例 是’本發明係並不被限定於此。例如，亦可設 號η較小之送訊導體12處供給展頻碼Ck，並在5 大之送訊導體處供給反轉碼〔Ck(反轉）〕。同 針對將索引標號較小之受訊導體14連接於差重 之「+」端子處，並將索引標號m較大之受訊導 差動放大器386之「-」端子處，來進行差動放 而作了說明’但是’亦可將索引標號m較小之 接於「-」端子處’並將索引標號m較大之受訊 示體之對向 連接於差動 數）的情況 的根數，係 導體的根數 。於此情況 了的奇數根 於接地或者 算是當指示 此被配置在 能夠對於感 丨標號η較小 Ε索引.標號η 示說明，但 爲在索引標 f引標號η較 樣的，雖係 j放大器3 8 6 體14連接於 大器的情況 受訊導體連 導體連接於 -102- 201122922 「+」端子處。 〔變形例1 7〕 另外’在上述變形例i 6中，雖係針對將從展頻碼產生 電路2 1所供給之展頻碼c k、和身爲此展頻碼c ^之反轉碼的 反轉碼〔Ck(反轉）〕，以對於相鄰之4根送訊導體而讓相同 之碼相鄰接的方式來作供給的情況而作了例示說明，但是 ’本發明’係並不被限定於此情況。例如，亦可在相鄰之 4根的送訊導體Υη〜γη + 3中’對於位置在兩端處之送訊導 體Υη以及Υη + 3而供給展頻碼Ck或者是反轉碼〔Ck(反轉）〕 ’並對於位置在中央處之送訊導體Yn+1以及八+ 2而供給反 轉碼〔Ck(反轉）〕或者是展頻碼Ck。 根據圖5 0 ’針對變形例丨7之構成以及動作作說明。圖 5 0(a) ’係爲此變形例1 7之槪略構成圖，圖5 0 ( b )，係 爲從此變形例1 7中之差動放大器所輸出的輸出訊號之波形 圖。 此變形例1 7與上述之變形例1 6間的相異點，係在於： 展頻碼ck以及反轉碼〔ck(反轉）〕之供給形態，係成爲「-+ + -」，以及，4輸入1輸出之差動放大器396的受訊訊號14 之檢測形態，係成爲從受訊導體1 4之索引標號m較小者起 而以「- + + -」之順序來作配置。而，在相鄰接之4根的受 訊導體Xm〜Xm+3之中，將受訊導體Xm+1以及Xm + 2連接於差 動放大器3 96之「+」端子處，並將受訊導體Xm以及Xm + 3連 接於差動放大器3 96之「-」端子處。其他之構成以及動作 -103- 201122922 ，由於係爲與變形例16(參考圖1以及圖47〜圖49)成爲 相同之構成’因此’在相同之構成處，係附加相同之號碼 ，並省略其說明。 而，在此變形例1 7中，從展頻碼供給電路2 1 (參考圖 1 )所供給而來之展頻碼Ck，係被供給至被送訊導體選擇 電路382所選擇了的4根的導體丫„〜¥„ + 3中之位置在兩端處 的送訊導體Yn以及丫„ + 3處，而，在位置於中央處之送訊導 體Υη+1以及Υη + 2處，係被供給有將展頻碼Ck作了碼反轉的 反轉碼〔Ck(反轉）〕。 接著，參考圖47(b)，針對當如同上述一般而對於 被與差動放大器3 96之4個的輸入端子相連接之受訊導體作 了切換的情況時之輸出訊號的位移作說明。另外，以下， 爲了方便說明，係將差動放大器3 96之4個的輸入端子，從 被與受訊導體之索引標號m爲大之側相連接之輸入端子起 來分別依序稱爲輸入端子396a〜396d。 若是如同上述一般，而使受訊導體選擇電路3 84對於 被與差動放大器396之輸入端子396a〜396d相連接之受訊 導體14作切換，則，首先，當被連接在差動放大器396之 輸入端子3 96 a〜396 d處之受訊導體係存在於完全不會受到 指示體之影響的位置處時，從差動放大器3 96而來之輸出 訊號係成爲〇(圖50(b)之390a)。 接著，由於係從被與差動放大器3 96之輸入端子3 96a 作了連接的受訊導體14起而接近指示體19’因此’輸入至 差動放大器3 9 6之「-」端子處的訊號係逐漸地減少。其結 -104- 201122922 果，從差動放大器3 9 6而來之輸出訊號’係朝向正側而震 盪（圖47(b)之390b)。而後’若是受訊導體選擇電路384 對於被與差動放大器396作連接之受訊導體14作切換’則 由於被連接於差動放大器396之輸入端子396a處的受訊導 體係接近指示體19，並且’被連接於差動放大器396之輸 入端子396b處的受訊導體係接近指示體19，因此’被輸入 至「-」端子處之訊號係逐漸的增加’並且’被輸入至「+ 」端子處之訊號係逐漸的減少’因此’從差動放大器396 而來之輸出訊號係朝向負側震盪（圖50(b)之390c) ° 而，若是受訊導體選擇電路384對於被與差動放大器 396之輸入端子396a〜396d相連接之受訊導體更進而作切 換，則，被連接在差動放大器396之輸入端子396a以及 3 96b處的受訊導體係逐漸遠離指示體19，並且’差動放大 器396之輸入端子396c處之受訊導體係逐漸接近指示體19 。其結果，由於被輸入至差動放大器3 9 6之「+」端子處的 訊號係更進而減少’並且’被輸入至「-」端子處之訊號 係增加，因此，從差動放大器396而來之輸出訊號係更進 而減少。而’從此差動放大器396而來之輸出訊號的訊號 準位，係當指示體19所被放置之位置成爲位置在被連接於 差動放大器396之輸入端子396c以及396d處的受訊導體之 間時，而最爲減少（圖50(b)之3 8 0d)。 接著，若是受訊導體選擇電路384進而對於被與差動 放大器396之輸入端子396a〜396d作連接之受訊導體作切 換，則由於被連接於差動放大器3 96之輸入端子3 96 a、 -105- 201122922 396b以及396c處的受訊導體係逐漸遠離指示體19，並且’ 被連接於差動放大器396之輸入端子396d處的受訊導體係 接近指示體19，因此，被輸入至差動放大器3 96之「+」端 子處的訊號係逐漸地增加。其結果，從差動放大器396而 來之輸出訊號係朝向正側而震盪（圖50(b)之3 90d)，而’ 當被與差動放大器396之輸入端子396d相連接之受訊導體 最爲接近指示體19時，從差動放大器396而來之輸出訊號 的準位係最爲增加（圖50(b)之3 90e)。 而後，若是進而使受訊導體選擇電路3 84進行被與差 動放大器396之輸入端子396a〜396d相連接之受訊導體14 的切換，則被與差動放大器396之輸入端子3 96a〜396d相 連接之受訊導體，由於係均爲逐漸遠離指示體19，因此’ 被輸入至差動放大器396之輸入端子處的訊號係逐漸地增 加，而若是被與差動放大器3 96之輸入端子3 96a〜396d相 連接之受訊導體係被切換至位於不會受到指示體19之影響 的位置處之受訊導體，則從差動放大器396而來之輸出訊 號係成爲〇 (圖50(b)之3900 。 若是對於從以上之差動放大器3 96而來的輸出訊號之 準位位移作圖示，則係成爲如同圖50 ( b )中之曲線390 — 般。另外，此圖50(b)中所展示之從差動放大器3 96而來 的輸出訊號以及對於此輸出訊號作了積分後之値’係爲當 指示體19被放置在正被供給有展頻碼Ck之送訊導體12與受 訊導體1 4之間的交叉點處的情況時之輸出特性’當此指示 體19係被放置在正被供給有反轉碼〔Ck(反轉）〕的送訊導 -106- 201122922 體12與受訊導體14之間的交叉點處的情況時（例如，在圖 5〇 ( a )中以點線所示之指示體1 9所被放置的送訊導體Yn 與受訊導體Xm+1之間的交叉點），從差動放大器3 96而來 之輸出訊號，係成爲與上述之輸出特性相反的特性。 如同上述一般，從展頻碼供給電路所供給而來之展頻 碼Ck，係被供給至藉由送訊導體選擇電路3 8 2所選擇了的4 根的導體Yn〜Yn + 3中之位置在兩端處的送訊導體Yn以及 Υη + 3處，而，在位置於中央之送訊導體Υπ+Ι以及Υη + 2處， 係被供給有將展頻碼Ck作了碼反轉的反轉碼〔Ck(反轉）〕 ，又，在4輸入1輸出之差動放大器396的輸入端子處，相 鄰接之4根的受訊導體中，受訊導體Xm+1以及Xm + 2係被連 接於差動放大器3 96之「+」端子處，而受訊導體Xm以及 Xm + 3係被連接於差動放大器3 9 6之「-」端子處的情況時， 從差動放大器3 96所得到之輸出訊號，係成爲與進行了積 分處理後相同之輸出訊號。故而，當採用有此變形例1 7之 檢測形態的情況時，由於係並不需要進行積分處理，因此 ’在進行了積分處理的情況時所可能發生的雜訊之累積， 係成爲不會發生。又，由於係進行有差動放大處理，因此 ，係能夠將雜訊耐性作更進一步的提升。 又，在此變形例1 7中，由於係與上述之變形例1 4相同 的，設爲對於從與供給相同之展頻碼的送訊導體12之根數 相同數量的受訊導體Μ而來之輸出訊號作放大的構成，因 此’在感測部上之最小檢測區域Smin，係成爲正方形狀。 其結果，在感測部上之最小檢測區域中，係能夠得到等向 -107- 201122922 性之感度分布。於此情況，例如就算是在感測部上被配置 有對向面爲圓形狀之指示體，亦能夠將該指示體之對向面 檢測爲圓形狀。 另外，在上述之說明中，雖係針對將被連接於差動放 大器處之受訊導體的根數設爲了 4根（偶數）的情況作了 例示說明，但是，本發明係並不被限定於此。例如，亦能 夠將被連接於差動放大器處之受訊導體14的根數，設爲3 根或者是5根（奇數）。於此情況，如同上述變形例1 2中 所示一般，以將被選擇了的奇數根之受訊導體中的被配置 在中央之送訊導體連接於接地或者是參考電壓處爲理想。 〔變形例1 8〕 在上述變形例1 7中，雖係針對展頻碼和此展頻碼之反 轉碼的供給形態、以及從受訊導體而來之訊號的檢測形態 ，設定爲「- + + -」的情況而作了例示說明，但是，展頻碼 和此展頻碼之反轉碼的供給形態、以及從受訊導體而來之 訊號的檢測形態，係亦可設定爲「+--+」。以下，在圖5 1 中，針對設定爲此供給形態以及檢測形態並供給展頻碼以 及此展頻碼之反轉碼，而藉由差動放大器來對於受訊訊號 進行差動放大的情況作例示。 若是將此變形例1 8與變形例1 7作比較，則其兩者間之 相異點，係在於：將從展頻碼產生電路2 1所供給至送訊導 體處之展頻碼Ck作碼反轉的碼反轉器381，係以對於在藉 由送訊導體選擇電路3 82而被作了選擇之4根的送訊導體Yn -108- 201122922 〜Υη + 3中之位置在中央處之2根的送訊導體Υη + 1以及Υη + 2來 供給反轉碼的方式而被作了配置，以及，差動放大器397 之4個的輸入端子之極性，係從受訊導體14之索引標號m較 大者起而依序設定爲「+--+」。其他之構成，係成爲與變 形例1 7 (參考圖5 0 )相同之構成。 藉由此變形例1 8中所示之構成，亦能夠得到與變形例 1 7相同之效果。亦即是，由於係並不需要進行積分處理， 因此，在進行了積分處理的情況時所可能發生的雜訊之累 積，係成爲不會發生。又，由於係進行有差動放大處理， 因此，係能夠將雜訊耐性作更進一步的提升。進而，由於 係對於複數之送訊導體而供給相同之展頻碼以及將此展頻 碼作了碼反轉之反轉碼，並且，設爲對於從與供給此相同 之展頻碼的送訊導體之根數相同數量的受訊導體而來之輸 出訊號作放大的構成，因此，在感測部上之最小檢測區域 Smin，係成爲正方形狀。其結果，在感測部上之最小檢測 區域中，係能夠得到等向性之感度分布。於此情況，例如 就算是在感測部上被配置有對向面爲圓形狀之指示體，亦 能夠將該指示體之對向面檢測爲圓形狀。 在上述變形例16〜18 (參考圖47〜51)中，係對於將 藉由送訊導體選擇電路以及受訊導體選擇電路所選擇的送 訊導體以及受訊導體之根數設定爲偶數的情況而作了例示 說明。在以下之變形例1 9中，係根據圖5 2〜圖5 4，針對將 此被選擇之送訊導體以及受訊導體的根數設定爲奇數的情 況作說明。另外，在以下所說明之變形例1 9以及20中，受 -109- 201122922 訊導體群13係由130根之受訊導體14所構成。 〔變形例1 9〕 首先，根據圖52，針對變形例1 9之構成作說明。此圖 52，係爲在放大電路32(參考圖1)中使用3輸入1輸出之 差動放大器的情況時之指示體檢測裝置的槪略構成圖。 首先’根據圖1以及圖52，針對此變形例1 9中之槪略 構成作說明。在送訊部200 (參考圖1 )中，係具備有：將 展頻碼C k作供給之展頻碼供給電路2 1、和將從此展頻碼供 給電路2 1所供給而來之展頻碼Ck選擇性地供給至送訊導體 14處之送訊導體選擇電路4〇2、和被設置在展頻碼供給電 路21與送訊導’體選擇電路402之間並將從展頻碼供給電路 21所供給而來之展頻碼Ck作碼反轉並產生反轉碼〔ck(反 轉）〕而作輸出之碼反轉器401。此展頻碼匕以及反轉碼〔 Ck(反轉）〕，係經由送訊導體選擇電路4 02而被供給至相鄰 之3根的送訊導體Yn〜Yn + 2處。具體而言，從展頻碼產生 電路2 1所供給而來之展頻碼Ck，係經由送訊導體選擇電路 402而被供給至2根的送訊導體Yn以及γη + 2處，並且，該展 頻碼Ck，係在碼反轉器401處而被碼反轉爲反轉碼〔Ck(反 轉）〕’之後經由送訊導體選擇電路402而被供給至送訊導 體Yn+1處。亦即是，在此圖52中，展頻碼的供給形態，係 被標記爲「+-+」。另外，在此變形例19中，送訊部200的 其他之構成，由於係成爲與圖1中所示之第1實施形態相同 之構成，因此，係省略其說明。 -110- 201122922 接下來，參考圖53 ’對送訊導體選擇電路402之詳細 內容作說明。 送訊導體群11 ’係被區分爲將相鄰接之6根的送訊導 體作爲1個群組的15個送訊區塊403 °此送訊導體選擇電路 402，例如，係爲週知之邏輯電路’並由與各送訊區塊403 的數量同數量（16個）之開關群4〇2a所構成°各送訊區塊 4〇3，係成爲將構成該送訊區塊403之6根的送訊導體12中 之索引標號η爲最大的2根之送訊導體12與相鄰之其他的送 訊區塊403作共有的構成。具體而言，係如同此圖53中所 示一般，將構成各送訊區塊403之送訊導體Υη〜Υη + 5中之 索引標號η爲最大的2根之送訊導體Υη + 4以及Υη + 5與相鄰之 送訊區塊作共有。 各開關群402a，係由3個的開關402a,、402a2以及 402a3所構成。各開關群402a之輸出側之6個的端子402b， 係分別被與相對應之送訊導體Yn〜Yn + 5相連接。又，在此 3個的開關402a!、402a2以及402a3之中，開關402a,以及 4〇2a3之輸入端子4〇2c，係被與將各展頻碼〜Cl6作供給 之展頻碼產生電路24(參考圖1以及圖4)相連接，而開關 4〇2a2之輸入端子4〇2c，係經由碼反轉器401而被與將各展 頻碼C,〜C, 6作供給之展頻碼產生電路η相連接。 而後，如同此圖5 3中所示一般，例如，被供給有展頻 碼匕以及此展頻碼（^之反轉碼〔Ck(反轉）〕的開關群4〇2a ’係將展頻碼Ck供給至送訊導體γη以及Υη + 2處，並且，將 反轉碼〔ck(反轉）〕供給至送訊導體八+ 1處。而，在將此 -111 - 201122922 展頻碼ck以及反轉碼〔Ck(反轉）〕作了特定時間之供給後 ’對於被與展頻碼供給電路24相連接之送訊導體12作切換 ’而將展頻碼匕供給至送訊導體Yn+1以及Yn + 3處，並且將 反轉碼〔Ck(反轉）〕供給至送訊導體Υη + 2處。之後，經時 性地對於被與各展頻碼供給電路24相連接之送訊導體作切 換，並在將展頻碼Ck供給至送訊導體γη + 5以及γη + 3處，且 將反轉碼〔Ck(反轉）〕供給至送訊導體γη + 4處之後，再度 地將展頻碼Ck供給至送訊導體γη以及γη + 2處，並且將反轉 碼〔Ck(反轉）〕供給至送訊導體γη+1處，之後，反覆進行 上述動作。如同上述一般，而將從展頻碼供給電路2 1所供 給而來之展頻碼Ck以及其之反轉碼〔Ck(反轉）〕供給至構 成送訊導體群11之全部的送訊導體12處。 接下來，參考圖1、圖52以及圖54，針對在變形例19 中之受訊導體選擇電路8 1 3之詳細內容作說明。如同此圖 54中所示一般，在此變形例19中之受訊部320，係由受訊 導體選擇電路813、和放大電路32、和A/D變換電路33、 和相關値算出電路3 4、以及位置算出電路3 5所構成。 受訊導體群13，係被區分爲43個的檢測區塊3 3 6。此 檢測區塊3 3 6，係藉由相鄰接（索引標號m爲連續）之3根 的受訊導體Xm〜Xm + 2所構成。構成各檢測區塊3 3 6之受訊 導體Xm〜Xm + 2，係被與相鄰接之其他的檢測區塊3 3 6作共 用。具體而言，在此變形例1 9中，受訊導體群1 3，係被分 割爲檢測區塊{ Xi〜X3 } 、 { X2〜X4 } ..... { X127〜The differential amplifier 386 differentially amplifies the input signal from the received conductor 14 during each of the above-mentioned switching, and outputs it to the A/D conversion circuit 33 of the subsequent stage (refer to the figure). 1). Thereafter, the output signal digitally converted in the A-97-201122922/D conversion circuit 33 is correlated in the correlation calculation circuit 34, and is related to the result of the correlation calculation. It is stored in the associated memory circuit 34d (refer to Figure 8). Further, in the following description, for the received form of the differential amplifying circuit 386 shown in FIG. 49, the received conductor connected to the "+" terminal of the differential amplifying circuit is marked as "+", and the signal conductor connected to the "-" terminal is marked as "-j. That is, the signaled form of the signal as shown in Figure 49 is marked as "+ + --". Next, referring to Fig. 47 (b), the displacement of the output signal when the signal conductor connected to the input terminals of the differential amplifiers 386 is switched as described above will be described. Here, the curve 380 indicated by the dotted line in FIG. 47(b) is such that when the signal conductor connected to the input terminals of the differential amplifiers 386 is minimized from the index mark m. When the received conductors are sequentially switched, the waveform of the output signal output from the differential amplifier 386, the curve 380X, is obtained after integrating the output signals from the differential amplifier 386. Waveform. In the following description, for convenience of explanation, the input terminals of the four differential amplifiers 186 are sequentially referred to as input terminals 386a from the input terminals connected to the larger side of the index of the signal conductor. 386d. If, as in the above, the signal conductor selection circuit 384 switches the signal conductor 14 connected to the input terminals 386a to 386d of the differential amplifier 386, first, when connected to the input of the differential amplifier 386 When the signal conductor 14 at the terminals 386a to 386d is present at a position that is not affected by the indicator 19 at all, the output signal from the differential amplifier 386 is -98 - 201122922 becomes 0 (Fig. 47 (b ) 380a). Then, since it is close to the indicator 19' from the signal conductor 14 connected to the input terminal 386a of the differential amplifier 386, the signal input to the "-" terminal of the differential amplifier 386 is gradually reduced. . As a result, the output signal from the differential amplifier 386 is oscillated toward the positive side (Fig. 47(b) 3 80b). Thereafter, if the received conductor selection circuit 384 switches the signal conductor 14 connected to the differential amplifier 386, it is connected to the signal receiving system at the input terminals 386a and 38 6b of the differential amplifier 386. The indicator body 19 is approached, so that the output signal from the differential amplifier 386 is further oscillated toward the positive side. The signal level of the output signal from the differential amplifier 386 is such that the position at which the indicator 19 is placed becomes the position at the input terminals 3 86c and 3 8 6d connected to the differential amplifier 386. When the conductor is between the conductors, it becomes the largest (Fig. 47(b) 380c). Next, if the received conductor selection circuit 384 switches the signal conductor 14 connected to the input terminals 3 86a to 86d of the differential amplifier 386, it is connected to the input terminal 3 of the differential amplifier 386. The signal conductors 14 at 8 6a and 3 86b are gradually away from the indicator 19, and the signal receiving system connected to the input terminals 386c and 386d of the differential amplifier 386 is close to the indicator 19, and thus is input to the difference The signal at the "+" terminal of the amplifier 386 is gradually reduced, and the signal input to the "-" terminal is gradually increased. As a result, the output signal from the differential amplifier 386 is oscillated toward the negative side (3, 80d of Fig. 47(b)). The output signal of the differential amplifier 386 is input when the position of the indicator 19 is connected between the signal conductor at the input terminal 386c and the signal conductor connected to the input terminal 38 6b at -99 - 201122922. The signal at the "+" terminal of the differential amplifier 386 is the most reduced. As a result, the output signal from the differential amplifier 386 is the most reduced (Fig. 47(b) 3 80e). Then, if the signal conductor selection circuit 384 is further switched by the signal conductor 14 connected to the input terminals 386a to 386d of the differential amplifier 386, the input terminal 3 86a to 3 is connected to the differential amplifier 386. Since the signal conductors 14 connected to the 6d are gradually separated from the indicator 19, the signal input to the "+" terminal of the differential amplifier 386 gradually increases, so that the differential amplifier is 86. The output signal is gradually increased (38 Of Figure 47(b)), and the signal conductor 14 connected to the input terminals 3 8 6a to 3 8 6d of the differential amplifier 386 is switched to be located. The output signal from the position of the differential amplifier 386 becomes 0 (380g of Fig. 47(b)). If the displacement of the output signal from the above differential amplifier 386 is plotted, it is similar to the curve 380 shown by the dotted line in Fig. 47 (b). However, if the output signal from the differential amplifier 386 is integrated, a curve 3 80X as shown by the solid line in Fig. 47 (b) is obtained. Then, by calculating the center of gravity of the depressed portion of the curve 3 80X, the position of the pointer 19 is detected. In addition, the output signal from the differential amplifier 386 shown in FIG. 47(b) and the integration of the output signal are obtained when the indicator 19 is placed in the spread spectrum being supplied. The output characteristic at the intersection between the signal conductor 12 and the signal conductor 14 at the intersection of the signal conductor 12, when the indication -100-201122922 body 1 9 is placed is being supplied with the inverted code [Ck( When the intersection of the signal conductor 1 2 and the signal conductor 14 is reversed (for example, the signal is placed on the indicator 19 as indicated by the dotted line in Fig. 47 (a) The output signal from the differential amplifier 386 is the intersection of the conductor Yn and the received conductor Xm+1, which is the opposite of the above-described output characteristics. When the configuration example shown in the modification 16 is used, the detection accuracy can be maintained without increasing the circuit scale, and the differential signal output from the differential amplifier 380 can be made. The increase is also widened, and the range of detection is also widened. Therefore, the detection sensitivity can be improved. Further, in the modification 16, since the spread code Ck and the inverted code [Ck (reverse)] are supplied to the transmission conductor I2, the indicator body does not exist. In the case of 19, since the spread code Ck and the inverted code [Ck (reverse)] cancel each other, the output signal of the differential amplifier 386 and the dynamic range of the input signal of the A/D conversion circuit can be suppressed. Further, the noise can be canceled, and therefore, the noise resistance can be improved. Further, in the same manner as the modification 14, the transmission conductor 12 to which the same spread code Ck is supplied and the reverse of the code inversion of the spread code Ck are supplied. The total number of the signal conductors 12 of the code [Ck (reverse)] is set to be the same as the number of the signal conductors 14 connected to the differential amplifier 386. As a result, in the configuration of the modification 16 described above, the smallest detection area Smin' on the sensing portion is also square. As a result, the sensitivity distribution of the isotropic property is obtained in the smallest detection area on the sensing unit as in the modification 14. In this case, for example, even if the sensor unit is provided with a pointing body having a circular counter face, the finger surface can be detected as a circular shape. Further, in the above-described Modification No. 16, the number of the conductors to be received by the amplifier 386 is four (oddly exemplified, but the signal conductor to be connected is not It is limited to four. For example, the signal to be connected can also be used as a unit of 3 or 5 (odd number), as shown in the above modification 12, to be selected. It is desirable that the centrally connected signal conductor connection in the conductor is a reference voltage. This is because, if the body is not sufficiently grounded, it can also be transmitted via the centrally received conductor. A part of the current is shunted, and the degree of decrease is suppressed. Further, in this modification 16, the reverse code [Ck (reverse)] is supplied to the signal conductor 12 of the cable bow. And the case where the larger transmission conductor is supplied with the spread spectrum code is exemplified by the present invention. The present invention is not limited thereto. For example, the transmission conductor 12 having a small number η may be provided at the spread spectrum. Code Ck, and supply the inversion code [Ck (reverse)] at the 5th transmission conductor. The signal conductor 14 having a smaller index number is connected to the "+" terminal of the differential weight, and the "-" terminal of the differential amplifier amplifier 386 having a larger index number m is differentially placed. Note that 'but' can also be the number of cases where the index number m is smaller than the "-" terminal and the direction of the receiver with a larger index number m is connected to the differential number. The number of roots. The odd number of roots in this case is grounded or it is said that this is configured to be smaller than the index η. The index η is shown, but the index η is similar to the index η, although it is a j amplifier. 3 8 6 When the body 14 is connected to the bulk, the conductor conductor is connected to the "+" terminal at -102- 201122922. [Modification 1 7] Further, in the above-described modification i6, the spreading code ck supplied from the spreading code generating circuit 2 1 and the inverted code of the spreading code c ^ are obtained. The reverse code [Ck (reverse)] is exemplified in the case where the same code is adjacent to the adjacent four transmission conductors, but the 'present invention' is not It is limited to this case. For example, it is also possible to supply the spread spectrum code Ck or the inverted code [Ck (for the transmission conductors Υn and Υη + 3 at both ends) in the adjacent four transmission conductors Υn to γη + 3 Invert))] and supply the inversion code [Ck (inversion)] or the spreading code Ck for the transmission conductors Yn+1 and 八+2 at the center. The configuration and operation of the modification 丨7 will be described based on Fig. 50'. Fig. 50(a)' is a schematic diagram of the modification of the modification 17 and Fig. 5(b) is a waveform diagram of the output signal output from the differential amplifier in the modification 17. The difference between the modification 17 and the above-described modification 16 is that the supply form of the spread code ck and the reverse code [ck (reverse)] is "-+ + -", and The detection mode of the received signal 14 of the differential amplifier 396 of the 4-input and 1-output is arranged in the order of "- + + -" from the smaller index mark m of the received conductor 14. And, among the adjacent four received conductors Xm to Xm+3, the received conductors Xm+1 and Xm + 2 are connected to the "+" terminal of the differential amplifier 3 96 and will be received. The conductors Xm and Xm + 3 are connected to the "-" terminals of the differential amplifier 3 96. The other configuration and the operation -103-201122922 are the same as the modification 16 (refer to FIG. 1 and FIG. 47 to FIG. 49). Therefore, in the same configuration, the same number is attached, and the same reference numeral is omitted. Description. Further, in the modification 17 described above, the spread code Ck supplied from the spread spectrum code supply circuit 2 1 (refer to FIG. 1) is supplied to the four selected by the signal conductor selection circuit 382. The conductor 丫„~¥„ + 3 is located at the two ends of the transmission conductor Yn and 丫 „ + 3, and at the center of the transmission conductor Υη+1 and Υη + 2, is The inverted code [Ck (inverted)] having the code inversion of the spread code Ck is supplied. Next, referring to FIG. 47(b), it is directed to four of the differential amplifiers 3 96 as described above. The displacement of the output signal when the input conductor connected to the input terminal is switched is explained. In addition, for convenience of explanation, the input terminals of the differential amplifier 3 96 are received and received. The index of the conductor, m, is the input terminal to which the large side is connected, and is referred to as the input terminal 396a to 396d, respectively. If the above is the same, the received conductor selection circuit 3 84 is connected to the input terminal of the differential amplifier 396. 396a~396d connected to the signal conductor 14 for switching, then, first, when connected When the signal receiving system connected to the input terminal 3 96 a to 396 d of the differential amplifier 396 is present at a position that is completely unaffected by the pointer, the output signal from the differential amplifier 3 96 becomes 〇 (390a of Fig. 50(b)) Next, since it is close to the indicator 19' from the signal conductor 14 connected to the input terminal 3 96a of the differential amplifier 3 96, it is input to the differential amplifier 3 The signal at the "-" terminal of 9 6 is gradually reduced. The result is -104-201122922. The output signal from the differential amplifier 3 9 is oscillated toward the positive side (390b of Fig. 47(b)). Then, if the received conductor selection circuit 384 switches the signal conductor 14 connected to the differential amplifier 396, the signal receiving system connected to the input terminal 396a of the differential amplifier 396 approaches the indicator 19, And the signal receiving system connected to the input terminal 396b of the differential amplifier 396 is close to the indicator 19, so the signal input to the "-" terminal is gradually increased 'and' is input to the "+" terminal. The signal is gradually reduced. Therefore, the output signal from the differential amplifier 396 is oscillated toward the negative side (390c of Fig. 50(b)). If the received conductor selection circuit 384 is connected to the differential amplifier When the signal conductors connected to the input terminals 396a to 396d of the 396 are further switched, the signal receiving system connected to the input terminals 396a and 3 96b of the differential amplifier 396 gradually moves away from the indicator 19, and 'differential The signal receiving system at the input terminal 396c of the amplifier 396 gradually approaches the indicator body 19. As a result, since the signal signal input to the "+" terminal of the differential amplifier 396 is further reduced and the signal input to the "-" terminal is increased, the differential amplifier 396 is derived from the differential amplifier 396. The output signal is further reduced. The signal level of the output signal from the differential amplifier 396 is such that the position at which the indicator 19 is placed becomes between the received conductors connected to the input terminals 396c and 396d of the differential amplifier 396. At the time, it is the most reduced (Fig. 50(b) 380d). Next, if the signal conductor selection circuit 384 further switches the signal conductor to be connected to the input terminals 396a to 396d of the differential amplifier 396, it is connected to the input terminal 3 96 a of the differential amplifier 3 96. 105- 201122922 The signal transmission system at 396b and 396c gradually moves away from the indicator 19, and the signal receiving system connected to the input terminal 396d of the differential amplifier 396 approaches the indicator 19, and thus is input to the differential amplifier. The signal at the "+" terminal of 3 96 is gradually increased. As a result, the output signal from the differential amplifier 396 oscillates toward the positive side (3, 90d of Fig. 50(b)), and 'when the signal conductor is connected to the input terminal 396d of the differential amplifier 396 When the pointer 19 is approached, the level of the output signal from the differential amplifier 396 is the most increased (Fig. 50(b) 3 90e). Then, if the signal conductor selection circuit 3 84 is further switched by the signal conductor 14 connected to the input terminals 396a to 396d of the differential amplifier 396, it is connected to the input terminals 3 96a to 396d of the differential amplifier 396. Since the connected conductors are gradually away from the indicator 19, the signal input to the input terminal of the differential amplifier 396 gradually increases, and if it is input terminal 3 96a of the differential amplifier 3 96 When the signal transmission system connected to the 396d is switched to the signal conductor located at a position that is not affected by the indicator 19, the output signal from the differential amplifier 396 becomes 〇 (Fig. 50(b) 3900. If the displacement of the output signal from the above differential amplifier 3 96 is shown, it is like the curve 390 in Figure 50 (b). In addition, in Figure 50(b) The output signal from the differential amplifier 3 96 and the integration of the output signal are shown when the indicator 19 is placed on the signal conductor 12 being supplied with the spread code Ck. The intersection between the conductors 14 The output characteristic at the time of the situation 'When the indicator body 19 is placed at the intersection of the body guide 12-201122922 body 12 and the signal conductor 14 to which the reverse code [Ck (reverse)] is being supplied In the case of a point (for example, the intersection between the signal conductor Yn and the signal conductor Xm+1 in which the pointer 19 is placed as indicated by a dotted line in Fig. 5(a)) The output signal from the amp 3 96 is opposite to the above-described output characteristics. As described above, the spread code Ck supplied from the spread code supply circuit is supplied to the transmission conductor. The four conductors Yn to Yn + 3 selected by the circuit 382 are located at the signal conductors Yn and Υη + 3 at both ends, and are located at the center of the transmission conductor Υπ+Ι and Υ η + 2 is supplied with a reverse code [Ck (reverse)] which inverts the spread code Ck, and is adjacent to the input terminal of the differential amplifier 396 of the 4-input 1 output. Among the four received conductors, the received conductors Xm+1 and Xm + 2 are connected to the "+" terminal of the differential amplifier 3 96, and are received. When the body Xm and Xm + 3 are connected to the "-" terminal of the differential amplifier 396, the output signal obtained from the differential amplifier 396 is the same as the output signal after the integration process. Therefore, when the detection mode of the modification 17 is employed, since the integration processing is not required, the accumulation of noise that may occur when the integration processing is performed is not performed. Occurs, and because of the differential amplification process, the noise tolerance can be further improved. Further, in the first modification, the same as the above-described modification 14, the same number of received conductors from the number of the transmission conductors 12 that supply the same spread code are used. Since the output signal is enlarged, the minimum detection area Smin on the sensing portion is square. As a result, in the minimum detection area on the sensing unit, the sensitivity distribution of the isotropic -107-201122922 can be obtained. In this case, for example, even if the pointing portion having the circular facing shape is disposed on the sensing portion, the opposing surface of the pointer can be detected as a circular shape. In the above description, the case where the number of the received conductors connected to the differential amplifier is four (even) is exemplified. However, the present invention is not limited to this. For example, it is also possible to set the number of the received conductors 14 connected to the differential amplifier to three or five (odd). In this case, as shown in the above-described Modification 12, it is preferable to connect the centrally disposed signal conductor to the ground or the reference voltage among the odd-numbered signal conductors to be selected. [Modification 18] In the above-described Modification No. 17, the supply pattern of the spread code and the inverted code of the spread code, and the detection form of the signal from the signal conductor are set to "-". The case of + + -" is exemplified, but the supply pattern of the spread code and the inverted code of the spread code, and the detection form of the signal from the signal conductor can also be set to "+ --+". Hereinafter, in FIG. 51, for the case where the supply mode and the detection mode are set and the spread code and the inverted code of the spread code are supplied, the differential amplifier performs differential amplification on the received signal. Illustrative. If the modified example 18 is compared with the modified example 17, the difference between the two is based on the spread code Ck supplied from the spread spectrum code generating circuit 21 to the transmitting conductor. The code inversion code invertor 381 is at the center of the position of the four transmission conductors Yn -108 - 201122922 ~ Υ η + 3 selected by the transmission conductor selection circuit 382 The two transmission conductors Υη + 1 and Υη + 2 are arranged to supply the inverted code, and the polarities of the four input terminals of the differential amplifier 397 are indexed from the received conductor 14. The larger the number m is, and the order is set to "+--+". The other configuration is the same as that of the modified example 17 (refer to Fig. 50). According to the configuration shown in the modification 18, the same effects as those of the modification 17 can be obtained. That is, since the integration processing is not required, the accumulation of noise that may occur in the case where the integration processing is performed does not occur. Further, since the differential amplification processing is performed, the noise resistance can be further improved. Further, since the same spreading code is supplied to the plurality of transmission conductors and the code is reversed by the code inversion of the spreading code, and the transmission is performed for the same spreading code as that supplied thereto. Since the output signal from the same number of conductors of the conductor is amplified, the minimum detection area Smin on the sensing portion is square. As a result, an isotropic sensitivity distribution can be obtained in the minimum detection area on the sensing unit. In this case, for example, even if the pointing portion having the opposite facing surface is disposed on the sensing portion, the opposing surface of the pointer can be detected as a circular shape. In the above-described Modifications 16 to 18 (refer to FIGS. 47 to 51), the number of the transmission conductors and the received conductors selected by the transmission conductor selection circuit and the signal conductor selection circuit is set to an even number. An illustration is given. In the following Modification 19, the case where the number of selected transmission conductors and the received conductors is set to an odd number will be described with reference to Figs. 5 2 to 54. Further, in the modifications 19 and 20 described below, the conductor group 13 is composed of 130 signal conductors 14 from -109 to 201122922. [Modification 19] First, the configuration of Modification 19 will be described with reference to Fig. 52. Fig. 52 is a schematic block diagram of the pointer detecting device in the case where a differential amplifier of three inputs and one output is used in the amplifying circuit 32 (refer to Fig. 1). First, the schematic configuration in the modification 19 will be described based on Fig. 1 and Fig. 52. The transmitting unit 200 (refer to FIG. 1) includes a spreading code supply circuit 2 1 for supplying the spread code C k and a spread spectrum supplied from the spread code supply circuit 2 1 . The code Ck is selectively supplied to the transmission conductor selection circuit 4'2 at the transmission conductor 14, and is disposed between the spread code supply circuit 21 and the transmission guide body selection circuit 402 and supplies the spread code from The spread code Ck supplied from the circuit 21 is code inverted by the code inversion and generates a reverse code [ck (reverse)]. The spread code 匕 and the inverted code [Ck (reverse)] are supplied to the adjacent three communication conductors Yn to Yn + 2 via the transmission conductor selection circuit 422. Specifically, the spread spectrum code Ck supplied from the spread spectrum code generating circuit 21 is supplied to the two transmission conductors Yn and γη + 2 via the transmission conductor selection circuit 402, and The spread code Ck is supplied to the transmission conductor Yn+1 via the transmission conductor selection circuit 402 after being inverted by the code inverting unit 401 to the inverted code [Ck (reverse)]. That is, in Fig. 52, the supply form of the spread spectrum code is marked as "+-+". In addition, in the modification 19, the other configuration of the transmitting unit 200 is the same as that of the first embodiment shown in Fig. 1, and therefore the description thereof will be omitted. -110- 201122922 Next, the details of the transmission conductor selection circuit 402 will be described with reference to Fig. 53'. The transmission conductor group 11' is divided into six adjacent communication conductors as one group of 15 transmission blocks 403. The transmission conductor selection circuit 402 is, for example, a well-known logic. The circuit 'is composed of the same number (16) of switch groups 4〇2a as the number of each transmission block 403. Each of the communication blocks 4〇3 is formed into 6 pieces of the communication block 403. The two transmission conductors 12 of the transmission conductor 12 having the largest index number n are shared with the adjacent other transmission blocks 403. Specifically, as shown in FIG. 53, generally, the two transmission conductors Υη + 4 and Υη which constitute the largest index η of the transmission conductors Υn to Υη + 5 of the respective transmission blocks 403 are the largest. + 5 is shared with adjacent communication blocks. Each switch group 402a is composed of three switches 402a, 402a2, and 402a3. The six terminals 402b on the output side of each switch group 402a are connected to the corresponding signal conductors Yn to Yn + 5, respectively. Further, among the three switches 402a!, 402a2, and 402a3, the input terminals 4〇2c of the switches 402a and 4〇2a3 are connected to the spread code generating circuit 24 for supplying the spread codes to Cl6. (refer to FIG. 1 and FIG. 4) are connected, and the input terminal 4〇2c of the switch 4〇2a2 is supplied with the spread code of each of the spread codes C, C, and 6 via the code inverter 401. The generating circuit η is connected. Then, as shown in this FIG. 5, for example, the switch group 4〇2a' to which the spread spectrum code 匕 and the spread code (the inverted code [Ck (reverse)] of the spread code is supplied will be spread. The code Ck is supplied to the transmission conductor γη and Υη + 2, and the inverted code [ck (reverse)] is supplied to the transmission conductor VIII + 1. However, in this -111 - 201122922 spread code ck And the reverse code [Ck (reverse)] is supplied to the transmission conductor Yn by switching the transmission conductor 12 connected to the spread code supply circuit 24 after the supply of the specific time. +1 and Yn + 3, and the inverted code [Ck (reverse)] is supplied to the transmission conductor Υη + 2. Then, it is connected to the respective spread code supply circuits 24 over time. The conductor is switched, and the spread code Ck is supplied to the signal conductors γη + 5 and γη + 3, and the inverted code [Ck (reverse)] is supplied to the signal conductor γη + 4, and then again. The spread code Ck is supplied to the transmission conductors γη and γη + 2, and the inverted code [Ck (reverse)] is supplied to the transmission conductor γη+1, and then repeated The above operation is performed. As described above, the spread code Ck supplied from the spread spectrum code supply circuit 21 and the inverted code [Ck (reverse) thereof) are supplied to all of the transmission conductor groups 11. Next, referring to Fig. 1, Fig. 52, and Fig. 54, the details of the received conductor selection circuit 813 in Modification 19 will be described. As shown in Fig. 54, The signal receiving unit 320 in the modification 19 is composed of a signal conductor selection circuit 813, an amplifier circuit 32, an A/D conversion circuit 33, an associated 値 calculation circuit 34, and a position calculation circuit 35. The received conductor group 13 is divided into 43 detection blocks 3 36. The detection block 3 3 6 is a three-way signal conductor Xm adjacent to each other (index number m is continuous). The structure is composed of ~Xm + 2. The signal conductors Xm to Xm + 2 constituting each of the detection blocks 3 3 6 are shared with other adjacent detection blocks 3 3 6 . In Example 19, the received conductor group 13 is divided into detection blocks { Xi~X3 }, { X2~X4 } ..... { X127~
Xl29)以及{X丨 28 〜Xl3〇}。 -112- 201122922 差動放大器405，係爲3輸入1輸出之差動放大 差動放大器405之3個的輸入端子，係將被與藉由受 選擇電路813而被作了選擇之3根的受訊導體Xm〜X 索引標號m爲最小之受訊導體Xm以及索引標號爲 Xm + 1作連接的輸入端子之極性設定爲「+」，並將 餘之1根的受訊導體Xm + 1作連接之輸入端子的極性 「-」。而。在此差動放大器405處’係使用進行有 之「-」端子處所輸入之訊號相較於從「+」端子所 訊號而作2倍的放大動作之差動放大器。此係因爲 變形例19之差動放大器405處，被連接於「-」端子 訊導體14的根數係爲1根，相對於此，被連接於「— 處之受訊導體1 4的根數係爲2根，因此，需要設爲 差動放大之訊號的準位成爲相同（差動放大後之輸 的準位成爲〇)的構成之故。而，差動放大器405 ’ 受訊導體14而來的輸出訊號作差動放大，並輸出至 A/D變換電路33處。另外，在圖54中，爲了避免 複雜化，係將複數之1/ V變換電路32a以及開關群I 載省略。又，受訊部3 2 0之其他構成，由於係爲與^ 形態（參考圖2 0 )成爲相同之構成，因此，針對相 成，係省略其說明。 受訊導體選擇電路8 1 3，係進行與變形例4 (參 )以及變形例1 6 (參考圖49 )相同之選擇切換。具 ，首先，此受訊導體選擇電路813之開關群815，係 索引標號之受訊導體L〜X3起，而依序將受訊導體 器。此 訊導體 m + 2中的 最大之 被與剩 設定爲 將從其 輸入之 ，在此 處之受 h J端子 使進行 出訊號 係將從 後段之 圖面的 5 1 5的記 g 2實施 同之構 考圖3 1 體而言 從最小 Xm以及 -114- 201122922 受訊導體選擇電路813，係具備有由3個的開關所成之 開關群8 1 5。此開關群8 1 5之輸入端子8 1 5a，係分別被與相 對應之受訊導體1 4相連接。又，開關群8 1 5之各別的輸出 端子815b，係被與I/V變換電路3 2a之輸入端子相連接。 而後，此開關群8 1 5，係以特定之時間間隔，來對於與1/ V變換電路32a相連接之檢測區塊3 3 6依序作切換。具體而 言，假設若是最初係將檢測區塊{ X,〜X3 }與後段之1/ V 變換電路32a作了連接，則，在下一個特定時間間隔中， 係切換爲將檢測區塊{ X2〜X/丨與I/V變換電路32a作連 接。之後，受訊導體選擇電路8 1 3，係以特定之時間間隔 來對於檢測區塊3W作切換，最後，係將檢測區塊{ X128 〜Xi }與1/ V變換電路32a作了連接，而後，係再度將 最初之檢測區塊{ Xt〜X3 }與後段之1/ V變換電路32a作 連接’之後，反覆進行上述動作。而，從各受訊導體14而 來的輸出訊號，係在1/ V變換電路32a處而被變換爲電壓 訊號，並被輸入至差動放大器405中。 放大電路32，係由3個的I/V變換電路32a和差動放大 器405所構成。各1/V變換電路32a之輸出端子，係分別被 與差動放大器40 5之各輸入端子作連接。於此，各ϊ/ν變 換電路32a ’係將被與索引標號m最小的受訊導體Xm作連 接的1/ V變換電路32a、和被與索引標號m最大之受訊導體 Xm + 2作連接的I/V變換電路32a，與差動放大器405之極性 爲「+」的輸入端子相連接，並將剩餘之I/V變換電路32a ’與差動放大器405之極性爲「-」的輸入端子相連接。 -113- 201122922Xl29) and {X丨 28 ~ Xl3〇}. -112- 201122922 The differential amplifier 405 is a three-input and one-output differential amplifier differential amplifier 405, and three input terminals are selected for the three selected by the selection circuit 813. The polarity of the input conductor of the signal conductor Xm to X with the smallest index conductor m and the index number Xm + 1 is set to "+", and the remaining one of the signal conductors Xm + 1 is connected. The polarity of the input terminal is "-". and. In the differential amplifier 405, a differential amplifier that performs an amplification operation in which the signal input at the "-" terminal is doubled compared to the signal from the "+" terminal is used. In this case, since the differential amplifier 405 of the nineteenth modification is connected to the "-" terminal conductor 14, the number of the conductors 14 is one, and the number of the received conductors 14 connected to the "-" is Since there are two, it is necessary to set the level of the signal for differential amplification to be the same (the level of the output after the differential amplification is 〇). However, the differential amplifier 405' receives the conductor 14 and The output signal is differentially amplified and output to the A/D conversion circuit 33. In addition, in Fig. 54, in order to avoid complication, the complex 1/V conversion circuit 32a and the switch group I are omitted. The other configuration of the receiving unit 320 is the same as that of the configuration (see FIG. 20). Therefore, the description is omitted for the phase. The receiving conductor selection circuit 8 1 3 performs The selection switching is the same as the modification 4 (reference) and the modification 16 (refer to FIG. 49). First, the switch group 815 of the received conductor selection circuit 813 is the index conductor L~X3. And the conductor will be received in sequence. The maximum and remaining settings of this conductor m + 2 Input from it, where the signal is transmitted from the h J terminal, the signal from the 5 1 5 of the posterior segment is implemented in the same manner as the figure 3 1 from the minimum Xm and -114 - 201122922 The received conductor selection circuit 813 is provided with a switch group 8 1 5 formed by three switches. The input terminals 8 1 5a of the switch group 8 1 5 are respectively associated with the received conductor 1 Further, the respective output terminals 815b of the switch group 8 1 5 are connected to the input terminals of the I/V conversion circuit 32a. Then, the switch group 8 1 5 is at a specific time interval. In order to switch the detection block 3 3 6 connected to the 1/V conversion circuit 32a in sequence, specifically, it is assumed that if the block is initially detected, the block { X, ~X3 } and the 1/V conversion circuit of the latter stage are detected. 32a is connected. Then, in the next specific time interval, the detection block {X2~X/丨 is connected to the I/V conversion circuit 32a. After that, the received conductor selection circuit 8 1 3 is connected. The detection block 3W is switched at a specific time interval, and finally, the detection block {X128~Xi} and 1/V are transformed. The circuit 32a is connected, and then the first detection block {Xt~X3} is connected to the 1/V conversion circuit 32a of the subsequent stage again, and then the above operation is repeated. From the respective signal conductors 14, The output signal is converted into a voltage signal at the 1/V conversion circuit 32a, and is input to the differential amplifier 405. The amplification circuit 32 is composed of three I/V conversion circuits 32a and a differential amplifier 405. Composition. The output terminals of the respective 1/V conversion circuits 32a are connected to the respective input terminals of the differential amplifier 40 5 . Here, each ϊ/ν conversion circuit 32a' is connected to the 1/V conversion circuit 32a connected to the received conductor Xm having the smallest index number m, and to the received conductor Xm + 2 having the largest index number m. The I/V conversion circuit 32a is connected to an input terminal of which the polarity of the differential amplifier 405 is "+", and the remaining I/V conversion circuit 32a' and the polarity of the differential amplifier 405 are "-". Connected. -113- 201122922
Xm + 2與差動放大器405之「+」端子作連接’並且’將受訊 導體xm + 1與「-」端子作連接（圖54之狀態）°亦即是’ 將差動放大器405之2個的「+」端子分別與受訊導體χι以 及Χ3作連接，並將「」端子與受訊導體Χ2作連接。接著 ，若是經過特定之時間’則受訊導體選擇電路8 1 3之開關 群815，係將被連接於放大電路4〇5處之受訊導體切換 爲位置在使其索引標號m增加之方向上的受訊導體，亦即 是，將受訊導體X2以及X4與差動放大器4〇5之「+」端子作 連接，並且將受訊導體X3與差動放大器405之「-」端子作 連接。而，在此切換後，從被連接於開關群8 1 5處之受訊 導體X2〜X4而得到新的輸出訊號。之後，受訊導體選擇電 路8 1 3之開關群8 1 5，係以特定之時間間隔’而依序對於被 連接於差動放大器405處之受訊導體Μ作切換’並在將身 爲最後被作連接之3根的受訊導體Χ128〜X13G與差動放大器 405作了連接後，再度回到最初之狀態、亦即是回到此圖 54中所示之狀態，之後，反覆進行上述動作。 而，差動放大器405，係在上述之每一切換時，對於 所輸入之從受訊導體Xm而來的輸出訊號作差動放大，並輸Xm + 2 is connected to the "+" terminal of the differential amplifier 405 and 'connects the received conductor xm + 1 to the "-" terminal (state of Fig. 54), that is, 'the differential amplifier 405 2 The "+" terminals are connected to the signal conductors χι and Χ3, respectively, and the "" terminal is connected to the signal conductor Χ2. Then, if the switch group 815 of the received conductor selection circuit 8 1 3 passes the specific time ', the signal conductor connected to the amplifier circuit 4〇5 is switched to the position in the direction in which the index mark m is increased. The signal conductors, that is, the signal conductors X2 and X4 are connected to the "+" terminals of the differential amplifiers 4'5, and the signal conductor X3 is connected to the "-" terminal of the differential amplifier 405. However, after this switching, a new output signal is obtained from the received conductors X2 to X4 connected to the switch group 8 1 5 . Thereafter, the switch group 8 1 5 of the received conductor selection circuit 8 1 3 is sequentially switched to the received conductor connected to the differential amplifier 405 at a specific time interval ' and is finally at the end After the three connected signal conductors 128 to X13G are connected to the differential amplifier 405, they return to the initial state, that is, return to the state shown in FIG. 54, and then repeat the above operation. . The differential amplifier 405 differentially amplifies the input signal from the received conductor Xm during each of the above switching operations, and inputs
出至後段之A/ D變換電路33處（參考圖1 )。之後，在A /D變換電路33中而被作了數位變換之輸出訊號，係在相 關値算出電路3 4中而被作相關演算，並將身爲此相關演算 之結果的相關値記億在相關値記憶電路3 4d中（參考圖8 ) 〇 若是如同此變形例1 9一般地而將輸出訊號之檢測形態 -115- 201122922 設爲「+-+」，則差動放大器405之3個的輸入端子之極性 的配置’係相對於中央之輸入端子的極性而成爲左右對稱 ’因此，與變形例1 7相同的，能夠得到與進行了圖5 0 ( b )中所示一般之位置檢測時的積分處理後相同之結果。故 而’在此變形例1 9中，亦能夠得到與變形例1 7相同之效果 。亦即是’由於係並不需要設置積分電路，因此，在進行 了積分處理的情況時所可能發生的雜訊之累積，係成爲不 會發生。又，由於係進行有差動訊號處理，因此，係能夠 將雜訊耐性作更進一步的提升。 又，在此變形例1 9中，由於係與變形例1 4以及變形例 17相同的，設爲對於從與供給相同之展頻碼Ck的送訊導體 12之根數相同數量的受訊導體14而來之輸出訊號作放大的 構成’因此，在感測部1 00上之最小檢測區域中，係能夠 得到等向性之感度分布。於此情況，例如就算是在感測部 上被配置有對向面爲圓形狀之指示體，亦能夠將該指示體 之對向面檢測爲圓形狀。 〔變形例20〕 在上述變形例1 9中，雖係將展頻碼之供給形態以及受 訊形態設爲了「+-+」，但是，亦可設爲「- + -」。以下， 針對將此受訊形態設定爲「- + -」的情況作說明。 根據圖5 5，針對此變形例2 0之槪略構成作說明。若是 將此變形例20與上述之變形例1 9 (參考圖52 )作比較，則 兩者間之相異點，係在於：在展頻碼供給電路2 1與送訊導 -116- 201122922 體選擇電路402之間，係被設置有2個的將從展頻碼供給電 路21所供給而來之展頻碼Ck作碼反轉並將反轉碼〔Ck(反 轉）〕作輸出的碼反轉器406 ;反轉碼〔Ck(反轉）〕’係構 成被供給至在藉由送訊導體選擇電路402而被選擇之3根的 送訊導體Yn〜Yn + 2中之位置在兩端處的送訊導體Yn以及 Υη + 2處；以及，3輸入1輸出之差動放大器407之3個的輸入 端子，係將被與藉由受訊導體選擇電路813所選擇了的3根 的受訊導體Xm〜Xm + 2中之索引標號m爲最小的受訊導體Xm 以及索引標號m爲最大之受訊導體Xm+I相連接的輸入端子 設定爲「-」，並且將被與剩餘的1根之受訊導體Xm+ !相連 接的輸入端子之極性設定爲「+」。此些以外之構成，由 於係成爲與上述變形例1 9相同之構成，因此，針對相同之 構成，係省略其說明。 此變形例20，亦與變形例1 9相同的，由於差動放大器 407之3個的輸入端子之極性的配置，係相對於中央之輸入 端子的極性而成爲左右對稱，因此，係能夠得到與進行了 圖50 ( b )中所示一般之位置檢測時的積分處理後相同之 結果。故而，在此變形例20中，亦能夠得到與變形例1 7以 及19相同之效果。亦即是，由於係並不需要進行積分處理 ，因此，在進行了積分處理的情況時所可能發生的雜訊之 累積，係成爲不會發生。又，由於係進行有差動訊號處理 ，因此，係能夠將雜訊耐性作更進一步的提升。 <8、第8實施形態：懸浮狀態之檢測> -117- 201122922 另外，本發明所被作適用之指示體檢測裝置’係除了 被搭載於液晶顯示裝置處的情況之外，例如，亦可考慮有 如同採用了既存之電磁感應方式的位置檢測裝置一般之與 液晶顯示裝置相獨立地而將指示體檢測裝置另外單獨地構 成之情況。將既存之指示體檢測裝置作了搭載的液晶顯示 裝置，由於一般而言係將指示體檢測裝置之檢測區域與液 晶顯示裝置之顯示區域重疊形成，因此，使用者若是對於 欲進行指示或者是選擇之對象（例如圖符或者是工具列等 )所被作顯示的位置而藉由手指等之指示體來作指示，則 係能夠對於所期望之位置作指示。 但是，當將指示體檢測裝置與液晶顯示裝置相獨立地 分開形成的情況時，例如身爲既存之個人電腦的輸入裝置 之觸控板或者是電磁感應方式之數化器（digitizer )的情 況時，則係難以直接地對於此些之輸入裝置上所指示了的 位置與液晶顯示裝置上的位置之間的關連性作掌握。因此 ，在此些之既存的輸入裝置中，係藉由亦將指示體正在作 接近的狀態（指示體與輸入裝置之檢測部並未直接作接觸 之狀態，以下，稱爲懸浮狀態）檢測出來，而成爲能夠讓 使用者對於所欲作指示之輸入裝置上的位置係與液晶顯示 裝置上之何者的位置相對應一事作視認，以提升使用者之 便利性。 然而，當指示體係爲懸浮狀態的情況時，亦即是當指 示體係爲從感測部1〇〇之表面（圖13中之第2基板）而略微 浮起的狀態時，由於檢測感度係爲低，且亦會大幅受到雜 -118- 201122922 訊之影響，因此，確實地進行懸浮狀態時之位置檢測一事 ，係變得困難。 〔變形例2 1〕 在變形例2 1中，針對能夠對於指示體是否爲懸浮狀態 —事而以更良好之精確度來作判定的辨識手法’參考圖5 6 〜5 8來作說明。於此’圖5 6 ’係爲對於手指（指示體）1 9 正接觸於感測部1 〇 〇之上的狀態、以及在此狀態下所得到 之檢測訊號（相關値）之準位曲線作展示的圖’圖5 7 ’係 爲對於手指1 9略浮起於感測部1 〇 〇上之狀態（懸浮狀態） 、以及在此狀態下所得到之檢測訊號之準位曲線作展示之 圖，圖58，係爲對於在圖57所示之狀態下的交叉點附近之 區域處而於某一時刻所得到的檢測訊號（相關値）之準位 値的分布作了映射之圖。以下’將此手指1 9之正在作接觸 的狀態與並未作接觸的狀態（懸浮狀態）作對比說明。 首先，當手指1 9正與感測部1 〇〇之表面作接觸的狀態 (參考圖56(a))下，如同在第1實施形態（參考圖13)中 所作了說明一般，從送訊導體1 2所放出之電場的一部份係 在手指19處收斂，從送訊導體12而朝向受訊導體14流動之 電流的一部份，係經由手指1 9而分流至接地處。其結果’ 流入至受訊導體1 4處之電流由於係減少’因此’準位曲線 420，相較於手指19並未作接觸之區域，在正在作接觸之 區域42 0a處，訊號準位係急遽地變高，在此區域處’係得 到訊號準位之峰値420a (參考圖56(b))。 -119- 201122922 相對於此，當手指19並未與感測部100之表面作接觸 的狀態（懸浮狀態，參考圖57(a))下，由於從送訊導體12 所放出之電場的少數一部份亦會在手指1 9處收斂’因此’ 從送訊導體1 2而朝向受訊導體1 4流動之電流的少數一部份 ，係會經由手指1 9而分流至接地處。其結果，由於流入至 受訊導體1 4中之電流亦會有若干的減少，因此’準位曲線 421之訊號準位係會在手指19最爲接近感測部10之表面的 區域處而變高，並且得到其之峰値421a。然而，該峰値 421a，相較於手指19接觸於感測部100上時之峰値420a， 其値係變小，而準位曲線421係平緩化（圖57(b))。 在此變形例2 1之懸浮狀態的辨識手法中，係從準位曲 線之邊緣的斜率與峰値而求取出兩者之比，並藉由將此比 與特定之臨限値作比較，來辨識出指示體1 9是否爲懸浮狀 會g 〇 若是對於在手指19所接近的交叉點附近之區域處的於 某一時刻所得到的檢測訊號（相關値）之準位値的分布作 映射，則例如係成爲如同圖5 8中所示一般之分布。另外， 在此圖5 8中，係展示藉由3 X 3之交叉點所得到了的準位値 ’該準位値’係被作了正規化。而後，將此峰値與邊緣之 斜率間的比計算出來，並將此算出了的比與特定之臨限値 (例如0 · 7 )作比較。 在此圖5 8所示之例中，在中央之交叉點處，係得到準 位之最大値「100」，在位置於其之左右上下的交叉點處 ’係得到準位値「5 0」。在檢測訊號（相關値）之準位曲 -120- 201122922 線4 2 1中的邊緣之斜率，係可藉由對於峰値（圖5 7 (b )中之 黑箭頭的長度，圖58之中央格）、和與得到該峰値之交叉 點相鄰接的其他交叉點處之準位値，來求取出兩者之間的 差，而得到之。例如，於此圖5 7之情況中，準位曲線之峰 値，由於係成爲圖58之中央格之「100」，因此，邊緣之 斜率，係成爲1 00-50 = 5 0。故而，準位曲線之邊緣之斜率 與峰値間的比，係成爲（邊緣之斜率/峰値）=(50/ 1 00 )=0.5。故而，在此圖58所示之例中，指示體19係被判別 爲身爲懸浮狀態。又，當此準位曲線42 1之邊緣之斜率與 峰値間的比爲較特定之臨限値更大的情況時（例如，當此 値爲0.9的情況時），指示體19係被判別爲與感測部100之 表面相接觸的狀態。 於此，在上述圖5 8所示之例中，雖係針對設置了 1個 的用以進行懸浮狀態之有無的辨識之特定的臨限値之情況 而作了例示說明，但是，本發明係並不被限定於此。例如 ，亦可藉由設置較此特定的臨限値更小的第2臨限値，並 將準位曲線之邊緣之斜率與峰値間的比與此第2臨限値作 比較，來對於懸浮狀態之程度（感測部與指示體間之距離 等）作更詳細的辨識。 另外，上述辨識手法，雖並未特別作圖示說明，但是 ，例如，係可在被設置於受訊部3 0 0 (參考圖1 )中之位置 檢測電路3 5處來進行上述演算，亦可在外部之電腦處來進 行演算。 另外，在上述變形例2 1中，雖係針對根據檢測訊號之 -121 - 201122922 準位曲線（準位値之映射資料）來直接進行懸浮狀態之辨 識的情況而作了例示說明，但是，本發明係並不被限定於 此。亦可對於檢測訊號之準位曲線進行非線性處理，並根 據非線性處理後之特性來對於懸浮狀態作辨識。 於此，針對對於檢測訊號（相關値）之準位曲線，作 爲非線性處理而進行了對數變換之情況，來作例示說明。 當並不進行非線性處理的情況時，藉由指示體1 9與感測部 1 00的表面作接觸所得到的檢測訊號之準位，於指示體1 9 與感測部1 00相接觸之部分處，係成爲極端的大，而於指 示體1 9從感測部1 0 0之表面而浮起之處，係成爲極端的小 。故而，就算是在想要亦包含有指示體1 9爲從感測部1 〇〇 而僅些許地浮起之狀態的來進行辨識處理的情況時，亦由 於檢測訊號之準位係在上述之2個的情況中而極端的相異 ，因此正確的進行辨識一事係爲困難。 相對於此，若是對於檢測訊號（相關値）之準位曲線 ，而進行特定之訊號變換處理、例如進行對數變換，則能 夠使檢測訊號中之準位爲小的訊號部分變得顯著，並對於 準位爲大的訊號部分作抑制。亦即是，在對數變換後之準 位曲線中，峰値部之形狀係寬闊化，其之最大値係被作抑 制。於此情況，在指示體1 9之接觸狀態與非接觸狀態間的 邊界附近之準位値的變化，係成爲連續性，就算是當指示 體1 9從感測部1 〇〇而僅些許地浮起的狀態時，亦能夠容易 地辨識出懸浮狀態’而能夠使辨識特性提升。 -122- 201122922 〔變形例22〕 接下來，參考圖59以及圖60，針對就算是指示體爲懸 浮狀態的情況時亦能夠確實地進行指示體之位置檢測的構 成例作說明。 於此，圖59，係爲對於當指示體1 9存在於感測部1 00 (參考圖1 )之近旁的情況下之最小檢測區域S !的展頻碼 Ck之供給形態以及輸出訊號之檢測形態間的關係作展示的 槪念圖，圖60，係爲對於當指示體1 9存在於離感測部1 00 而較遠之處的情況下之最小檢測區域S2的展頻碼ck之供給 形態以及輸出訊號之檢測形態間的關係作展示的槪念圖。 首先，針對送訊導體12以及受訊導體14之選擇根數的 切換動作作槪略說明。此選擇根數之切換，例如，係根據 在上述變形例2 1中所說明了的指示體1 9是否成爲懸浮狀態 一事之判定來進行之。亦即是，係根據在某一時刻所得到 之檢測訊號（相關値）的準位値來求取出準位曲線之邊緣 之斜率與峰値間的比，並將此比與特定之臨限値作比較， 而判定是否爲懸浮狀態。而後，當判定出係爲懸浮狀態時 ’係以藉由送訊導體選擇電路以及受訊導體選擇電路（參 考圖1等）來選擇複數之送訊導體12以及受訊導體14的方 式來作控制。如同上述一般，懸浮狀態之判定，例如，係 藉由位置檢測電路35(參考圖1、圖39)來進行，並成爲 當被判定爲懸浮狀態時，而從位置檢測電路3 5來對於控制 電路4〇(參考圖1)輸出特定之訊號。而後，控制電路40 ’係當從此位置檢測電路35而被輸入了特定之訊號時，對 -123- 201122922 於送訊導體選擇電路22以及受訊導體選擇電路231作控制 ’並對於複數之送訊導體12而供給特定之展頻碼Ck，並且 ，根據從複數之受訊導體14而來的輸出訊號而求取出相關 値。 接下來’針對上述切換動作之詳細內容作說明。在以 下之說明中，爲了能夠容易地理解其原理，係針對下述之 情況來作例示說明：亦即是，設爲能夠將展頻碼Ck供給至 任意之複數的送訊導體¥„處，並且，在受訊部300之放大 電路32處’係使用具備有極性爲「+」的複數之輸入端子 的放大器410，而藉由此放大器41〇來將任意之受訊導體乂〇] 的輸出訊號檢測出來。 首先，當指示體19正與感測部100之表面作接觸時， 展頻碼Ck，係被供給至2根的送訊導體Yn+1以及Yn + 2處，被 設置在受訊部300之放大電路32處的放大器410，係將從2 根的受訊導體Xm+I以及Xm + 2而來的輸出訊號作放大並作輸 出（圖59之狀態）。 接下來，若是手指等之指示體19從感測部100之表面 而離開，則根據檢測訊號（相關値）之準位値所得到的準 位曲線之邊緣之斜率與峰値間的比，由於係成爲較特定之 臨限値而更小，因此，係被判定爲懸浮狀態。如此一來， 控制電路40，係根據從位置檢測電路3 5而來之特定的訊號 ，而對於送訊導體選擇電路22以及受訊導體選擇電路231 (參考圖39 )作控制，並以使展頻碼Ck被供給至4根的送 訊導體Yn〜Yn + 3處的方式，來將展頻碼供給電路21與送訊 -124- 201122922 導體群1 [作連接。同樣的，控制電路40，係對於受 選擇電路231作控制，在被設置於放大電路32處之 411的各輸入端子處，係被連接有4根的受訊導體χη 。如此一來，檢測區域，係從當指示體1 9正與感名 之表面作接觸的狀態下之檢測區域S 1 (參考圖5 9 ) 切換爲可檢測範圍更廣之檢測區域S2 (參考圖60 ) 另外，此時，在送訊部200處的展頻碼Ck之供 以及在受訊部3 1 0處的訊號之檢測形態，例如係亦 「++」或者是「+-」。 如同上述一般，在此變形例22中，當判斷指示 爲懸浮狀態的情況時，係藉由以使送訊導體1 2以及 體1 4之根數增加的方式來作控制，並藉由將被供給 之展頻碼Ck的送訊導體12以及被與放大器同時作連 訊導體之根數增加，來使檢測感度提升，經由此， 更確實地進行懸浮狀態之指示體1 9的位置檢測。 另外，在此變形例22中，雖係針對因應於指示 測狀態來將所選擇之送訊導體以及受訊導體的根霍 或者是4根之間作增減的情況而作了例示說明’但 發明係並不被限定於此。例如，所選擇之送訊導體 受訊導體1 4之根數，係可作任意的設定。例如’亦 檢測訊號之峰値而預先設定複數之臨限値’並將峰 臨限値作比較，而設定爲伴隨著峰値成爲較臨限値 事來將所選擇之根數逐漸地作增加。又’所選擇之 體1 2以及受訊導體1 4之根數，係亦可並非爲相同數 訊導體 放大器 〜Xm + 3 IJ 部 1〇〇 ，而被 Ο 給形態 可設爲 體19係 受訊導 有相同 接的受 係能夠 體的檢 5[在2根 是，本 12以及 可對於 値與此 更小一 送訊導 量。進 -125- 201122922 而，所選擇之送訊導體以及受訊導體的根數之增減，係並 不需要在送訊導體12以及受訊導體14之兩者處而均進行， 亦可設爲僅對於其中一方來作增減。 另外，指示體檢測裝置，例如，係爲了成爲能夠將手 指等的指示體立即地檢測出來，而就算是當指示體並未作 接觸的狀態時，亦爲了檢測出指示體，而涵蓋感測部上之 全部交叉點的而隨時進行有電流變化之檢測處理（掃描） (參考圖18。以下，將此使用全部之送訊導體以及受訊導 體來進行檢測動作一事，稱爲全掃描）。此全掃描，係爲 了能夠將指示體立即地且確實地檢測出來，而期望能達成 高檢測感度與高速化。 然而，若是對於每一根或者是每少數根之送訊導體以 及受訊導體而進行全掃描，則應進行掃描之點係變多，直 到全掃描結束爲止所需的時間係變長。 〔變形例23〕 以下，針對用以將此全掃描更高感度且更高速地來進 行的方法作說明。首先，當並未從感測部而檢測出輸出訊 號時’係藉由使一次之檢測處理（最小檢測區域）中所使 用之送訊導體以及受訊導體的根數增加，而將檢測區域增 大。 另外’所選擇之導體的根數，係可因應於感測部之尺 寸或者是所需要之感度、所期望之檢測速度等，來任意作 設定。 -126- 201122922 另外，將根數作增減之導體，係可爲送訊導體以及受 訊導體之雙方，亦可爲其中一方。另外，當對於送訊導體 以及受訊導體之雙方的根數作增減的情況時，兩者之根數 係亦可爲相異。又，在本發明中，只要是實際地對於進行 訊號檢測之有效面積（檢測區域）作增減的方法，則係可 適用各種之方法。 另外，不僅是根據檢測訊號之有無，亦可根據該檢測 訊號之準位，來對於所使用之送訊導體以及受訊導體之根 數作變更。例如，當檢測訊號之準位係較預先所設定了的 特定之臨限値更大時，係使根數減少，而當該檢測訊號之 準位係較特定之臨限値更小時，則係使根數增大。臨限値 ，係亦可並非僅有1個，而設定2個以上。作爲將檢測訊號 之準位檢測出來的方法，係可使用在變形例2 1 (圖5 6〜圖 5 8 )中所說明了的手法。 於此變形例2 3中，當無法從感測部而得到檢測訊號時 ，係藉由將在指示體之檢測中所使用之送訊導體以及受訊 導體的根數增加，而將檢測區域增廣，藉由此，係能夠實 現高感度且高速之全掃描。 〔變形例24〕 另外，在第1實施形態中，係針對將受訊導體1 4近接 於檢測面（第2基板1 7側）而作了設置的感測部1 〇 〇作了例 示（參考圖2 )。在此第1實施形態中所展示了的感測部 100 ’由於送訊導體12係被配置在相較於受訊導體14而更 -127- 201122922 遠離指示體19之位置處，因此，從送訊導體12所發出之電 場，係會較朝向受訊導體14收斂之電場而更擴廣地在指示 體19處收斂（參考圖12(b))。因此，在指示體19處，從位 置在較指示體19所實際被作放置之位置而更靠受訊導體14 之延伸方向的外側處之送訊導體12而來的電場亦會作收斂 以下，參考圖61，針對此現象作說明。另外，在以下 之說明中，爲了能夠容易地對於此現象作理解，係針對使 送訊導體選擇電路以及受訊導體選擇電路分別同時選擇5 根的送訊導體Yn〜Yn + 4以及受訊導體Xm〜Χπ + 4並將指示體 1 9檢測出來的情況作例示說明。 如同此圖61中所示一般，送訊導體選擇電路，係對於 所選擇了的5根之送訊導體Υη〜γη + 4中的索引標號η爲小的 送訊導體Υη以及Υη+1，而供給從展頻碼供給電路21所供給 而來之展頻碼Ck。又，對於索引標號η爲大的送訊導體 Υη + 3以及Υη + 4，係供給經由碼反轉器431而將展頻碼Ck作了 碼反轉後之反轉碼〔Ck(反轉）〕，位置在中央之送訊導體 Yn + 2，係被與接地相連接。 同樣的，受訊導體選擇電路，係將被作了選擇的受訊 導體xm〜Xm + 4中，索引標號m爲大之2根的受訊導體Xm + sW 及Xm + 4 ’與差動放大器43 0之極性爲「+」的輸入端子作連 接’並將索引標號m爲小之2根的受訊導體Xm以及Xm+i， 與差動放大器430之極性爲「_」的輸入端子作連接，而位 置在中央之受訊導體X^ + 2 ’係被與接地作連接。另外，其 -128- 201122922 他之構成，係與變形例1 2 (圖4 0 )爲相同，針對相同之構 成，係省略其圖示以及說明。 而後，例如，若是假設係被放置有略圓形狀（圖61中 之實線）之指示體1 9，則從與指示體1 9所被放置之送訊導 體¥„〜¥11 + 4相鄰接（位置在受訊導體14所延伸之方向的外 側）的送訊導體Ynq以及Υη + 5所發出之電場，係會被指示 體1 9所吸收，並如同該圖中之點線所示一般地而被檢測出 來。特別是，當送訊導體1 2與指示體1 9之間的距離係更加 遠離的情況時，例如當中介存在於送訊導體1 2與受訊導體 14之間的間隔物16爲厚的情況時、或者是對於懸浮狀態之 指示體1 9作檢測的情況時，係會變得顯著。 因此，於此變形例24中，爲了解決上述課題，係設爲 下述之構成：亦即是，將被配置在離感測部1 00之檢測面 較遠的位置處之送訊導體群1 1側的檢測寬幅縮窄，並將接 近檢測面之受訊導體群1 3側的檢測寬幅增廣，藉由此，而 使得在檢測面處，於由送訊部所供給而來之送訊訊號的準 位曲線之寬闊程度（檢測寬幅）與被輸入至受訊部中之受 訊訊號的準位曲線之寬闊程度，其兩者之間不會產生差異 〔變形例25〕 圖62，係爲對於在此變形例25中之送訊部的展頻碼之 供給形態與受訊部之訊號的檢測形態間之關係作展示的圖 。以下，參考圖39以及圖62，針對此變形例25作說明。於 -129- 201122922 此’圖6 2 ’係爲對於將藉由送訊導體選擇電路而作選擇的 送訊導體1 2從5根而減少爲3根的情況作展示，其他之構成 ，係成爲與圖6 1相同。 此變形例2 5，例如’係如同在變形例丨2 (參考圖4 〇 ) 中所示一般’受訊導體選擇電路231，例如係將相鄰接之 任意的5根之受訊導體乂^〜Xm + 4中的位置在兩側處之Xm、 Xm+i以及Xm + 3、Xm + 4與差動放大器3 5 0之任一者的輸入端 子作連接。另外’在此變形例2 5中，亦同樣的，從藉由受 訊導體選擇電路231而被作了選擇之受訊導體Χηι、乂〇1+1而 來之輸出訊號，係在I/V變換電路31a處而被變換爲電壓 訊號’並被供給至差動放大器430之各輸入端子處，但是 ，由於係成爲與圖39中'所示之變形例1〇相同之構成，因此 ，爲了避免圖面變得複雜，係將受訊導體選擇電路231以 及1/V變換電路23 1 a的記載省略。 另一方面，送訊導體選擇電路22，係對於相鄰接之任 意的3根之送訊導體Yn+1〜Yn + 3作選擇，並對於此3根的送 訊導體中之索引標號m爲最小的送訊導體Υη+Ι供給展頻碼 ，且對於索引標號m爲最大之送訊導體Υη + 3供給反轉碼， 同時，將位置在中央的送訊導體Υη + 2與接地作連接。 如此這般，藉由將以送訊導體選擇電路22所選擇之送 訊導體Υη的數量設爲較以受訊導體選擇電路231所選擇之 受訊導體Xm之根數更少，能夠將在檢測面處之由送訊部 2 00所供給而來之送訊訊號的準位曲線之寬闊程度與被輸 入至受訊部310處之受訊訊號的準位曲線之寬闊程度設爲 -130- 201122922 略相同。亦即是’係能夠使由送訊部2 00以及受訊部3 1 0所 致之準位曲線的寬闊程度的縱橫比接近1。其結果，就算 是當在感測部100上而被配置有對向面爲圓形狀之指示體 的情況時’亦如同在圖6 1中以虛線所展示一般，而能夠並 不將指示體檢測爲橢圓形狀且檢測爲圓形狀。 另外，在此變形例2 5中，雖係針對對於所選擇之送訊 導體以及受訊導體的根數作改變而使縱橫比成爲1的情況 而作了例示說明，但是，本發明係並不被限定於此。例如 ，亦可對於送訊導體以及受訊導體之形狀（寬幅等）、其 配置圖案（圓形狀或者是龜殻紋路狀等）、各導體間之節 距作變更，以對於縱橫比作調整。又，於圖6 1中，雖係針 對在受訊部之放大電路中而使用差動放大器的情況而作了 例示，但是，亦可使用單端輸入之放大器。 〔變形例2 6〕 另外，第1實施形態之指示體檢測裝置1，爲了能夠安 定地進行相關演算，從1/ V變換電路32a所輸出之受訊訊 號，係將其之訊號準位在未圖示之放大器中而放大至特定 之訊號準位，之後，再在A/D變換電路33中而被變換爲 數位訊號並被輸入至相關値算出電路34中（參考圖1等） 。當雜訊爲較受訊訊號更大的情況時，若是將混合存在有 雜訊之受訊訊號的訊號準位均一地作放大，則會產生下述 —般之問題：亦即是，雜訊亦會被放大，而A/D變換器 會被箝制（clip )，並成爲無法將受訊訊號適當地檢測出 -131 - 201122922 來。 然而，若是不將受訊訊號之訊號準位作放大，則，例 如上述變形例23—般，當對於身爲懸浮狀態之指示體作檢 測時，受訊訊號之變化準位係變小，而產生無法將指示體 檢測出來之問題。 以下，參考圖63以及圖64，針對變形例26作說明。此 圖63，係爲在此變形例26中之受訊部3 3 0的槪略區塊構成 圖，圖64，係爲構成後述之增益値設定電路的絕對値檢波 電路之電路構成圖。於此，若是將此變形例26中所示之受 訊部330，和第1實施形態（參考圖1、圖6以及圖8等）中 之受訊部300作比較，則其之相異點，係在於：代替被設 置在放大電路32之I/V變換電路32a與A/D變換電路33之 間的未圖示之放大器，係設置有增益調整電路481之點， 以及係設置有增益値設定電路482之點。關於其他之構成. ，由於係爲與圖1所示之變形例1中的受訊部3 00成爲相同 之構成，因此，對於相同之構成，係附加相同之號碼，並 省略其說明。 增益調整電路481，係爲用以將被輸入了的訊號之訊 號準位適宜地放大或者是減少爲特定之訊號準位的電路。 此增益調整電路481，係被設置在放大電路32之I/V變換 電路32a與A/D變換電路33之間，並根據從後述之增益値 設定電路482而來的控制訊號，來進行特定之訊號準位的 變更。此時，在增益調整電路481之能量成分的訊號強度 中’由於係並不僅是應檢測出之訊號（展頻碼）成分，而 -132- 201122922 亦包含有雜訊等，因此，增益控制電路4 8 2，係成爲根據 藉由訊號檢測電路3 1所檢測出之訊號全體的能量成分之訊 號強度來設定受訊增益値。 增益値設定電路482，係爲用以根據在A/ D變換電路 33中而被變換爲數位訊號後的輸出訊號來對於增益調整電 路48 1作控制之電路。此增益値設定電路48 2，係具備有絕 對値檢波電路4 8 3、和自動增益値設定電路484。 絕對値檢波電路48 3，係將從A/ D變換器33所輸出之 輸出訊號的能量成分之訊號強度檢測出來。另外，在從A / D變換器3 3所輸出之訊號中，由於並不僅是應檢測出之 訊號（展頻碼）成分，而亦包含有雜訊等之不必要的訊號 成分，因此，在增益調整電路48 1處，係檢測出包含有雜 訊等之不必要的訊號成分之檢測訊號全體的能量成分之訊 號強度。 自動增益値設定電路484，係爲根據在絕對値檢波電 路483中所檢測出之訊號強度來對於增益調整電路481之增 益作控制的電路。此自動增益値設定電路484，係被與絕 對値檢波電路483與增益調整電路481相連接，並對於增益 調整電路48 1而輸出控制訊號。 接下來，參考圖64，針對絕對値檢波電路483之構成 作說明。此絕對値檢波電路483，係具備有積算器483 a、 和被連接於此積算器483a之輸出端子處的積分器483b。 積算器483 a，係對於A/D變換器33之輸出訊號作平方 演算，並將演算後之輸出訊號輸出至積分器48 3b處。另外 -133- 201122922 ，在積算器483a之2個的輸入端子處，A/D變換器33 (參 考圖63)之輸出訊號係被作分歧並被輸入，而相互之訊號 係被作乘算。又，積分器483b，係對於積算器48 3 a之輸出 訊號作時間性的積分，並將該積分訊號作爲控制訊號而輸 出至增益調整電路481 (參考圖63)處。 如同上述一般，在此變形例26之受訊增益値的設定中 ，係將並不僅是應檢測出之訊號（展頻碼）成分而亦包含 有雜訊等之訊號的能量成分之訊號強度檢測出來，並根據 該訊號強度來設定受訊增益値。於此情況，就算是當被輸 入至增益調整電路48 1處的輸入訊號中被重疊有雜訊等的 情況時，亦能夠適當地對於受訊增益値作設定。 另外，絕對値檢波，只要是能夠將包含有應檢測之訊 號成分以及雜訊的訊號之準位檢測出來，則係可使用任意 之方法。例如，除了上述之手法以外，亦可使用將輸出訊 號之準位的絕對値作積分之手法等。又，在絕對値檢波處 理中，係亦可使用A/ D變換後之數位訊號處理以及A/ D 變換前之類比訊號處理之任一者。 〔變形例27〕 另外’如同上述一般，本發明之指示體檢測裝置，係 成爲能夠將身爲檢測對象之手指等的指示體同時性地作複 數之檢測。因此，本發明之指示體檢測裝置，例如，係可 考慮有由複數之使用者同時作使用或者是由1人的使用者 以兩手來進行操作等的情況。其結果，可以想見，感測部 -134- 201122922 ’係爲了能夠以複數之指示體來作使用，而會有被大型化 的情況。 在上述實施形態以及各種變形例中，係對於從送訊導 體1 2之其中一方的端部來供給展頻碼Ck的構成例而作了說 明。然而’若是將感測部作了大型化，則由於身爲展頻碼It goes to the A/D conversion circuit 33 of the latter stage (refer to FIG. 1). Thereafter, the output signal digitally converted in the A/D conversion circuit 33 is correlated in the correlation calculation circuit 34, and the correlation calculation result is related to the result of the correlation calculation. In the correlation memory circuit 3 4d (refer to FIG. 8), if the detection mode of the output signal -115-201122922 is set to "+-+" as in the modification 19, three of the differential amplifiers 405 The arrangement of the polarity of the input terminal is symmetrical with respect to the polarity of the input terminal at the center. Therefore, similarly to the modification of the first embodiment, the position detection in the general position shown in Fig. 5 (b) can be obtained. The same result after the integration of the points. Therefore, in the modification 19, the same effect as that of the modification 17 can be obtained. That is, since the integration circuit is not required to be installed, the accumulation of noise that may occur in the case where the integration processing is performed does not occur. Moreover, since the differential signal processing is performed, the noise tolerance can be further improved. Further, in the modification 19, the same number of the signal conductors as the number of the transmission conductors 12 that are supplied with the same spread code Ck are the same as those of the modification 14 and the modification 17. The output signal from 14 is enlarged. Therefore, the sensitivity distribution of the isotropic property can be obtained in the minimum detection area on the sensing unit 100. In this case, for example, even if the pointing portion having the opposite facing surface is disposed on the sensing portion, the opposing surface of the pointer can be detected as a circular shape. [Modification 20] In the above-described Modification 19, the supply form and the reception form of the spread code are set to "+-+", but "- + -" may be used. Hereinafter, a case where this reception form is set to "- + -" will be described. The outline of this modification 20 will be described with reference to Fig. 5 5. If this modification 20 is compared with the above-described modification 19 (refer to FIG. 52), the difference between the two is based on the spread spectrum code supply circuit 2 1 and the transmission guide-116-201122922 body. Between the selection circuits 402, two codes for inverting the spread code Ck supplied from the spread code supply circuit 21 and outputting the inverted code [Ck (reverse)] are provided. The inverter 406; the inverted code [Ck (reverse)]' is configured to be supplied to the three signal conductors Yn to Yn + 2 selected by the transmission conductor selection circuit 402 in two positions. At the end of the signal conductors Yn and Υη + 2; and the input terminals of the three input and output differential amplifiers 407 are selected by the three selected by the signal conductor selection circuit 813 The received conductor Xm of the received conductor Xm~Xm + 2 with the smallest index mark m and the input terminal of the received conductor Xm+I whose index number m is the largest is set to "-", and will be with the remaining The polarity of the input terminal connected to one of the signal conductors Xm+ ! is set to "+". The configuration other than the above is the same as the configuration of the above-described modification 19. Therefore, the description of the same configuration will be omitted. Also in the modification 20, similarly to the modification 19, since the polarity of the input terminals of the three differential amplifiers 407 is bilaterally symmetrical with respect to the polarity of the input terminal of the center, it is possible to obtain The same result after the integration processing at the time of the general position detection shown in Fig. 50 (b) was performed. Therefore, in the modification 20, the same effects as those of the modifications 17 and 19 can be obtained. That is, since the integration processing is not required, the accumulation of noise that may occur in the case where the integration processing is performed does not occur. Moreover, since the differential signal processing is performed, the noise tolerance can be further improved. <8, the eighth embodiment: detection of the suspension state> -117-201122922 In addition, the indicator detection device "applied to the present invention" is also mounted on the liquid crystal display device, for example, It is conceivable that the position detecting device using the existing electromagnetic induction method is generally configured separately from the liquid crystal display device and the indicator detecting device is separately formed. A liquid crystal display device in which an existing indicator detecting device is mounted is generally formed by superimposing a detection region of the pointer detecting device and a display region of the liquid crystal display device. Therefore, if the user wants to indicate or select When the object (for example, an icon or a toolbar) is displayed as a position to be displayed by a pointer such as a finger, it is possible to indicate the desired position. However, when the pointer detecting device is formed separately from the liquid crystal display device, for example, when the touch panel of the input device of the existing personal computer is used or the digitizer of the electromagnetic induction method is used, It is difficult to grasp directly the relationship between the position indicated on the input device and the position on the liquid crystal display device. Therefore, in such an existing input device, the indicator is also in a state of being approached (the state in which the indicator is not in direct contact with the detecting portion of the input device, hereinafter referred to as a floating state) is detected. Moreover, it is possible to allow the user to visually recognize the position on the input device to be instructed and the position on the liquid crystal display device to enhance the convenience of the user. However, when the indication system is in a floating state, that is, when the indication system is in a state of slightly floating from the surface of the sensing portion 1 (the second substrate in FIG. 13), since the detection sensitivity is It is low and will be greatly affected by the miscellaneous -118-201122922. Therefore, it is difficult to carry out the position detection in the suspended state. [Modification 2 1] In the modification 2, the identification method which can determine whether the indicator is in a suspended state or not, and which is judged with better accuracy is described with reference to FIGS. 5 6 to 5 8 . Here, 'Fig. 5 6' is a state in which the finger (indicator) 1 9 is in contact with the sensing unit 1 〇〇 and the level of the detection signal (related 値) obtained in this state is made. The figure shown in the figure 'Fig. 5 7' is a diagram showing the state in which the finger 1 9 is slightly floated on the sensing portion 1 (suspended state), and the level of the detection signal obtained in this state. Fig. 58 is a diagram for mapping the distribution of the level 値 of the detection signal (correlation 得到) obtained at a certain point in the region near the intersection in the state shown in Fig. 57. Hereinafter, the state in which the finger 1 9 is in contact is compared with the state in which the finger is not in contact (suspended state). First, when the finger 1 9 is in contact with the surface of the sensing unit 1 (refer to FIG. 56(a)), as described in the first embodiment (refer to FIG. 13), the transmission is performed. A portion of the electric field emitted by the conductor 12 converges at the finger 19, and a portion of the current flowing from the transmitting conductor 12 toward the signal conductor 14 is shunted to the ground via the finger 19. As a result, the current flowing into the signal conductor 14 is reduced by the 'and therefore' level curve 420, compared to the area where the finger 19 is not in contact, at the area 42 0a where the contact is being made, the signal level system Risingly high, in this area, 'the peak of the signal level 420a (refer to Figure 56 (b)). -119- 201122922 In contrast, when the finger 19 is not in contact with the surface of the sensing portion 100 (suspended state, refer to FIG. 57(a)), a small number of electric fields are discharged from the transmitting conductor 12 A portion will also converge at the finger 19 so that a small portion of the current flowing from the signal conductor 1 2 toward the signal conductor 14 is shunted to the ground via the finger 19. As a result, since the current flowing into the signal conductor 14 is also somewhat reduced, the signal level of the 'quad curve 421' will change at the region where the finger 19 is closest to the surface of the sensing portion 10. It is high and gets its peak 値 421a. However, the peak 421a is smaller than the peak 420a when the finger 19 is in contact with the sensing portion 100, and the alignment curve 421 is flattened (Fig. 57(b)). In the identification method of the suspension state of the modification 21, the ratio between the slope and the peak of the level curve is taken out, and the ratio is compared with the specific threshold. It is recognized whether the indicator body 19 is in a suspended state or not, and if it is a map of the distribution of the level (値) of the detection signal (correlation 得到) obtained at a certain point in the vicinity of the intersection point where the finger 19 is close, Then, for example, it becomes a general distribution as shown in Fig. 58. Further, in Fig. 58, it is shown that the level 値 'the level ’ ' obtained by the intersection of 3 X 3 is normalized. Then, the ratio between the peak and the slope of the edge is calculated, and the calculated ratio is compared with a specific threshold 例如 (for example, 0 · 7). In the example shown in Fig. 58, at the intersection of the center, the maximum 値 "100" of the level is obtained, and at the intersection of the position up and down, the position is "5 0". . The slope of the edge in the line 4 2 1 of the detection signal (correlation 値) can be obtained by the peak of the peak (the length of the black arrow in Fig. 57 (b), the center of Fig. 58 The position 値 at the other intersections adjacent to the intersection point at which the peak is obtained is obtained by taking the difference between the two. For example, in the case of Fig. 57, the peak of the level curve is "100" in the center of Fig. 58, so the slope of the edge becomes 1 00-50 = 50. Therefore, the ratio between the slope of the edge of the level curve and the peak value is (slope of the edge / peak 値) = (50 / 1 00 ) = 0.5. Therefore, in the example shown in Fig. 58, the indicator 19 is judged to be in a suspended state. Further, when the ratio of the slope of the edge of the level curve 42 1 to the peak-to-peak ratio is larger than the specific threshold ( (for example, when the 値 is 0.9), the indicator 19 is discriminated. It is in a state of being in contact with the surface of the sensing unit 100. Here, in the example shown in FIG. 58 described above, although the specific threshold for setting the presence or absence of the suspension state is provided, the present invention is exemplified. It is not limited to this. For example, by setting a second threshold 値 smaller than the specific threshold 値, and comparing the slope of the edge of the calibration curve with the ratio of the peaks to the second threshold, The degree of suspension (the distance between the sensing unit and the indicator, etc.) is more detailed. In addition, although the above identification method is not particularly illustrated, for example, the above calculation may be performed at the position detecting circuit 35 provided in the receiving unit 300 (refer to FIG. 1). The calculation can be performed at an external computer. Further, in the above-described Modification 21, the case where the suspension state is directly recognized based on the -121 - 201122922 level curve (the mapping data of the level 値) of the detection signal is exemplified, but The invention is not limited thereto. The quasi-position curve of the detection signal can also be nonlinearly processed, and the suspension state can be identified according to the characteristics of the nonlinear processing. Here, the case where the logarithmic curve of the detection signal (correlation 値) is subjected to logarithmic transformation as a nonlinear process will be exemplified. When the non-linear processing is not performed, the level of the detection signal obtained by the contact of the pointer 19 with the surface of the sensing unit 100 is in contact with the sensing unit 1 00. The portion is extremely large, and the indicator body 19 is extremely small when it floats from the surface of the sensing portion 100. Therefore, even if it is desired to include the indication that the indicator 19 is in a state of being slightly floated from the sensing unit 1 , the detection signal is also in the above-mentioned manner. The two cases are extremely different, so it is difficult to correctly identify them. On the other hand, if a specific signal conversion process is performed on the level curve of the detection signal (correlation 値), for example, logarithmic transformation is performed, the signal portion in the detection signal can be made small, and the signal portion becomes significant. The level is suppressed for the large signal portion. That is, in the logarithmic curve after the logarithmic transformation, the shape of the peak portion is broadened, and the maximum enthalpy is suppressed. In this case, the change in the level 値 in the vicinity of the boundary between the contact state and the non-contact state of the indicator 19 is continuous, even when the indicator 19 is only slightly from the sensing unit 1 In the floating state, the floating state can be easily recognized, and the identification characteristics can be improved. [Variation 22] Next, a configuration example in which the position detection of the pointer can be surely performed even when the pointer is in the floating state will be described with reference to Figs. 59 and 60. Here, FIG. 59 is a supply form of the spread code Ck and detection of the output signal for the minimum detection area S! when the pointer 19 exists in the vicinity of the sensing unit 100 (refer to FIG. 1). A commemorative diagram showing the relationship between the morphologies, FIG. 60, is a supply of the spread code ck of the minimum detection area S2 in the case where the pointer 19 exists farther from the sensing unit 100. A commemorative diagram showing the relationship between the form and the detected form of the output signal. First, the switching operation of the number of selected conductors 12 and the received conductor 14 will be briefly described. The switching of the number of selections is performed, for example, based on the determination as to whether or not the pointer 1 9 described in the above modification 21 is in a floating state. That is, based on the level of the detection signal (correlation 得到) obtained at a certain time, the ratio between the slope of the edge of the calibration curve and the peak value is obtained, and the ratio is compared with the specific threshold. For comparison, it is determined whether it is in a floating state. Then, when it is determined that the system is in a floating state, the control is performed by selecting the plurality of signal conductors 12 and the signal conductors 14 by the signal conductor selection circuit and the signal conductor selection circuit (refer to FIG. 1 and the like). . As described above, the determination of the floating state is performed, for example, by the position detecting circuit 35 (refer to Figs. 1, 39), and becomes the control circuit when it is determined to be in the floating state, and from the position detecting circuit 35. 4〇 (refer to Figure 1) outputs a specific signal. Then, when the control circuit 40' is input with a specific signal from the position detecting circuit 35, the control conductor selection circuit 22 and the signal conductor selection circuit 231 are controlled to -123-201122922 and the plurality of transmissions are transmitted. The conductor 12 is supplied with a specific spreading code Ck, and the correlation 値 is extracted based on the output signal from the plurality of signal conductors 14. Next, the details of the above switching operation will be described. In the following description, in order to be able to easily understand the principle, it is exemplified for the case where the spread code Ck can be supplied to an arbitrary plural number of transmission conductors. Further, an amplifier 410 having a plurality of input terminals having a polarity of "+" is used in the amplifying circuit 32 of the receiving unit 300, and the output of any of the received conductors 乂〇 is output by the amplifier 41A. The signal is detected. First, when the pointer 19 is in contact with the surface of the sensing unit 100, the spreading code Ck is supplied to the two transmission conductors Yn+1 and Yn+2, and is disposed in the receiving unit 300. The amplifier 410 at the amplifying circuit 32 amplifies and outputs an output signal from the two received conductors Xm+I and Xm + 2 (state of Fig. 59). Next, if the pointer 19 such as a finger is separated from the surface of the sensing unit 100, the slope of the edge of the level curve obtained from the level 检测 of the detection signal (correlation 値) and the peak-to-peak ratio are due to The system becomes smaller than the specific threshold, and therefore, it is determined to be in a suspended state. In this way, the control circuit 40 controls the signal conductor selection circuit 22 and the signal conductor selection circuit 231 (refer to FIG. 39) according to the specific signal from the position detecting circuit 35. The frequency code Ck is supplied to the four signal conductors Yn to Yn + 3 to connect the spread code supply circuit 21 to the conductor-124-201122922 conductor group 1. Similarly, the control circuit 40 controls the selection circuit 231, and four signal conductors χη are connected to the input terminals of the 411 provided at the amplifier circuit 32. In this way, the detection area is switched from the detection area S 1 (refer to FIG. 5 9 ) in a state in which the pointer 19 is in contact with the surface of the sense to the detection area S2 having a wider detectable range (refer to the figure). 60) In addition, at this time, the detection form of the spread code Ck at the transmitting unit 200 and the signal at the receiving unit 3 10 are, for example, "++" or "+-". As described above, in the modification 22, when it is judged that the indication is in the floating state, it is controlled by increasing the number of the transmission conductors 1 2 and the body 14 and by being The number of the communication conductors 12 supplied to the spread code Ck and the number of the communication conductors simultaneously with the amplifier are increased to improve the detection sensitivity, whereby the position detection of the pointer 19 in the floating state is more reliably performed. Further, in the modification 22, the case where the selected transmission conductor and the signal conductor are added or subtracted in accordance with the state of the indication measurement is exemplified. The invention is not limited thereto. For example, the number of selected transmission conductors of the signal conductor 14 can be arbitrarily set. For example, 'the peak of the signal is also detected and the threshold of the plural is set in advance' and the peak limit is compared, and the number of selected roots is gradually increased as the peak becomes a more restrictive event. . Further, the number of the selected body 1 2 and the received conductor 14 may not be the same number of conductor amplifiers ~Xm + 3 IJ part 1 〇〇, and the mode may be set to body 19 The signal has the same connection of the body capable of detecting 5 [in 2, this 12 and can be a smaller one for the 送 and the delivery guide. -125- 201122922, the number of selected transmission conductors and the number of received conductors is not required to be performed at both the transmission conductor 12 and the signal conductor 14, or may be set Only for one of them to increase or decrease. Further, the indicator detecting device is, for example, a sensor that can detect a finger or the like immediately, even when the pointer is not in contact, and also covers the sensing unit in order to detect the indicator. The detection processing (scanning) of the current change is performed at all the intersections (refer to Fig. 18. Hereinafter, the detection operation using all of the transmission conductors and the signal conductors is referred to as full scanning). This full scan is capable of detecting the indicator immediately and surely, and it is desirable to achieve high detection sensitivity and high speed. However, if a full scan is performed for each or every few of the signal conductors and the signal conductor, the number of points to be scanned is increased until the time required for the end of the full scan becomes longer. [Modification 23] Hereinafter, a method for performing this full scan with higher sensitivity and higher speed will be described. First, when the output signal is not detected from the sensing unit, the detection area is increased by increasing the number of the transmission conductors and the signal conductors used in the detection processing (minimum detection area) Big. Further, the number of selected conductors can be arbitrarily set depending on the size of the sensing unit or the required sensitivity, the desired detection speed, and the like. -126- 201122922 In addition, the conductor for increasing or decreasing the number of the conductors may be either a transmitting conductor or a conductor, or one of them. Further, when the number of both the transmission conductor and the signal conductor is increased or decreased, the number of the two may be different. Further, in the present invention, as long as it is a method of increasing or decreasing the effective area (detection area) for performing signal detection, various methods can be applied. In addition, not only the presence or absence of the detection signal, but also the number of the transmission conductors and the signal conductors to be used can be changed according to the level of the detection signal. For example, when the level of the detection signal is larger than the specific threshold set in advance, the number of roots is reduced, and when the level of the detection signal is smaller than the specific threshold, the system is Increase the number of roots. There is not only one, but two or more. As a method of detecting the level of the detection signal, the method described in the modification 21 (Fig. 56 to Fig. 5) can be used. In the second modification, when the detection signal is not obtained from the sensing unit, the detection area is increased by increasing the number of the transmission conductor and the signal conductor used in the detection of the pointer. Broad, by this, it is possible to achieve high-sensitivity and high-speed full scanning. [Variation 24] In the first embodiment, the sensing unit 1 provided with the receiving conductor 14 in proximity to the detecting surface (the second substrate 17 side) is exemplified (refer to figure 2 ). In the sensor unit 100' shown in the first embodiment, since the signal conductor 12 is disposed at a position further away from the indicator 19 than the signal conductor 14, the slave transmission unit 12 The electric field emitted by the conductor 12 converges at the indicator 19 more widely than the electric field that converges toward the signal conductor 14 (refer to Fig. 12(b)). Therefore, at the indicator body 19, the electric field from the signal conductor 12 at the outer side in the direction in which the direction of the conductor 14 is extended from the position where the indicator body 19 is actually placed is also converged below. This phenomenon will be described with reference to FIG. Further, in the following description, in order to make it easy to understand the phenomenon, the transmission conductor selection circuit and the signal conductor selection circuit are simultaneously selected for five transmission conductors Yn to Yn + 4 and the signal conductor. The case where Xm~Χπ + 4 is detected and the indicator 19 is detected is exemplified. As shown in this FIG. 61, the transmission conductor selection circuit is a small transmission conductor Υη and Υη+1 for the index number η of the selected five transmission conductors Υn to γη + 4 . The spread code Ck supplied from the spread code supply circuit 21 is supplied. Further, for the transmission conductors Υn + 3 and Υη + 4 whose index number η is large, the inverted code [Ck (reverse)) after code-inverting the spread code Ck via the code inverter 431 is supplied. ], the signal conductor Yn + 2 at the center is connected to the ground. Similarly, the received conductor selection circuit is the selected signal conductor xm~Xm + 4, and the index mark m is the larger of the two received conductors Xm + sW and Xm + 4 'and the differential amplifier The input terminals of 43 0 whose polarity is "+" are connected, and the signal conductors Xm and Xm+i whose index number m is two are connected to the input terminal of the differential amplifier 430 whose polarity is "_". And the signal conductor X^ + 2 ' in the center is connected to the ground. Further, the configuration of -128-201122922 is the same as that of the modification 1 2 (Fig. 40), and the same configuration is omitted, and the illustration and description thereof are omitted. Then, for example, if it is assumed that the indicator body 1 9 having a slightly round shape (solid line in Fig. 61) is placed, it is adjacent to the transmission conductor ¥ ～~¥11 + 4 placed with the indicator body 19 The electric field emitted by the signal transmission conductor Ynq and Υη + 5 connected to the outside of the direction in which the conductor 14 is extended is absorbed by the indicator 19 and is as shown by the dotted line in the figure. The ground is detected. In particular, when the distance between the transmitting conductor 12 and the indicator 19 is further away, for example, when the intermediate exists between the transmitting conductor 12 and the signal conductor 14 When the object 16 is thick or when the indicator body 19 in the floating state is detected, it is remarkable. Therefore, in the modification 24, in order to solve the above problem, the following is used. In other words, the detection width of the transmission conductor group 11 side at a position far from the detection surface of the sensing unit 100 is narrowed, and the signal conductor group 1 close to the detection surface is narrowed. The width of the detection on the 3 side is widened, so that at the detection surface, it is supplied by the transmitting department. The broadness of the level of the transmitted signal (the width of the detection) and the width of the signal received by the signal received by the receiver are not different. 25] Fig. 62 is a view showing a relationship between the supply form of the spread spectrum code of the transmitting unit and the detection form of the signal of the receiving unit in the modification 25 of the modification 25. Hereinafter, reference is made to Figs. 39 and 62. This modification 25 will be described. -129-201122922 This 'Fig. 6 2' is a case where the number of the transmission conductors 12 selected by the transmission conductor selection circuit is reduced from five to three. For the sake of display, the other components are the same as those of Fig. 61. This modification 25, for example, is as shown in the modification 丨2 (refer to Fig. 4 一般), the general 'received conductor selection circuit 231, for example, Any of the five received conductors adjacent to each other, Xm, Xm+i, and Xm + 3, Xm + 4 and the differential amplifier 3 5 0 at both sides The input terminals of the user are connected. In addition, in this modification 25, the same is also selected from the signal conductor. The output signal of the selected signal conductors Χηι, 乂〇1+1, which is selected as the path 231, is converted into a voltage signal ' at the I/V conversion circuit 31a and supplied to each of the differential amplifiers 430. At the input terminal, since it has the same configuration as the modification 1 shown in FIG. 39, in order to avoid the complexity of the drawing, the received conductor selection circuit 231 and the 1/V conversion circuit 23 are provided. The description of 1 a is omitted. On the other hand, the transmission conductor selection circuit 22 selects three adjacent transmission conductors Yn+1 to Yn + 3 adjacent to each other, and pairs the three transmission conductors. The indexing element m with the smallest indexing conductor Υn+Ι is supplied with the spreading code, and the inversion code is supplied to the transmitting conductor Υη + 3 whose index number m is the largest, and the transmitting conductor Υη + at the center is located at the same time. 2 Connect to ground. In this manner, by detecting the number of the signal conductors Υn selected by the signal conductor selection circuit 22 to be smaller than the number of the signal conductors Xm selected by the signal conductor selection circuit 231, it is possible to detect The breadth of the level of the signal transmitted by the transmitting unit 200 and the level of the signal received by the receiving unit 310 are set to -130- 201122922 Slightly the same. In other words, the aspect ratio of the width of the level curve caused by the transmitting unit 2 00 and the receiving unit 3 10 is close to 1. As a result, even when the indicator body having the opposite direction is disposed on the sensing unit 100, 'as in the case of the dotted line in FIG. 61, the indicator can be detected. It is an elliptical shape and is detected as a circular shape. Further, in the modification 25, the case where the aspect ratio is set to 1 for the number of selected transmission conductors and the received conductors is exemplified, but the present invention is not It is limited to this. For example, the shape of the transmission conductor and the signal conductor (wide width, etc.), the arrangement pattern (circular shape or the shape of the shell, etc.), and the pitch between the conductors may be changed to adjust the aspect ratio. . Further, although Fig. 61 shows a case where a differential amplifier is used in the amplifier circuit of the signal receiving unit, a single-ended input amplifier can also be used. [Modification 2 6] In addition, in the indicator detecting device 1 of the first embodiment, in order to perform the related calculation stably, the signal to be received from the 1/V conversion circuit 32a is signaled to the position. The amplifier shown in the figure is amplified to a specific signal level, and then converted into a digital signal by the A/D conversion circuit 33 and input to the correlation calculation circuit 34 (refer to FIG. 1 and the like). When the noise is larger than the received signal, if the signal level of the signal signal mixed with the noise is uniformly amplified, the following general problem will occur: that is, the noise It will also be amplified, and the A/D converter will be clamped and will not be able to properly detect the signal being transmitted -131 - 201122922. However, if the signal level of the received signal is not amplified, for example, in the above-described modification 23, when the indicator body in the suspended state is detected, the change level of the received signal becomes smaller, and There is a problem that the indicator cannot be detected. Hereinafter, a modification 26 will be described with reference to FIGS. 63 and 64. Fig. 63 is a schematic diagram showing a schematic configuration of the signal receiving unit 303 in the modification 26, and Fig. 64 is a circuit configuration diagram of an absolute 値 detecting circuit constituting a gain 値 setting circuit to be described later. Here, if the receiving unit 330 shown in the modification 26 is compared with the receiving unit 300 in the first embodiment (see FIGS. 1, 6, and 8, etc.), the difference is different. In place of the amplifier (not shown) provided between the I/V conversion circuit 32a and the A/D conversion circuit 33 of the amplifier circuit 32, the gain adjustment circuit 481 is provided, and the gain is set. The point of the circuit 482 is set. The other components are the same as those of the receiving unit 300 in the first modification shown in Fig. 1. Therefore, the same components are denoted by the same reference numerals and the description thereof will be omitted. The gain adjustment circuit 481 is a circuit for appropriately amplifying or reducing the signal level of the input signal to a specific signal level. The gain adjustment circuit 481 is provided between the I/V conversion circuit 32a of the amplifier circuit 32 and the A/D conversion circuit 33, and is specified based on a control signal from a gain 値 setting circuit 482, which will be described later. Change of signal level. At this time, in the signal strength of the energy component of the gain adjustment circuit 481, 'because the system is not only the signal (spreading code) component to be detected, but the -132-201122922 also contains noise, etc., therefore, the gain control circuit 4 8 2 is to set the received gain 値 based on the signal strength of the energy component of the signal detected by the signal detecting circuit 31. The gain 値 setting circuit 482 is a circuit for controlling the gain adjusting circuit 48 1 based on an output signal which is converted into a digital signal in the A/D converting circuit 33. The gain 値 setting circuit 48 2 is provided with an absolute 値 detection circuit 484 and an automatic gain 値 setting circuit 484. The absolute chirp detection circuit 48 3 detects the signal intensity of the energy component of the output signal output from the A/D converter 33. In addition, in the signal output from the A/D converter 33, since not only the signal (spreading code) component to be detected but also unnecessary signal components such as noise are included, The gain adjustment circuit 48 1 detects the signal intensity of the energy component of the entire detection signal including the unnecessary signal component such as noise. The automatic gain 値 setting circuit 484 is a circuit that controls the gain of the gain adjustment circuit 481 based on the signal strength detected in the absolute snubber circuit 483. The automatic gain 値 setting circuit 484 is connected to the absolute 値 detecting circuit 483 and the gain adjusting circuit 481, and outputs a control signal to the gain adjusting circuit 48 1 . Next, the configuration of the absolute chirp detecting circuit 483 will be described with reference to Fig. 64. The absolute helium detection circuit 483 is provided with an integrator 483a and an integrator 483b connected to an output terminal of the integrator 483a. The totalizer 483 a performs a square calculation on the output signal of the A/D converter 33, and outputs the calculated output signal to the integrator 48 3b. Further, at -133-201122922, at the input terminals of the two accumulators 483a, the output signals of the A/D converter 33 (refer to Fig. 63) are diverged and input, and the mutual signals are multiplied. Further, the integrator 483b integrates the output signal of the totalizer 48 3 a temporally, and outputs the integrated signal as a control signal to the gain adjustment circuit 481 (refer to Fig. 63). As described above, in the setting of the received gain 此 of the modification 26, the signal intensity detection of the signal component including the signal (spreading code) component to be detected and the signal including the noise or the like is detected. Come out and set the received gain 根据 according to the signal strength. In this case, even when noise or the like is superimposed on the input signal input to the gain adjustment circuit 48 1 , the received gain can be appropriately set. In addition, the absolute detection can be performed by any method as long as it can detect the level of the signal including the signal component to be detected and the noise. For example, in addition to the above-described methods, an absolute method of integrating the level of the output signal may be used. Further, in the absolute 値 detection processing, any of the digital signal processing after the A/D conversion and the analog signal processing before the A/D conversion can be used. [Variation 27] In addition, as described above, the pointer detecting device of the present invention is capable of simultaneously detecting a plurality of indicators such as a finger to be detected. Therefore, the pointer detecting device of the present invention may be, for example, a case where a plurality of users simultaneously use or a user of one person operates with both hands. As a result, it is conceivable that the sensing unit -134-201122922' may be used in order to be able to use a plurality of indicators. In the above-described embodiment and various modifications, a configuration example in which the spread code Ck is supplied from the end of one of the transmission conductors 12 is explained. However, if the sensory unit is enlarged, it is due to the spread code.
Ck之傳輸路徑的送訊導體12以及身爲輸出訊號之傳輸路徑 的受訊導體14會隨著感測部之大型化而變長，因此，會產 生展頻碼Ck之由於傳輸路徑的浮游電容所導致的輸出訊號 之準位降低或者是檢測訊號之相位延遲等的問題。針對此 問題’一面參考圖6 5 ( a )以及（b ) —面更具體地作說明 〇 於此，圖65 ( a )，係爲對於將展頻碼Ck供給至任意 之送訊導體¥1^處時的模樣作展示之圖，圖65(b)，係爲 對於在將展頻碼Ck供給至送訊導體Yk處時之藉由各受訊導 體1 4所得到的檢測訊號之準位之間的比之變化作展示之圖 。另外，在圖65(b)中，橫軸係爲受訊導體14之位置， 縱軸係爲檢測訊號之準位與相位。又，在圖6 5 ( b )中， 係爲了將說明簡略化，而對於在從受訊導體Xm、Xm + 2 ' Xm + 4、Xm + 6以及Xm + 8之5根的受訊導體14而來之檢測訊號 處的變化作展示。 如圖65 (a)中所示一般，若是從送訊導體Yk之其中 —方的端部（於圖65 ( a )之例中，係爲送訊導體1 2之右 端）而供給身爲供給訊號之展頻碼Ck，則由於身爲傳送路 徑之送訊導體Yk的浮游電容之影響，若是越從展頻碼匕之 -135- 201122922 供給側而遠離（亦即是，從接近供給側之受訊導體Xm + 8起 而越朝向遠離供給側之受訊導體xm )，則從受訊導體1 4而 來之檢測訊號的準位係降低。同樣的，輸出訊號之相位延 遲，亦係隨著位置越遠離展頻碼ck2供給側而變得越大。 其結果，如圖65 ( b )中所示一般，從受訊導體Xm + 8 起而朝向Xm，輸出訊號之訊號準位與相位係均降低。如此 這般，在接近展頻碼ck之供給側的受訊導體Xm + 8與較遠之 受訊導體Xm之間所產生的輸出訊號之訊號準位差或者是相 位差，係會導致在位置檢測時之相關値無法適當地被取得 ，並會導致檢測感度之降低。特別是，當在送訊導體1 2以 及受訊導體14處而使用有ITO膜之，感測部的情況時，該些 之導體的電阻値係爲高，而輸出訊號之訊號準位的降低或 是相位延遲係會顯著地出現。 因此，在此變形例27中，係參考圖66，而針對能夠解 決上述之問題的展頻碼之供給方法作說明。於此，圖6 6 ( a)以及（b )，係爲對於在此變形例26中之展頻碼Ck的供 給形態以及輸出訊號之準位與相位的變化特性分別作展示 之圖。 此變形例27與上述之實施例以及變形例之間的相異點 ，係如同圖66 ( a)中所示一般，在於從1個的送訊導體Yk 之兩端而同時性地供給相同之展頻碼Ck之點處。爲了實現 此供給形態，例如，係在第1實施形態之構成中，將展頻 碼供給電路（參考圖1 )之各輸出端子與送訊導體¥)4的 兩端作連接。 -136- 201122922 如此這般’右是從送訊導體Y k之兩端來同時性地供給 相同之展頻碼Ck ’則相較於僅從送訊導體Yk之其中一方的 端部來供給展頻碼Ck的情況’從展頻碼Ck2供給側（送訊 導體12之兩端）起直到存在於最遠之位置處的受訊導體14 (於此圖66(a)中，係爲受訊導體Xm + 4 )，爲止的距離，係 成爲一半。其結果’如圖66(b)中所示一般，輸出訊號 之準位，雖然係在距離展頻碼C k之供給側（送訊導體i 2之 兩端）最遠的受訊導體Xm + 4處而成爲最小，但是，相較於 僅從其中一方的端部來供給展頻碼Ck的情況，係能夠將輸 出訊號之訊號準位作改善，而能夠將受訊導體1 4間之準位 差或者是相位差大幅度地減少，並且能夠對於檢測感度之 降低作抑制。 〔變形例28〕 在變形例2 8中，係針對在本發明之指示體檢測裝置中 而適合於檢測出當手指等之指示體在感測部之檢測面上作 了接觸時之推壓力（以下，稱爲指示壓力）的手法作說明 〇 在先前技術之手法中，指示壓力，係根據在感測部之 檢測面處的與指示體間之接觸面積來作計算。然而，在此 手法中，會產生下述一般之問題：亦即是，例如手指較細 的使用者’就算是對於感測部之檢測面強力地作接觸，亦 由於此時之接觸面積爲小，而會被辨識爲較輕的接觸。 因此’在此變形例2 8中，係爲了解決上述一般之問題 -137- 201122922 ’而使用在指不體之位置檢測時所得到的各交叉點處之檢 測訊號（相關値）的準位之空間分布（映射資料），來檢 測出指示壓力》以下’參考圖1、圖6 7以及圖6 8，對於該 手法作具體作說明。另外，此指示壓力之檢測，係藉由受 訊部300之位置檢測電路35(參考圖1)來進行。 於圖6 7中’對於當指示體對於感測部之檢測面（參考 圖2等）作了接觸時之被記憶在相關値記憶電路34d (參考 圖8 )中的訊號（相關値）之準位的空間分布之模式圖作 展示。圖67中之橫軸’係代表受訊導體14之位置，圖面上 之從[方而朝向深處的方向之軸’係代表送訊導體12之位 置’而，圖6 7中之縱軸，係代表檢測訊號（相關値）之準 位。另外’縱軸之準位，係爲作了正規化之値。又，在圖 67所示之例中’係對於指示體正在送訊導體γη與受訊導體 Xm之交叉點上作接觸的情況時之檢測訊號的準位之空間分 布作展示’並且’爲了使說明簡略化，而僅對於藉由送訊 導體Υη·4〜 Yn + 4與受訊導體Xm-4〜Xm + 4所包圍的區域中之 準位的空間分布作展示。 首先’位置檢測電路3 5，係將被記憶在相關値記憶電 路3 4d中的訊號之映射資料讀出，並藉由對於在各交叉點 處之輸出訊號的訊號準位施加內插處理等，而對於各交叉 點間之訊號準位作內插，而計算出在指示體所作了接觸的 交叉點〔Xm，Yn〕上之成爲頂點（或者是頂上）的山形狀 之準位曲面490。另外，在圖67所示之例中，雖係對於在 各交叉點處之輸出訊號的訊號準位而施加內插處理等並產 -138- 201122922 生準位曲面490，但是，亦可設爲：將對於在每—交叉點 處所求取出的相關値施加內插處理後所得到的資料作爲& 射資料而保存在相關値記憶電路3 4 d中，並且由此被作了 內插處理之映射資料來產生準位曲面490。 接著，進行藉由特定之準位面490a (圖67中之斜線區 域）來將準位曲面490作切割之訊號處理。進而，進行求 取出藉由準位曲面490所包圍了的區域之體積的訊號處理 。另外，於此，係將特定之準位面490a的面積，設爲指示 體之接觸面積。 於此’一面參考圖68，一面對於簡易地求取出被準位 曲面4 9 0所包圍了的區域之體積的手法作說明。首先，將 準位曲面490，分割爲沿著送訊導體12之延伸方向的方向 之平面（圖6 7之狀態）。藉由此，如圖6 8中所示一般，例 如，係沿著送訊導體Υ η . 4〜Υ η + 4之延伸方向，而分別產生 有分割平面491〜499。 接著，將分割平面491〜499之面積Sa,〜Sa9分別求取 出來。而後，將算出了的面積S a !〜S a 9作加算，並將該加 算値作爲被準位曲面4 9 0所包圍了的區域之體積的近似値 。被此準位曲面490所包圍之區域的體積，係爲與指示壓 力相對應的値，若是指示壓力變大，則該體積亦會增加。 故而’係可根據被此準位曲面490所包圍了的區域之體積 ’來求取出指示壓力。於此變形例2 8中，係藉由進行此種 訊號處理來求取出指示體之指示壓力。 另外，亦可將如同上述一般所求取出之被準位曲面 -139- 201122922 490所包圍的區域之體積，更進而以接觸面積來作除算。 於此情況’係求取出與接觸區域之每單位面積的指示壓力 相對應之値。 如同上述一般，在此變形例2 8中，係當指示體與感測 部100之檢測面作了接觸時，在位置檢測電路處而算出檢 測訊號（相關値）之3維的準位曲面，並將被該準位曲面 所包圍之區域的體積計算出來，而特定出指示壓力。故而 ，係能夠解決上述之在先前技術之指示壓力的檢測方法中 所產生之問題，並成爲能夠檢測出與使用者之接觸感相對 應的指示壓力。 在上述之指示壓力的檢測手法中，雖係設爲：將準位 曲面490分割爲複數之平面，並將該複數之分割平面的面 積之合計値（亦即是積分値）設爲該準位曲面490之體積 ，但是，本發明係並不被限定於此。爲了將準位曲面490 之體積以更良好的精確度而計算出來，亦可數値解析性地 來對於準位値作權重加算。進而，體積之計算方法，係並 不被限定於作了分割的平面之合計値，亦可設爲適用多維 曲面近似（例如梯形近似或是平方近似等）來對體積作計 算。 於此，在對於分割平面之面積進行權重加算的方法中 ，針對使用梯形近似來求取出被準位曲面490所包圍之區 域的體積之處理程序，一面參考圖69 —面作說明。 圖69，係爲對於送訊導體12之位置與藉由在圖68中所 說明了的手法而求取出之準位曲面490的分割平面491〜 140 - 201122922 499之面積Sai〜Sa9之間的關係作展示之圖表。另外，在此 圖69中，橫軸係爲送訊導體12之位置，縱軸係爲分割平面 之面積。圖69中之曲線495，係爲將面積Sai〜Sa92資料點 作了連結者。 被準位曲面495所包圍之區域的體積，係相當於由圖 69中之橫軸與曲線495所包圍之部分的面積。又，在圖69 之特性中，若是將面積Sai〜Sa9之資料點間用直線來作連 結，則在送訊導體Yn_2〜Yn + 2之間的區域處，係被形成有4 個的梯形區域》在梯形近似中，係將被圖69中之橫軸與曲 線49 5所包圍之部分的面積，近似爲在圖69中之送訊導體 Υη-2〜Υη + 2之間所產生之4個的梯形區域之面積的合計値（ 圖68中之斜線部的面積）。更具體而言，係如同下述一般 地而求取出體積。 首先，對於圖69中之構成斜線部區域的資料點Sa3〜 S a7 ’依據梯形近似而附加權重値。例如，係對於資料點 S a3附加權重1，並同樣的對於資料點S a4附加權重2，對於 資料點Sa5附加權重2，對於資料點Sa6附加權重2，對於資 料點Sa7附加權重1。而後，準位曲面490之體積Vl，係將 「附加了權重之分割平面的面積之合計値」，藉由「被包 含於各梯形中之權重値的平均値」來作除算，而求取出來 。亦即是，準位曲面490之體積V,，係成爲： 體積 V^nxSas + OSaeSxSas + SxSadlxSa?)/^。 於此，「權重値之平均値」（上述式中之分母的値）， 係藉由將「各資料點之權重値的合計」除以r梯形之數量 -141 - 201122922 」而求取出來，於此例中，係成爲（1+2 + 2 + 2 + 1)/2 = 4。 若是使用上述之梯形近似的方法，則由於圖69中之構 成4個的梯形之斜邊與曲線495之間的誤差係爲小，因此， 使用梯形近似所得到之計算結果（斜線部之面積）與實際 的準位曲面490之體積，其兩者間的誤差係變小。故而， 藉由使用此手法，能夠較爲正確地求取出準位曲面490之 體積。又，藉由使用此種近似計算來求取出準位曲面490 之體積，能夠將施加於位置檢測電路35處之負荷降低。 又，在上述之對於分割平面進行權重加算的方法中， 代替梯形近似，亦係可使用平方近似。於此情況，係對於 圖6 9中之構成斜線部區域的資料點S a3〜S a7，依據平方近 似而附加權重値。例如，係對於資料點Sa3附加權重1，並 同樣的對於資料點S a4附加權重4，對於資料點S a5附加權重 2，對於資料點Sa6附加權重4，對於資料點Sa7W加權重1。 於此情況，準位曲面490之體積V2，係成爲： 體積 V2 = (lxSa3 + 4xSa4 + 2xSa5 + 4xSa6+lxSa7)/3。 於此，「權重値之平均値」（上述式中之分母的値） ，係藉由將「各資料點之權重値的合計」除以「梯形之數 量j而求取出來，於此例中，係成爲（1+4 + 2 + 4+1)/3 =4。 〔變形例29〕 在至此爲止所說明了的各實施形態以及變形例中，係 設爲使用較送訊導體12之根數而更少的數量之展頻碼Ck， 並對於此複數之展頻碼Ck作切換而供給至送訊導體12處之 -142- 201122922 構成’但是，例如，亦可設爲下述之構成：亦即是，使用 與送訊導體12之根數相等的種類之複數的展頻碼Ck，並使 各個的展頻碼Ck與送訊導體12作一對一的對應，藉由此， 而成爲並不封於供給展頻碼C1{之送訊導體1 2作切換。 圖70’係爲對於使用與送訊導體之數量相同數量的展 頻碼，並將各個的展頻碼分別供給至相異之送訊導體處的 情況作例示之圖。故而，與圖20中所示之第2實施形態相 同的，在此變形例29中，圖1中所示之送訊導體選擇電路 22係成爲不必要。 於此，在此變形例29中，由於係對於送訊導體1 2，而 供給與送訊導體12相同數量（亦即是64種類）之相異的展 頻碼Ck ’因此，展頻碼心之碼片數，係成爲需要較在第1 實施形態等之中所說明了的1 6碼片而更長的碼片數之例如 64碼片以上的碼片數。 圖71，係爲對於此變形例29中之相關値算出電路334 的構成作展示之圖。在此變形例29中之相關値算出電路 3 34、和在第1實施形態中之相關値算出電路34，其兩者間 之相異點，係在於：構成被設置在相關値算出電路334中 之訊號延遲電路3 3 4a的D-正反器電路之數量，係爲由64個 的D-正反器電路3 3 4ai~ 3 34a64所構成，以及，用以算出相 關値之相關器3 3 4b、和將相關値演算用碼供給至此相關器 3 3 4b處之相關値演算用碼產生電路3 3 4c，係各被設置有與 展頻碼Ck相同數量個（亦即是，各被設置有64個）。 相關値算出電路334，係藉由該些之64個的相關器 -143- 201122922 3 34bi、3 3 4b2、3 3 4b3、…3 3 4b64之各個，而將圖71中所示 之64個的展頻碼Ci〜C64和與各展頻碼相對應的相關値演 算用碼C , a ’〜C^a ’作乘算’並個別地計算出各展頻碼之相 關値。亦即是，係藉由以相關器3 3 4b !來將展頻碼C ,與相 關演算碼C ! A ’作乘算’而檢測出相關値，並藉由以相關器 3 3 4b2來將展頻碼C2與相關演算碼c 2 a ’作乘算，而檢測出相 關値’以下，同樣的’而將關於64個的全部之展頻碼Ci〜 Cm的相關値計算出來。所計算出之各個的相關値，係被 記憶在相關値記憶電路3 3 4d中。 當藉由此圖71中所示之相關値算出電路334而算出相 關値的情況時’由於係並不需要對於供給展頻碼Ck之送訊 導體12作切換，因此，係能夠將送訊部200之構成更加簡 潔化。 另外，在此變形例2 9中，雖係對於使用有與送訊導體 12之根數相同數量的展頻碼Ck的情況而作了例示說明，但 是，本發明係並不被限定於此情況。例如，亦可如同變形 例1 3 (參考圖4 1 )—般地，而例如對於相鄰接之2根的送 訊導體1 2供給相同之展頻碼Ck。於此情況，係並不需要使 用與送訊導體1 2相同數量之展頻碼Ck，亦即是，於此情況 ，藉由使用半數（32個）的展頻碼Ck，便能夠得到相同的 效果。 〔變形例3 0〕 另外，當指示體在送訊導體和受訊導體間之交叉點處 -144- 201122922 而作了接觸時，在該交叉點處所產生的電容値之變化，係 成爲極爲微小。例如，當指示體1 9並未在感測部1 00上作 接觸時，該交叉點之電容係爲〇.5pF，相對於此，當指示 體1 9作了接觸時，在該交叉點處之電容値的變化，係成爲 約0.05pF左右。 例如，當對於送訊導體1 2而供給了 2η碼片長度之碼列 的情況時’於任意一個的受訊導體1 4處所得到的輸出訊號 之訊號準位，係在當被供給至各送訊導體12處之碼列的第 m碼片（m爲1以上η以下之自然數）均以「1」來作了供給 的情況時’會成爲最大。此係因爲，輸出訊號之訊號準位 ’是與將各交叉點之電容値和被供給至該些之各交叉點處 之碼片作乘算後所得之値的合計値成正比之故。故而，例 如，當供給有如圖17 (a)中所示一般之16碼片長度的哈 德瑪得碼的情況時，從受訊導體1 4所得到之輸出訊號的訊 號準位’係在該16碼片長度之哈德瑪得碼的前端碼片被供 給至受訊導體14處時而成爲最大。 另一方面’當指示體1 9正與交叉點作接觸時所得到的 輸出訊號之訊號準位，係成爲從當指示體19並未與交叉點 相接觸時所得到的輸出訊號（電流訊號）中而減去了在該 交叉點處經由指示體1 9所分流的電流訊號後之値。如同上 述一般’當指示體19與交叉點作了接觸時之在該交叉點處 的電容値之變化量，由於係爲微小，因此，電流訊號之變 化量係成爲微小。爲了將此微小的電流訊號之變化檢測出 來’在放大電路處’係成爲必須要使用放大率爲高之放大 -145- 201122922 器。 然而’若是使用具備有適合於指示體19正在作接觸時 所得到之輸出訊號的放大率之放大器，則會產生新的問題 ，亦即是，在該1 6碼片長度之哈德瑪得碼的前端碼片被供 給至受訊導體1 4時所得到的輸出訊號，係會被作箝制（ clip)。然而，若是使用具備有適合於在該16碼片長度之 哈德瑪得碼的前端碼片被供給至受訊導體1 4時所得到的輸 出訊號的放大率之放大器，則會產生下述之問題，亦即是 ，會無法檢測出微小的輸出訊號之變化。 當將互爲相異之2n碼片長度的碼列分別供給至送訊導 體1 2處的情況時，在各碼列之第m碼片全部成爲“丨”時，由 於係會產生上述問題，因此，若是設爲並不將此第m碼片 之碼供給至送訊導體1 2處，則能夠將輸出訊號之訊號準位 的最大値抑制爲較低。具體而言，若是供給圖1 7 ( b )中 所示之1 5碼片長度的哈德瑪得碼，則係能夠對於輸出訊號 之最大値，而作與被供給至各送訊導體1 2處之哈德瑪得碼 的數量（當此圖1 7 ( b )中所示之哈德瑪得碼的情況時， 係爲「1 6」）同等之量的抑制。如此一來，在將此1 5碼片 長度之哈德瑪得碼供給至送訊導體1 2處的情況下，當在該 受訊導體14之任一者的交叉點處均未被放置有指示體19時 所得到的相關値之準位（以下，將此一定値之輸出訊號， 稱作「基準準位」），亦能夠被抑制爲較低。 然而，在將此15碼片長度之哈德瑪得碼供給至送訊導 體1 2處的情況時，會產生有新的問題，亦即是，若是指示 -146- 201122922 體1 9在任一者的交叉點處而作接觸，則基準準位係會變動 。此係因爲，相較於16碼片長度之哈德瑪得碼，由於碼長 度係短了 1碼片，因此，若是指示體19在15碼片長之哈德 瑪得碼處而於交叉點上作接觸，則基準準位係會作在此交 叉點而分流至接地處之電流的量之上升之故。因此，當指 示體1 9同時地對於複數之交叉點而作了接觸的情況時，基 準準位係會作與指示體1 9所接觸之交叉點的數量成正比之 變動。 另外，關於指示體19是否與交叉點作接觸一事的判定 ，例如，係藉由將輸出訊號之訊號準位與特定之臨限値作 比較一事，而進行之（參考圖1 6 )。本發明之指示體檢測 裝置，由於係能夠將複數之指示體同時性地檢測出來，因 此，例如，係可考慮有將手掌放置在感測部1 00之上或者 是使複數之指示體（例如複數之手指）在同一之受訊導體 1 4上的複數之交叉點處而同時作接觸的情況。於此種情況 中，從受訊導體I4而來之輸出訊號的基準準位，係會大幅 度的變動。其結果，在指示體1 9所正在作接觸之交叉點處 的相關値之準位亦會大幅度的變動，並會有成爲不會超過 臨限値而造成誤判定的情形。 以下，參考圖72以及圖73，針對用以解決上述問題之 變形例3 0作說明。在此變形例3 0中之指示體檢測裝置3， 和第1實施形態中之指示體檢測裝置（參考圖1 )，其兩者 間之相異點，係在於：指示體檢測裝置3，係爲了將從展 頻碼供給電路21而供給至感測部1〇〇處的展頻碼ck中之1個 -147- 201122922 的展頻碼直接地供給至放大電路3 3 2處’而將展頻碼供給 電路21與放大電路332作了連接。另外’爲了避免圖面之 複雜化，在圖73中，係將受訊導體選擇電路31之圖示作了 省略。又，爲了能夠更易於理解，係僅對於感測部1 00上 之送訊導體Yi'Yii與受訊導體Xi23〜X128作交叉的區域作 展示，並對於將展頻碼匕供給至送訊導體Y!〜Y6之各個處 且將從受訊導體Χ123〜Χ128而來之輸出訊號檢測出來的情 況作例示說明。進而，針對與第1實施形態中之指示體檢 測裝置1相同的構成，係附加同樣的符號，並省略其說明 〇 首先，如同圖72中所示一般，展頻碼供給電路21，係 除了被與送訊導體選擇電路22、時脈產生電路23、相關値 算出電路34、以及控制電路40作連接之外，亦被與放大電 路332作連接。而，係將構成展頻碼供給電路21之複數的 展頻碼產生電路24中之例如任意一個的展頻碼產生電路24 與放大電路332相連接。從此一被與放大電路332直接作了 連接的展頻碼產生電路24所輸出之展頻碼、例如展頻碼Q ，係並不經由送訊導體1 2地而直接供給至受訊部3 4 0之放 大電路3 3 2處’藉由此’而將此展頻碼c ι作爲相關特性之 基準準位的校正訊號（參考訊號）來使用。 根據圖7 3 ’針對此變形例3 〇中之受訊部3 4 〇作說明。 放大電路332，係由與受訊導體14相同數量之ι/ν變換電 路332a、和與此i/v變換電路332a相同數量之電容器332b ’而構成之。電容器33 2b’係被設置在產生展頻碼匕之展 -148- 201122922 頻碼產生電路24(未圖示）與i/v變換電路332a之間。故 而，展頻碼匚！，係經由此電容器3 32b而被供給至各1/ V變 換電路332a處。另外，產生其他之展頻碼（：2〜（：7的展頻碼 產生電路24，係分別被與送訊導體γ ,〜γ6作連接。其結果 ，展頻碼C !，係成爲經由電容器而被直接性地供給至構成 放大電路3 3 2之各I/V變換電路3 3 2a處。 藉由將展頻碼C,供給至電容器3 32b處，在各1/V變換 電路332a處，經由受訊導體14所輸出之輸出訊號、和藉由 將展頻碼h供給至電容器3 3 2b處一事所產生的電流訊號（ 校正訊號），係被作合成輸入。此一被與校正訊號作了合 成的輸出訊號，係在各I/V變換電路332a處而被變換爲電 壓訊號，並被作放大輸出。 A/D變換電路333，係由與構成放大電路332之I/V 變換電路3 3 2 a相同數量的A/D變換器3 3 3 a所構成。此些各 A/D變換器333a，係分別被與相對應之各I/V變換電路 3 32a相連接。而，在各1/V變換電路3 32a處而被輸出的電 壓訊號，係被輸入至各A/D變換電路333a中並被變換爲數 位訊號，而被輸出至相關値算出電路3 5 (參考圖7 2 )處。 相關値算出電路3 4，係藉由與各展頻碼相對應之相關 値演算用碼，而進行相關演算。於此，展頻碼C!，由於係 並不經由送訊導體12以及受訊導體14地而直接被輸入至構 成受訊部34〇之放大電路332中，因此，在展頻碼C!之訊號 成分中，係並不存在有經由送訊導體12以及受訊導體14所 產生的變動因素。其結果，由與展頻碼C !相對應之相關値 -149- 201122922 演算用碼c, ’所進行的相關演算之結果（亦 ’係成爲恆常安定的一定之値。 而’在此變形例3 0中，係將此一定之相 準位來使用。亦即是，相關値算出電路3 4， D變換電路3 3 2所輸入之各數位訊號，而進行 相關値演算用碼C t ’所致之相關演算。而後 關演算所得到了的相關値，作爲相關特性之 例如記憶在相關値記憶電路3 4d (參考圖8 ) 關値算出電路3 4，係與上述第1實施形態相 各展頻碼C2〜C 7分別相對應的相關値演算月 進行相關演算，並將身爲演算結果之相關値 記憶電路3 4 d處。 之後，位置算出電路35(參考圖1)， 在相關値記億電路34d中之針對各展頻碼C2 的相關値、和身爲相關特定之基準準位的相 定之臨限値，來對於指示體1 9是否正在感名 觸一事作判定。具體而言，位置算出電路3f 各展頻碼C2〜C 7所算出了的相關値來減去相 準位的値之後的値計算出來。而後，位置算 藉由將此減算後之値與特定之臨限値作比較 測部1 00上是否存在有指示體1 9—事作判定。 如此這般，藉由在複數之展頻碼中’將 並不經由送訊導體12以及受訊導體14地而直 部處，並將該展頻碼作爲相關特性之基準準 即是相關値） 關値作爲基準 係對於從A/ 由展頻碼（^之 ’將藉由此相 基準準位，來 中。之後，相 同的，對於與 碼C2 ’〜C7 ’而 記憶在相關値 係根據被記憶 〜C 7所算出了 關値、以及特 :!!部100上作接 ，係將從針對 關特性之基準 出電路3 5，係 ，而對於在感 特定之展頻碼 接供給至受訊 位的校正訊號 -150- 201122922 (參考訊號）來使用，就算是在基準準位處產生有變動， 亦能夠將由指示體1 9所致之接觸位置正確地檢測出來。 〔變形例3 1〕 另外，在上述變形例3 0中，係針對將從受訊導體而來 之輸出訊號與校正訊號在輸入至A/D變換電路中之前便 作合成（亦即是，在類比訊號之階段來作合成）的情況而 作了例示說明。如此這般，當將校正訊號與輸出訊號在類 比訊號的階段來作合成的情況時，由於係僅藉由設置電容 器3 3 2b便能夠實現，因此，在能夠將電路構成簡潔化一事 上，係爲優良。 然而’此電容器332b，係有必要設定爲與在送訊導體 12與受訊導體14之間所形成之電容器同等程度的電容値。 如同上述一般’在送訊導體12與受訊導體14間之交叉點處 所形成的電容器之容量，由於係成爲約0.5 PF左右之非常 小的容量’因此’要安裝在實際的電路基板上一事，係爲 非常困難。又’在變形例3 0中，由於係將校正訊號與受訊 訊號在類比訊號的階段處而作合成，因此，亦有著容易產 生誤差的問題。 因此’在此變形例3 1中，係針對將校正訊號與a / D 變換電路之輸出訊號（亦即是被變換成數位訊號後之受訊 訊號）作合成的情況來作說明。 參考圖74 ’針對將被變換爲數位訊號後之受訊訊號以 及校正訊號作合成的構成例作說明。在本變形例3丨中，在 -151 - 201122922 A/ D變換電路433與相關値算出電路34 (參考圖72 )之間 ，係具備有：用以將從A/ D變換電路433所輸出之各數位 訊號與被變換爲數位訊號後之校正訊號作合成的加算器群 434、和用以將被使用爲校正訊號之展頻碼直接地供給至 受訊部處之電容器435、和用以將電流訊號變換爲電壓訊 號之1/ V變換電路436、以及用以將校正訊號變換爲數位 訊號之A/ D變換器437。其他之構成，由於係爲與上述變 形例30(參考圖72)成爲相同之構成，因此，在相同之構 成處，係附加相同之號碼，並省略其說明。 藉由將展頻碼C,供給至電容器43 5處，在1/ V變換電 路43 6中係被輸入有電流訊號。此1/ V變換電路436，係將 被輸入了的電流訊號變換爲電壓訊號，並且作放大輸出。 從此1/ V變換電路43 6所輸出之電壓訊號，係在A/D變換 器43 7中而被變換爲數位訊號，並被輸入至加算器群434處 〇 加算器群434，係由與構成A/D變換電路433之A/D 變換電路43 3 a相同數量的加算器434a所構成。各加算器 43 4a，係分別被設置在與各受訊導體14作了連接之A/ D變 換器43 3 a與相關値算出電路34之輸入端子之間，並成爲被 輸入有從各A/ D變換器43 3 a所輸出之被變換爲數位訊號後 的輸出訊號、和在A/ D變換器43 7處而被變換爲數位訊號 後之校正訊號。而，各加算器434a，係成爲將被變換爲數 位訊號後之輸出訊號以及校正訊號作合成（加算）並作輸 出。 -152- 201122922 而，藉由各加算器434a而被與校正訊號作了合成之數 位訊號，係被輸入至相關値算出電路34中。之後，係在此 相關値算出電路34中而被進行相關演算。 在此圖74所示之構成例中，亦與圖73中所示之例相同 的，能夠進行基準準位之調整。在此變形例3 1中，由於係 能夠將校正訊號與受訊訊號藉由數位訊號來作合成，因此 ，在爲了供給校正訊號所設置之電容器43 5中，例如，係 使用8PF之電容器，並在A/D變換器43 7中，將4位元之資 料作位數減少，藉由此，係能夠以相較於藉由類比訊號來 作合成之情況而更高的精確度來進行訊號合成。 另外，在此變形例3 1中，雖係針對作爲用以對於基準 準位作調整之校正訊號而使用1個展頻碼的例子而作了說 明，但是，本發明，係並不被限定於此。例如，係亦可設 爲將2個以上的展頻碼作爲校正訊號來作供給。 【圖式簡單說明】 [圖1 ]本發明之第1實施形態之指示體檢測裝置的槪略 區塊構成圖。 [圖2 ]第1實施形態之指示體檢測裝置的感測部之槪略 剖面圖。 [圖3 ]第1實施形態之指示體檢測裝置的展頻碼供給電 路之槪略構成圖。 [圖4]第1實施形態之指示體檢測裝置的送訊導體選擇 電路之槪略構成圖。 -153- 201122922 [圖5]第1實施形態之指示體檢測裝置的送訊部處之展 頻碼切換動作之說明圖。 [圖6]第1實施形態之指示體檢測裝置的受訊導體選擇 電路之槪略構成圖。 [圖7]用以對於第1實施形態之指示體檢測裝置中的受 訊導體選擇電路之受訊導體之切換動作作說明的說明圖。 [圖8]第1實施形態之指示體檢測裝置的相關値算出電 路之區塊構成圖。 [圖9]第1實施形態之指示體檢測裝置的以時間分割來 進行相關演算之相關値算出電路的區塊構成圖。 [圖1〇]對於第1實施形態之指示體檢測裝置的相關器之 內部構成例作展示的區塊構成圖。 [圖1 1 ]圖1 1 ( a )〜（g )，係爲用以對於第1實施形態 之指示體檢測裝置的各部之動作作說明的時序圖。 [圖1 2]用以對於第1實施形態之指示體檢測裝置中的位 置檢測之原理作說明的說明圖。 [圖1 3 ]用以對於第1實施形態之指示體檢測裝置中的位 置檢測之原理（不存在有指示體之狀態）作說明的說明圖 〇 [圖14]用以對於第1實施形態之指示體檢測裝置中的位 置檢測之原理（存在有指示體之狀態）作說明的說明圖。 [圖1 5]用以對於第1實施形態之指示體檢測裝置中的位 置檢測之原理（在複數之交叉點處存在有指示體之狀態） 作說明的說明圖。 -154- 201122922 [圖1 6]對於在圖1 5所示之狀態下所檢測出來的輸出訊 號之例作展示的說明圖，圖1 6 ( a )係爲對於從受訊電極 Yi〜Y4所輸出之輸出訊號與碼編號之間的關係作展示之圖 ，圖1 6 ( b )係爲對於從受訊電極Y 5〜Y64所輸出之輸出訊 號與碼編號之間的關係作展示之圖。 [圖17]圖17 ( a)係爲對於16碼片長度之哈德瑪得碼（ Hadamard code )的例子作展示之圖，圖17(b)係爲對於 15碼片長度之哈德瑪得碼的例子作展示之圖，圖17(c) 係爲對於供給了圖17 ( a)中所示之16碼片長度之哈德瑪 得碼的情況時所得到之輸出訊號與碼編號間之關係作展示 之圖，圖17(d)係爲對於供給了 15碼片長度之哈德瑪得 碼的情況時所得到之輸出訊號與碼編號間之關係作展示之 圖。 [圖1 8 ]對於第1實施形態之指示體檢測裝置中的位置檢 測之處理程序作展示的流程圖。 [圖1 9]圖1 9 ( a )，係爲在本發明之第2實施形態中之 PSK調變前的展頻碼之波形圖，圖19(b)，係爲PSK調變 後之展頻碼的波形圖。 [圖2 0 ]第2實施形態之指示體檢測裝置的槪略區塊構成 圖。 [圖2 1 ]第2實施形態之指示體檢測裝置的展頻碼供給電 路之槪略構成圖。 [圖22]第2實施形態之指示體檢測裝置的相關値算出電 路之區塊構成圖。 -155- 201122922 [圖23]圖23 ( a)，係爲在本發明之第3實施形態中之 FSK調變則的展頻碼之波形圖’圖23(b)，係爲FSK調變 後之展頻碼的波形圖。 [圖2 4 ]第3實施形態之指示體檢測裝置的展頻碼供給電 路之槪略構成圖。 [圖2 5 ]第3實施形態之指示體檢測裝置的相關値算出電 路之區塊構成圖。 [圖26]用以對於變形例1中之展頻碼的供給方法作說明 之說明圖。 [圖27]變形例2中之送訊導體選擇電路的槪略構成圖。 [圖2 8 ]用以對於變形例2中之展頻碼的供給方法作說明 之說明圖。 [圖2 9 ]用以對於變形例3中之展頻碼的供給方法作說明 之說明圖。 [圖30]變形例4中之受訊導體選擇電路的區塊構成圖。 [圖31]用以對於變形例4中之受訊導體選擇電路的切換 動作作說明之說明圖。 [圖32]變形例5之感測部的槪略剖面圖。 [圖3 3 ]圖3 3 ( a )，係爲變形例6之感測部的槪略剖面 圖’圖3 3 ( b )，係爲對於變形例6之感測部的配置例作展 示之立體圖》 [圖34]圖34 ( a)，係爲對於變形例7之送訊導體以及 受訊導體的槪略構成作展示之平面圖，圖34(b)，係爲 對於變形例7之送訊導體的島狀導體部作了擴大之平面圖 -156- 201122922 [圖3 5 ]變形例8之感測部的槪略平面圖。 [圖3 6]變形例9之感測部的槪略平面圖。 [圖37]圖37 ( a)，係爲對於變形例9之感測部處的送 訊導體之透明電極膜的配置作展示之槪略構成圖，圖37 ( b ) ’係爲對於受訊導體之透明電極膜的配置作展示之槪 略構成圖。 [圖3 8 ]變形例1 〇之感測部的槪略構成圖。 [圖39]變形例11之受訊部的區塊構成圖。 [圖40]變形例12之差動放大器的槪略構成圖。 [圖4 1 ]用以對於變形例1 3之展頻碼的供給方法作說明 之槪略構成圖。 [圖42]變形例14之感測部的槪略構成圖。 [圖43]用以與變形例14作比較之感測部的槪略構成圖 〇 [圖44]對於變形例Μ之送訊導體的切換狀態之例作展 示的說明圖。 [圖45]對於變形例14之送訊導體的切換狀態之其他例 作展示的說明圖。 [圖46]對於變形例1 5中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係作展示的模式圖。 [圖47]對於變形例1 6中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖48]對於變形例16中之送訊導體選擇電路的內部構 -157- 201122922 成之例作展示的構成圖。 [圖49]對於變形例16中之受訊導體選擇電路之例作展 示的構成圖》 [圖50]圖50 ( a)，係爲對於變形例17中之送訊部的展 頻碼之送訊形態與受訊部之訊號的受訊形態間之關係作展 示的構成圖’圖50(b)，係爲從差動放大器所輸出之輸 出訊號的波形圖。 [圖5 1 ]對於變形例1 8中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖52]對於變形例1 9中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖53]變形例19之送訊導體選擇電路之例的區塊構成 圖。 [圖54]變形例19之受訊部之例的區塊構成圖。 [圖55]對於變形例20中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖56]圖56 ( a )以及（b )，係爲用以對於在變形例 2 1中之懸浮狀態的辨識原理作說明之說明圖。 [圖57]圖57 ( a )以及（b )，係爲用以對於在變形例 2 1中之懸浮狀態的辨識原理作說明之說明圖。 [圖58]用以對於變形例2 1中之懸浮狀態的辨識原理作 說明之分布圖。 [圖59]對於變形例22中之送訊部的展頻碼之送訊形態 與受訊部之訊號的受訊形態間之關係（檢測區域爲狹窄的 -158- 201122922 狀態）作展示的構成圖。 [圖60]對於變形例22中之送訊部的展頻碼之送訊形 與受訊部之訊號的受訊形態間之關係（檢測區域爲寬廣 狀態）作展示的構成圖。 [圖6 1 ]對於變形例2 4中之送訊部的展頻碼之送訊形 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖62]對於變形例25中之送訊部的展頻碼之送訊形 與受訊部之訊號的受訊形態間之關係作展示的構成圖。 [圖6 3 ]變形例2 6之受訊部之例的區塊構成圖。 [圖64]變形例26之絕對値檢波電路之例的區塊構成 〇 [圖65]圖65(a)，係爲對於將展頻碼從送訊導體之 側而作了供給的情況時之模樣作展示之圖，圖65 ( b ) 係爲對於在該情況下之受訊導體的位置、與檢測訊號之 位以及相位延遲之比（準位/相位），其兩者間的關係 展示之說明圖。 [圖66]圖66(a)，係爲對於在變形例27中，而將展 碼從送訊導體之兩側而作了供給的情況時之模樣作展示 圖’圖66 ( b )，係爲對於在該情況下之受訊導體的位 、與檢測訊號之準位以及相位延遲之比（準位/相位） 其兩者間的關係作展示之說明圖。 [圖6 7 ]用以對於在變形例2 8中之求取出指示體之指 壓力的原理作說明之特性圖。 [圖6 8 ]用以對於在變形例2 8中之求取出指示體之指 能 的 態 態 圖 單 > 準 作 頻 之 置 ) 示 示 -159- 201122922 壓力的原理作說明之特性圖^ [圖69]用以對於在變形例28中之求取出指示體之指示 壓力的原理作說明之特性圖。 [圖70]對於作爲變形例29而將展頻碼準備了與送訊導 體的數量相同之數量的例子作展示之說明圖。 [圖7 1 ]變形例29之相關値算出電路之例的區塊構成圖 〇 [圖72]變形例30之指示體檢測裝置的構成圖。 [圖7 3 ]變形例3 0中之受訊部的槪略構成圖。 [圖74]變形例3 1中之受訊部的槪略構成圖。 [圖75]圖75 ( a)，係爲先前技術之交叉點靜電耦合方 式之指示體檢測裝置的槪略構成圖，圖75(b)，係爲輸 出訊號波形圖。 【主要元件符號說明】 1 ' 2、3 :指示體檢測裝置 1 1、41 1 :送訊導體群 12、 412、 512、 612、 712、 812:送訊導體 13、 413 :受訊導體群 14、 414' 514、 614、 714:受訊導體 15 :第1基板 1 6 :間隔物 17 :第2基板 1 9 :手指（指示體） -160- 201122922 21、 221、222 :展頻碼供給電路 22、 202、382、402:送訊導體選擇電路 22a 、 202a 、 231a、 231b：開關 23 :時脈產生電路 24:展頻碼產生電路 25、125、3 8 3、403 :送訊區塊 26 : P SK調變電路 27: FSK調變電路 31、 131、 231、 384、 404、 415、 813：受訊 電路 3 1 a、1 3 1 a :開關 32、 232、 332、 333、 432 ：放大電路 32a、232a、332a、3 3 3 a ： I/V 變換電路 32b 、 232b 、 532 ：放大器 32c、232 c :電容器 32d、23 2d :切換開關 33、 43 3 : A/ D變換電路 34、 134、3 04、3 14 :相關値算出電路 34a、3 04 a、3 3 4a :訊號延遲電路 34a丨〜34a64、3 04a丨〜304a63: D-正反器電路 3 4b ' 34b!〜34b“、3 4 b x ' 3 04b i 〜3 04b63 ' 334b64_相關器 3 4c ' 34ci 〜34c“、1 3 4 c x、304c〗〜304C64、 3 3 4c64 :相關値演算用碼產生電路 導體選擇 334b1~ 3 3 4 c 1 〜 -161 - 201122922 34d、3 04d、3 3 4d :相關値記憶電路 34f,〜34f16 :乘算器 3 4 g :加算器 3 5 :位置檢測電路 3 6、136、2 3 6 ' 3 3 6 ：檢測區塊 40 :控制電路 100、 400、 500、 600、 700、 800 ：感測部 126 : PSK解調電路 1 27 : FSK解調電路 134e :暫存器 200、201 :送訊部 250 、 350 、 360 、 361 、 386 、 396 、 397 、 405 、 407 420、43 0 :差動放大器 300、301、310、320、330、340 ：受訊部 3 3 2b :電容器 381、406、431 :碼反轉器 382a、 384a、 402a、 815：開關群 382a,〜382a4、402a,~ 402a3 ：開關 4 0 1 :碼反轉器 43 3 a' 43 7： A/ D變換器 43 4 :加算器群 434a :加算器 43 5 :電容器 43 6 : 1/ V變換電路 -162- 201122922 4 8 1 :增益調整電路 4 8 2 :增益値設定電路 48 3 :絕對値檢波電路 48 3 a :積算器 4 8 3 b :積分器 484 :自動增益控制電路 501 ' 6 0 1··基板 5 1 3 :第1保護層 5 1 5 :第2保護層 5 1 6 :保護薄片 5 1 7 :第1透明電極膜 518 :第2透明電極膜 602 :金屬層 6 0 3 :絕緣層 722、 822 ：導體部 723、 8 2 3 :島狀導體部 -163-The transmission conductor 12 of the transmission path of Ck and the signal conductor 14 which is the transmission path of the output signal become longer as the size of the sensing portion increases, and therefore, the floating capacitance of the spreading code Ck due to the transmission path is generated. The resulting level of the output signal is reduced or the phase delay of the detected signal is a problem. For this problem, one side is more specifically described with reference to FIGS. 65(a) and (b). Here, FIG. 65(a) is for supplying the spread code Ck to an arbitrary transmission conductor ¥1. FIG. 65(b) shows the position of the detection signal obtained by each of the received conductors 14 when the spread code Ck is supplied to the signal conductor Yk. The change between the ratios is shown in the map. Further, in Fig. 65 (b), the horizontal axis is the position of the signal conductor 14, and the vertical axis is the level and phase of the detection signal. Further, in FIG. 6 5 (b), for the sake of simplification of the description, for the signal conductor 14 which is 5 from the received conductor Xm, Xm + 2 'Xm + 4, Xm + 6 and Xm + 8 The changes in the detection signal are displayed. As shown in Fig. 65 (a), if it is from the end of the transmitting conductor Yk (in the example of Fig. 65 (a), it is the right end of the transmitting conductor 12), the supply is supplied as a supply. The spread code Ck of the signal is affected by the floating capacitance of the transmission conductor Yk which is the transmission path, and is further away from the supply side of the spread frequency code -135-201122922 (that is, from the supply side) When the received conductor Xm + 8 is directed away from the signal conductor xm away from the supply side, the level of the detection signal from the signal conductor 14 is lowered. Similarly, the phase delay of the output signal is also increased as the position is further away from the supply side of the spread spectrum code ck2. As a result, as shown in Fig. 65 (b), generally, from the signal conductor Xm + 8 and toward Xm, the signal level and the phase system of the output signal are both lowered. In this way, the signal level difference or phase difference of the output signal generated between the signal conductor Xm + 8 on the supply side of the spread spectrum code ck and the remote signal conductor Xm is caused by the phase difference. The correlation at the time of detection cannot be properly obtained, and the detection sensitivity is lowered. In particular, when an ITO film is used at the signal conductor 12 and the signal conductor 14, in the case of the sensing portion, the resistance of the conductors is high, and the signal level of the output signal is lowered. Or the phase delay system will appear prominently. Therefore, in this modification 27, referring to Fig. 66, a method of supplying a spreading code capable of solving the above problem will be described. Here, Fig. 6 (a) and (b) are diagrams showing the supply form of the spread spectrum code Ck and the change characteristics of the level and phase of the output signal in the modification 26 of the present invention. The difference between this modification 27 and the above-described embodiment and modification is as shown in Fig. 66 (a), and the same is simultaneously supplied from both ends of one of the transmission conductors Yk. At the point of the spread code Ck. In order to realize this supply mode, for example, in the configuration of the first embodiment, the output terminals of the spread spectrum code supply circuit (refer to Fig. 1) are connected to both ends of the transmission conductor ¥)4. -136- 201122922 So, the right is that the same spread spectrum code Ck ' is simultaneously supplied from both ends of the transmission conductor Y k compared to the end of only one of the transmission conductors Yk. The case of the frequency code Ck 'from the supply side of the spread code Ck2 (the both ends of the transmission conductor 12) until the received conductor 14 present at the farthest position (in Fig. 66(a), it is received The distance from the conductor Xm + 4 ) is half. As a result, as shown in Fig. 66 (b), the level of the output signal is the farthest conductor Xm + which is farthest from the supply side of the spread code C k (the two ends of the transmission conductor i 2 ). It is the smallest in 4 places. However, compared with the case where the spread spectrum code Ck is supplied from only one of the ends, the signal level of the output signal can be improved, and the received conductor 14 can be quasi-positioned. The difference in phase or phase difference is greatly reduced, and it is possible to suppress the decrease in detection sensitivity. [Variation 28] In the modification of the indicator device of the present invention, it is suitable for detecting the pressing force when the pointer of the finger or the like touches the detection surface of the sensing portion ( Hereinafter, the method of indicating the pressure is explained. In the prior art method, the pressure is indicated based on the contact area with the indicator at the detecting surface of the sensing portion. However, in this method, the following general problem arises: that is, for example, a user whose finger is thinner is in contact with the detecting surface of the sensing portion, and the contact area is small at this time. And will be recognized as a lighter contact. Therefore, in this modification 28, in order to solve the above-mentioned general problem -137-201122922', the level of the detection signal (correlation 値) at each intersection obtained at the position detection of the finger is used. The spatial distribution (mapping data) is used to detect the indicated pressure "below" with reference to Fig. 1, Fig. 6 and Fig. 6, and the specific method is explained. Further, the detection of the indicated pressure is performed by the position detecting circuit 35 (refer to Fig. 1) of the receiving unit 300. In Fig. 67, 'the signal (related 値) that is memorized in the relevant 値 memory circuit 34d (refer to Fig. 8) when the indicator touches the detection surface of the sensing unit (refer to Fig. 2, etc.) A pattern diagram of the spatial distribution of bits is shown. The horizontal axis ' in Fig. 67 represents the position of the signal conductor 14, and the axis from the [square toward the depth direction represents the position of the transmission conductor 12], and the vertical axis in Fig. 67. Is the level of the detection signal (related). In addition, the standard of the vertical axis is the standardization. Further, in the example shown in Fig. 67, 'the spatial distribution of the level of the detection signal when the pointer is in contact with the intersection of the transmission conductor γη and the signal conductor Xm is shown 'and' The description is simplified, and only the spatial distribution of the level in the region surrounded by the transmission conductors ·n4 to Yn+4 and the received conductors Xm-4 to Xm+4 is shown. First, the position detecting circuit 35 reads out the mapping data of the signals memorized in the associated memory circuit 34d, and applies interpolation processing or the like to the signal level of the output signal at each intersection. The signal level between the intersections is interpolated, and a mountain-shaped alignment surface 490 which becomes a vertex (or a top) at the intersection [Xm, Yn] of the contact made by the pointer is calculated. Further, in the example shown in Fig. 67, although the interpolation processing is performed for the signal level of the output signal at each intersection, the -138-201122922 leveling surface 490 is produced, but it may be set to : The data obtained by applying the interpolation processing to the correlation 求 obtained at each intersection is stored as & data in the relevant 値 memory circuit 34 d, and is thereby interpolated. The data is mapped to produce a level surface 490. Next, signal processing for cutting the alignment curved surface 490 by a specific alignment surface 490a (hatched area in Fig. 67) is performed. Further, signal processing for extracting the volume of the area surrounded by the alignment curved surface 490 is performed. Further, here, the area of the specific alignment surface 490a is referred to as the contact area of the pointer. Referring to Fig. 68, a description will be given of a method for easily extracting the volume of the region surrounded by the alignment curved surface 490. First, the alignment curved surface 490 is divided into a plane along the direction in which the transmission conductor 12 extends (the state of Fig. 67). By this, as shown in Fig. 68, for example, it is along the signal conductor Υη. The direction of extension of 4~Υ η + 4 is generated by dividing planes 491 to 499, respectively. Next, the areas Sa, Sa9 of the division planes 491 to 499 are respectively obtained. Then, the calculated area S a !~S a 9 is added, and the added 値 is taken as the approximate 値 of the volume of the area surrounded by the level curved surface 490. The volume of the area surrounded by the level curved surface 490 is the 相对 corresponding to the indicated pressure, and if the indicated pressure becomes large, the volume also increases. Therefore, the indication pressure can be extracted based on the volume of the region surrounded by the alignment curved surface 490. In the modification 28, the indication pressure of the pointer is obtained by performing such signal processing. In addition, the volume of the area surrounded by the positional surface -139-201122922 490 which is generally taken out as described above may be further divided by the contact area. In this case, it is desirable to take out the enthalpy corresponding to the indicated pressure per unit area of the contact area. As described above, in the modified example 28, when the pointer is in contact with the detecting surface of the sensing unit 100, the three-dimensional surface of the detecting signal (correlation 値) is calculated at the position detecting circuit. The volume of the area surrounded by the level surface is calculated and the indicated pressure is specified. Therefore, it is possible to solve the above-described problems occurring in the detection method of the indication pressure of the prior art, and to become an indication pressure capable of detecting the feeling of contact with the user. In the above-described detection method of the indicated pressure, it is assumed that the reference curved surface 490 is divided into a plurality of planes, and the total area 亦 (that is, the integral 値) of the plurality of division planes is set to the level. The volume of the curved surface 490, however, the present invention is not limited thereto. In order to calculate the volume of the alignment curved surface 490 with better accuracy, it is also possible to calculate the weighting for the calibration level analytically. Further, the calculation method of the volume is not limited to the total of the planes in which the division is performed, and the volume can be calculated by applying a multidimensional surface approximation (e.g., trapezoidal approximation or square approximation). Here, in the method of performing weight addition on the area of the division plane, the processing procedure for obtaining the volume of the area surrounded by the alignment curved surface 490 using the trapezoidal approximation will be described with reference to Fig. 69. Figure 69 is a diagram showing the relationship between the positions Sai to Sa9 of the dividing planes 491 to 140 - 201122922 499 of the positional curved surface 490 taken out by the position of the transmitting conductor 12 and the method described in Fig. 68. A chart for display. Further, in Fig. 69, the horizontal axis is the position of the transmission conductor 12, and the vertical axis is the area of the division plane. The curve 495 in Fig. 69 is to link the area Sai~Sa92 data points. The volume of the region surrounded by the alignment curved surface 495 corresponds to the area of the portion surrounded by the horizontal axis and the curved line 495 in Fig. 69. Further, in the characteristics of Fig. 69, if the data points of the areas Sai to Sa9 are connected by a straight line, four trapezoidal regions are formed in the region between the transmission conductors Yn_2 to Yn + 2 In the trapezoidal approximation, the area of the portion surrounded by the horizontal axis and the curve 49 5 in Fig. 69 is approximately 4 which is generated between the transmission conductors Υn-2 to Υη + 2 in Fig. 69. The total area of the trapezoidal area (the area of the hatched portion in Fig. 68). More specifically, the volume is taken out as generally described below. First, the data points Sa3 to S a7 ' constituting the hatched area in Fig. 69 are added with weights 依据 according to the trapezoidal approximation. For example, a weight 1 is added to the data point S a3 , and a weight 2 is added to the data point S a4 , a weight 2 is added to the data point Sa5 , a weight 2 is added to the data point Sa6 , and a weight 1 is added to the data point Sa7 . Then, the volume V1 of the alignment curved surface 490 is obtained by subtracting the "average of the weights of the division planes included in the respective trapezoids" by the "average of the weights of the division planes added to the respective trapezoids". . That is, the volume V of the level surface 490 is: volume V^nxSas + OSaeSxSas + SxSadlxSa?)/^. Here, the "average weight of the weights" (the denominator of the above formula) is obtained by dividing "the total weight of each data point" by the number of r trapezoids -141 - 201122922". In this case, it is (1+2 + 2 + 2 + 1)/2 = 4. If the trapezoidal approximation method described above is used, since the error between the oblique sides of the four trapezoids and the curve 495 in FIG. 69 is small, the calculation result obtained by the trapezoidal approximation (the area of the oblique line portion) is used. With the volume of the actual level surface 490, the error between the two becomes smaller. Therefore, by using this method, the volume of the reference curved surface 490 can be relatively accurately obtained. Further, by using such an approximate calculation to extract the volume of the reference curved surface 490, the load applied to the position detecting circuit 35 can be reduced. Further, in the above method of performing weight addition on the division plane, instead of the trapezoidal approximation, a square approximation may be used. In this case, the weight points 附加 are added to the data points S a3 to S a7 constituting the hatched area in Fig. 69 in accordance with the square approximation. For example, the weight 1 is added to the data point Sa3, and the weight 4 is added to the data point S a4, the weight 2 is added to the data point S a5 , the weight 4 is added to the data point Sa6 , and the weight is 1 for the data point Sa7W. In this case, the volume V2 of the level curved surface 490 is: volume V2 = (lxSa3 + 4xSa4 + 2xSa5 + 4xSa6 + lxSa7) / 3. Here, the "average weight of 値" (the 分 of the denominator in the above formula) is obtained by dividing "the total weight of each data point" by the number of trapezoids j. In this example, (1 + 4 + 2 + 4 + 1) / 3 = 4. [Modification 29] In each of the embodiments and modifications described so far, it is assumed that the root of the communication conductor 12 is used. The number and the smaller number of the spread code Ck are switched to the -140-201122922 which is supplied to the transmission conductor 12 by switching the plural spread code Ck. However, for example, it may be configured as follows. That is, a plurality of spreading codes Ck of the same type as the number of the transmitting conductors 12 are used, and each of the spreading codes Ck and the transmitting conductor 12 are one-to-one correspondence, thereby The transmission conductor 1 2 is not sealed to the supply spread spectrum code C1. Figure 70 is the same number of spread spectrum codes used for the number of transmission conductors, and the respective spread codes are respectively supplied to The case of the different communication conductors is illustrated as an example. Therefore, the same as the second embodiment shown in Fig. 20, In the twenty-ninth embodiment, the transmission conductor selection circuit 22 shown in Fig. 1 is unnecessary. Here, in the modification 29, since the transmission conductor 12 is supplied, the same amount as the transmission conductor 12 is supplied. (that is, 64 types) of the different spreading code Ck'. Therefore, the number of chips of the spreading code center needs to be longer than the 16 chips described in the first embodiment and the like. The number of chips is, for example, the number of chips of 64 chips or more. Fig. 71 is a view showing the configuration of the correlation 値 calculation circuit 334 in the modification 29. The correlation 値 calculation circuit in the modification 29 3, 34, and the correlation calculation circuit 34 in the first embodiment, wherein the difference between the two is: D-positive of the signal delay circuit 3 3 4a provided in the correlation calculation circuit 334 The number of inverter circuits is composed of 64 D-reactor circuits 3 3 4ai~ 3 34a64, and correlators 3 3 4b for calculating correlations and supplying related calculus codes thereto. The correlation 値 calculation code generating circuit 3 3 4c at the correlator 3 3 4b is set to be associated with the spreading code Ck The number (that is, each is set to 64). The correlation calculation circuit 334 is based on the 64 correlators - 143 - 201122922 3 34bi, 3 3 4b2, 3 3 4b3, ... 3 3 4b64, and the 64 spreading codes Ci to C64 shown in FIG. 71 and the associated 値 calculation codes C, a '~C^a ' corresponding to the respective spreading codes are multiplied and individually Calculate the correlation 各 of each spread spectrum code, that is, detect the correlation 藉 by multiplying the spread code C and the associated calculus code C ! A ' by the correlator 3 3 4b ! And by using the correlator 3 3 4b2 to multiply the spreading code C2 and the related calculation code c 2 a ', the correlation 値 'below, the same ', and about 64 of all the spreading codes Ci will be detected. ~ Cm related 値 is calculated. The respective correlations calculated are stored in the associated memory circuit 3 3 4d. When the correlation 値 is calculated by the correlation 値 calculation circuit 334 shown in FIG. 71, 'the transmission unit 12 for supplying the spread code Ck is not required to be switched. Therefore, the transmission unit can be switched. The composition of 200 is more succinct. Further, in the modification 29, the case where the same number of the spreading code Ck as the number of the transmission conductors 12 is used is exemplified, but the present invention is not limited to this case. . For example, it is also possible to supply the same spread code Ck, for example, to the adjacent one of the two communication conductors 12, as in the modification 13 (refer to Fig. 4 1 ). In this case, it is not necessary to use the same number of spreading codes Ck as the transmitting conductor 12, that is, in this case, by using half of the (32) spreading codes Ck, the same can be obtained. effect. [Modification 30] In addition, when the pointer is contacted at the intersection between the signal conductor and the signal conductor at -144 to 201122922, the change in the capacitance 产生 generated at the intersection becomes extremely small. . For example, when the indicator body 19 is not in contact with the sensing portion 100, the capacitance of the intersection is 〇. 5pF, in contrast, when the pointer 19 is in contact, the change in capacitance 在 at the intersection becomes about 0. Around 05pF. For example, when a code train of 2 n chip length is supplied to the transmission conductor 12, the signal level of the output signal obtained at any one of the received conductors 14 is supplied to each of the signals. When the mth chip of the code train at the conductor 12 (m is a natural number of 1 or more and η or less) is supplied with "1", it will become the largest. This is because the signal level ' of the output signal' is proportional to the sum of the capacitances of the intersections and the sum of the chips supplied to the intersections. Therefore, for example, when a Hadamard code having a length of 16 chips as shown in Fig. 17 (a) is supplied, the signal level of the output signal obtained from the signal conductor 14 is attached to The front end chip of the Hadmaard code of 16 chip length is supplied to the signal conductor 14 to be maximized. On the other hand, the signal level of the output signal obtained when the pointer 19 is in contact with the intersection is the output signal (current signal) obtained when the indicator 19 is not in contact with the intersection. The enthalpy after the current signal shunted by the indicator 19 at the intersection is subtracted. As described above, the amount of change in the capacitance 在 at the intersection when the indicator 19 is in contact with the intersection is small, and therefore the amount of change in the current signal is minute. In order to detect this change in the minute current signal, 'at the amplifying circuit', it is necessary to use a magnification of -145-201122922. However, if an amplifier having an amplification factor suitable for the output signal obtained when the pointer 19 is in contact is used, a new problem arises, that is, the Harderma code at the length of 16 chips. The output signal obtained when the front-end chip is supplied to the signal conductor 14 is clamped. However, if an amplifier having an amplification factor of an output signal obtained by supplying a front-end chip suitable for the Hadamard code of the 16-chip length to the signal conductor 14 is used, the following The problem is that it will not detect small changes in the output signal. When the code columns of mutually different 2n chip lengths are respectively supplied to the transmission conductors 12, when the mth chips of the respective code columns are all "丨", the above problem occurs due to the problem. Therefore, if it is assumed that the code of the mth chip is not supplied to the transmission conductor 12, the maximum 値 of the signal level of the output signal can be suppressed to be low. Specifically, if the Hadamard code of the length of 15 chips shown in Fig. 17(b) is supplied, it is possible to supply and supply to the respective signal conductors 1 2 for the maximum chirp of the output signal. The number of Hadamard codes (in the case of the Harddam code shown in Figure 17 (b) is "16"). In this case, when the Hadamard code of the length of 15 chips is supplied to the signal conductor 12, no intersection is placed at the intersection of any of the receiver conductors 14 The level of the relevant enthalpy obtained at the time of the indication 19 (hereinafter, this predetermined output signal is referred to as "reference level") can also be suppressed to be low. However, when this 15 chip length Hadmar code is supplied to the transmission conductor 12, a new problem arises, that is, if the indication is -146-201122922, the body 1 9 is in either case. At the intersection of the contacts, the reference level will change. This is because, compared to the Hadamard code of 16 chip length, since the code length is 1 chip shorter, if the indicator 19 is at the intersection of 15 chips long Hadmar code, For contact, the reference level will increase the amount of current shunted to ground at this intersection. Therefore, when the indicator body 19 is simultaneously in contact with the intersection of the complex numbers, the reference level system fluctuates in proportion to the number of intersections with the pointer body 19. Further, the determination as to whether or not the indicator 19 is in contact with the intersection is performed, for example, by comparing the signal level of the output signal with a specific threshold (refer to Fig. 16). In the pointer detecting device of the present invention, since a plurality of indicators can be detected simultaneously, for example, it is conceivable to place the palm on the sensing unit 100 or to display a plurality of indicators (for example, The plural finger) is simultaneously contacted at the intersection of the complex numbers on the same received conductor 14 . In this case, the reference level of the output signal from the signal conductor I4 is greatly changed. As a result, the level of the relevant enthalpy at the intersection of the indicator body 19 is also greatly changed, and there is a case where the erroneous determination is made without exceeding the threshold. Hereinafter, a modification 30 for solving the above problem will be described with reference to Figs. 72 and 73. The pointer detecting device 3 in the modification 30 and the pointer detecting device (refer to FIG. 1) in the first embodiment are different from each other in the indicator detecting device 3. In order to supply the one-147-201122922 of the spread code ck supplied from the spread spectrum code supply circuit 21 to the sensing unit 1 直接 directly to the amplifying circuit 3 3 2 ' The frequency code supply circuit 21 is connected to the amplification circuit 332. Further, in order to avoid complication of the drawing, in Fig. 73, the illustration of the received conductor selection circuit 31 is omitted. Moreover, in order to make it easier to understand, only the area where the signal conductor Yi'Yii on the sensing unit 100 intersects with the signal conductors Xi23 to X128 is displayed, and the spreading code is supplied to the signal conductor. The case where the output signals from the signal conductors Χ123 to Χ128 are detected from each of Y! to Y6 is exemplified. In addition, the same components as those of the pointer detecting apparatus 1 of the first embodiment are denoted by the same reference numerals, and the description thereof will be omitted. First, as shown in FIG. 72, the spreading code supply circuit 21 is removed. The transmission conductor selection circuit 22, the clock generation circuit 23, the correlation calculation circuit 34, and the control circuit 40 are also connected to the amplification circuit 332. On the other hand, the spreading code generating circuit 24 of any one of the plurality of spreading code generating circuits 24 constituting the spread code supplying circuit 21 is connected to the amplifying circuit 332. The spreading code output from the spread spectrum code generating circuit 24 directly connected to the amplifying circuit 332, for example, the spread spectrum code Q, is directly supplied to the receiving portion 34 without being transmitted via the transmitting conductor 12. The amplifying circuit 3 3 at 2 is used by the tracking signal c ι as a reference signal for the correlation characteristic (reference signal). The receiving portion 3 4 of this modification 3 will be described with reference to Fig. 7 3 '. The amplifying circuit 332 is constituted by the same number of ι/ν converting circuits 332a as the received conductor 14, and the same number of capacitors 332b' as the i/v converting circuit 332a. The capacitor 33 2b' is provided between the frequency code generating circuit 24 (not shown) which generates the spread spectrum code, and the i/v conversion circuit 332a. Therefore, the spread spectrum code! The capacitor is supplied to each of the 1/V conversion circuits 332a via the capacitors 3 32b. In addition, other spread spectrum codes (: 2 to (: 7) of the spread spectrum code generating circuit 24 are connected to the transmission conductors γ and γ6, respectively. As a result, the spread code C! is passed through the capacitor. And directly supplied to the respective I/V conversion circuits 3 3 2a constituting the amplification circuit 33 2 . By supplying the spread code C to the capacitor 3 32b, at each 1/V conversion circuit 332a, The output signal outputted via the signal conductor 14 and the current signal (correction signal) generated by supplying the spreading code h to the capacitor 3 3 2b are combined inputs. This is done with the correction signal. The synthesized output signal is converted into a voltage signal at each I/V conversion circuit 332a, and is amplified. The A/D conversion circuit 333 is composed of an I/V conversion circuit 3 constituting the amplification circuit 332. 3 2 a is formed by the same number of A/D converters 3 3 3 a. Each of the A/D converters 333a is connected to a corresponding I/V conversion circuit 3 32a. The voltage signal outputted at the 1/V conversion circuit 3 32a is input to each A/D conversion circuit 333a and converted into The bit signal is output to the correlation 値 calculation circuit 35 (refer to Fig. 7 2). The correlation 値 calculation circuit 34 performs correlation calculation by correlating the calculus codes corresponding to the respective spreading codes. Here, the spread spectrum code C! is directly input to the amplifier circuit 332 constituting the signal receiving unit 34 without passing through the transmission conductor 12 and the signal conductor 14, so that the spread code C! In the signal component, there is no variation factor generated by the transmission conductor 12 and the signal conductor 14. As a result, the correlation code c-149-201122922 corresponding to the spreading code C! The result of the relevant calculations performed (also 'has become a certain constant for constant stability. 'In this variant 30, this is used for a certain level of alignment. That is, the correlation calculation circuit 3 4. The D-transformer circuit 3 3 2 inputs the respective digit signals, and performs the correlation calculation caused by the correlation calculus code C t ', and then the correlation 得到 obtained by the calculus is used as a correlation characteristic, for example, in the relevant memory. Circuit 3 4d (refer to FIG. 8) Regarding the calculation circuit 3 4, The correlation calculation is performed on the correlation 値 calculation month corresponding to each of the spread codes C2 to C7 in the first embodiment, and the correlation result is the correlation between the memory circuits 34 d. Then, the position calculation circuit 35 (Refer to Fig. 1), whether or not the indicator body 19 is in the sense of the correlation threshold for each of the spread code C2 and the relative threshold of the relevant specific reference level in the related note circuit 34d. Specifically, the position calculation circuit 3f calculates the correlation 算出 calculated by each of the spread codes C2 to C7 and subtracts the 値 of the phase. Then, the position calculation is compared with the specific threshold by comparing the subtracted 値 to the specific threshold 是否. In this way, by using the spread spectrum code in the complex number of codes, it will not be straight through the transmission conductor 12 and the signal conductor 14 and the spread spectrum code is used as a reference for the correlation characteristic. As a reference system for the A/ by the spread spectrum code (^' will be by this phase reference level, after the same, after the same, for the code C2 '~C7', the memory is related to Memory ~C 7 calculated the relationship between the key and the special:!! unit 100, the circuit will be output from the benchmark for the off-characteristics, and the spectrum-specific code will be supplied to the receiver. The position correction signal -150-201122922 (reference signal) is used, and even if there is a change in the reference level, the contact position caused by the indicator 19 can be correctly detected. [Modification 3 1] In the above modification 30, the output signal and the correction signal from the signal conductor are synthesized before being input to the A/D conversion circuit (that is, synthesized at the stage of the analog signal). An example is given. In this case, When the correction signal and the output signal are combined at the stage of the analog signal, since it can be realized only by providing the capacitor 3 3 2b, it is excellent in that the circuit configuration can be simplified. The capacitor 332b is necessarily set to have the same capacitance as the capacitor formed between the signal conductor 12 and the signal conductor 14. As described above, the intersection between the signal conductor 12 and the signal conductor 14 is generally as described above. The capacity of the capacitor formed by the space is about 0. It is very difficult to install a very small capacity around PF, so it is necessary to mount it on an actual circuit board. Further, in the modification 30, since the correction signal and the received signal are synthesized at the stage of the analog signal, there is also a problem that an error is easily generated. Therefore, in the modification 31, the case where the correction signal and the output signal of the a/D conversion circuit (i.e., the received signal converted into a digital signal) are combined will be described. Referring to Fig. 74', a description will be given of a configuration example in which a signal to be converted into a digital signal and a correction signal are combined. In the third modification, the -151 - 201122922 A/D conversion circuit 433 and the correlation calculation circuit 34 (refer to FIG. 72) are provided for output from the A/D conversion circuit 433. An adder group 434 for synthesizing each digital signal with a correction signal converted into a digital signal, and a capacitor 435 for directly supplying the spread code used as the correction signal to the signal receiving portion, and for The current signal is converted into a 1/V conversion circuit 436 of the voltage signal, and an A/D converter 437 for converting the correction signal into a digital signal. The other configurations are the same as those of the above-described modification 30 (refer to Fig. 72). Therefore, the same reference numerals will be given to the same components, and the description thereof will be omitted. By supplying the spread code C to the capacitor 435, a current signal is input to the 1/V conversion circuit 436. The 1/V conversion circuit 436 converts the input current signal into a voltage signal and amplifies the output. The voltage signal output from the 1/V conversion circuit 436 is converted into a digital signal by the A/D converter 43 7 and input to the adder group 434 at the adder group 434. The A/D conversion circuit 43 3 a of the A/D conversion circuit 433 is constituted by the same number of adders 434a. Each of the adders 43 4a is provided between the A/D converter 43 3 a connected to each of the received conductors 14 and the input terminal of the associated 値 calculation circuit 34, and is input from each A/ The output signal converted by the D converter 43 3 a is converted into a digital signal, and the correction signal after being converted into a digital signal at the A/D converter 43 7 . Further, each adder 434a combines (outputs) the output signal and the correction signal converted into a digital signal and outputs it. Further, the digital signal synthesized by the adder 434a and the correction signal is input to the correlation calculation circuit 34. Thereafter, the correlation calculation is performed in the correlation calculation circuit 34. In the configuration example shown in Fig. 74, also in the same manner as the example shown in Fig. 73, the adjustment of the reference level can be performed. In the modification 31, since the correction signal and the received signal can be synthesized by the digital signal, in the capacitor 43 5 provided for supplying the correction signal, for example, an 8PF capacitor is used, and In the A/D converter 437, the 4-bit data is reduced in number of bits, whereby the signal synthesis can be performed with higher precision than the synthesis by the analog signal. . Further, in the modification 3 1 described above, an example in which one spreading code is used as a correction signal for adjusting the reference level has been described. However, the present invention is not limited thereto. . For example, it is also possible to supply two or more spreading codes as correction signals. [Brief Description of the Drawings] Fig. 1 is a schematic block diagram of a pointer detecting apparatus according to a first embodiment of the present invention. Fig. 2 is a schematic cross-sectional view showing a sensing unit of the pointer detecting device according to the first embodiment. Fig. 3 is a schematic structural view showing a spread code supply circuit of the pointer detecting device of the first embodiment. Fig. 4 is a schematic structural view showing a transmission conductor selection circuit of the pointer detecting apparatus according to the first embodiment. [153] Fig. 5 is an explanatory diagram of the spreading code switching operation at the transmitting unit of the pointer detecting apparatus according to the first embodiment. Fig. 6 is a schematic structural view showing a receiving conductor selection circuit of the pointer detecting apparatus according to the first embodiment. Fig. 7 is an explanatory diagram for explaining a switching operation of a signal conductor of a signal conductor selection circuit in the pointer detecting device of the first embodiment. Fig. 8 is a block diagram showing the correlation calculation circuit of the pointer detection apparatus according to the first embodiment. [Fig. 9] A block configuration diagram of a correlation calculation circuit for performing correlation calculation by time division of the pointer detection apparatus according to the first embodiment. [Fig. 1A] A block configuration diagram showing an example of the internal configuration of the correlator of the pointer detecting apparatus according to the first embodiment. [Fig. 11] Fig. 1 (a) to (g) are timing charts for explaining the operation of each unit of the pointer detecting apparatus according to the first embodiment. [Fig. 1 2] is an explanatory diagram for explaining the principle of position detection in the pointer detecting apparatus of the first embodiment. [Fig. 13] An explanatory diagram for explaining the principle of position detection in the pointer detecting device according to the first embodiment (the state in which the indicator is not present) [Fig. 14] is used for the first embodiment. Description of the principle of position detection in the indicator detecting device (the state in which the indicator is present) is explained. [Fig. 15] An explanatory diagram for explaining the principle of position detection in the pointer detecting apparatus according to the first embodiment (the state in which the pointer is present at the intersection of the plural numbers). -154- 201122922 [Fig. 16] An explanatory diagram showing an example of the output signal detected in the state shown in Fig. 15. Fig. 16 (a) is for the slave receiving electrodes Yi to Y4. The relationship between the output signal and the code number is shown in the figure. Figure 16 (b) is a diagram showing the relationship between the output signal and the code number output from the receiving electrodes Y 5 to Y64. [Fig. 17] Fig. 17 (a) is a diagram showing an example of a Hadamard code of 16 chip length, and Fig. 17 (b) is a Hadmard for a length of 15 chips. An example of the code is shown in the figure, and Fig. 17(c) is between the output signal and the code number obtained in the case where the Hadamard code of the length of 16 chips shown in Fig. 17 (a) is supplied. The relationship is shown in the figure, and Fig. 17(d) is a diagram showing the relationship between the output signal and the code number obtained when the Hadmar code of 15 chip length is supplied. Fig. 18 is a flow chart showing a processing procedure of position detection in the pointer detecting apparatus according to the first embodiment. [Fig. 19] Fig. 19 (a) is a waveform diagram of a spreading code before PSK modulation in the second embodiment of the present invention, and Fig. 19(b) is an exhibition after PSK modulation. Waveform of the frequency code. [Fig. 20] Fig. 20 is a schematic block diagram of a pointer detecting device according to a second embodiment. [Fig. 21] A schematic configuration diagram of a spread code supply circuit of the pointer detecting device of the second embodiment. Fig. 22 is a block diagram showing the correlation calculation circuit of the pointer detection apparatus according to the second embodiment. -155-201122922 [Fig. 23] Fig. 23 (a) is a waveform diagram of the spread spectrum code of the FSK modulation in the third embodiment of the present invention, Fig. 23 (b), after FSK modulation The waveform of the spread code. Fig. 24 is a schematic structural view of a spread code supply circuit of the pointer detecting device of the third embodiment. Fig. 25 is a block diagram showing the correlation circuit of the pointer detecting device according to the third embodiment. Fig. 26 is an explanatory diagram for explaining a method of supplying a spread spectrum code in Modification 1. Fig. 27 is a schematic block diagram showing a transmission conductor selection circuit in a second modification. [Fig. 2] An explanatory diagram for explaining a method of supplying a spread spectrum code in Modification 2. [Fig. 29] An explanatory diagram for explaining a method of supplying a spread spectrum code in Modification 3. FIG. 30 is a block configuration diagram of a signal conductor selection circuit in Modification 4. FIG. Fig. 31 is an explanatory diagram for explaining a switching operation of the received conductor selection circuit in the fourth modification. FIG. 32 is a schematic cross-sectional view of a sensing unit according to a fifth modification. [ Fig. 3 3 ] Fig. 3 3 ( a ) is a schematic cross-sectional view of the sensing portion of the modification 6 ' Fig. 3 3 (b), showing an arrangement example of the sensing portion of the modification 6 Fig. 34(a) is a plan view showing a schematic configuration of a transmission conductor and a signal conductor of Modification 7, and Fig. 34(b) is a transmission for Modification 7. Plan view of enlarged island-shaped conductor portion - 156 - 201122922 [Fig. 3 5] A schematic plan view of the sensing portion of Modification 8. [Fig. 36] A schematic plan view of a sensing portion of Modification 9. 37(a) is a schematic structural view showing the arrangement of the transparent electrode film of the transmission conductor at the sensing portion of Modification 9, and FIG. 37(b)' is for receiving the signal. The configuration of the transparent electrode film of the conductor is shown as a schematic diagram. [Fig. 3] Modification 1 A schematic diagram of a sensing portion of the cymbal. FIG. 39 is a block configuration diagram of a receiving unit of Modification 11. FIG. Fig. 40 is a schematic diagram showing the configuration of a differential amplifier of a modification 12. [Fig. 4 1] A schematic configuration diagram for explaining a method of supplying a spread spectrum code of Modification 13. FIG. 42 is a schematic structural view of a sensing unit according to a modification 14. [Fig. 43] A schematic diagram of a sensing portion for comparison with a modification 14. [Fig. 44] An explanatory diagram showing an example of a switching state of a transmission conductor of a modification. Fig. 45 is an explanatory view showing another example of the switching state of the transmission conductor of the modification 14. Fig. 46 is a schematic diagram showing the relationship between the transmission mode of the spreading code of the transmitting unit in the modification 15 and the signal receiving form of the signal of the receiving unit. [Fig. 47] A configuration diagram showing the relationship between the transmission mode of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification of the first embodiment. [Fig. 48] A configuration diagram showing an example of the internal structure of the signal conductor selection circuit in the modification 16 - 157 - 201122922. [FIG. 49] A configuration diagram showing an example of the received conductor selection circuit in the modification 16 [FIG. 50] FIG. 50(a) shows the transmission of the spread code of the transmission unit in the modification 17. The relationship between the form of the signal and the signaled form of the signal of the receiving unit is shown in Fig. 50(b), which is a waveform diagram of the output signal output from the differential amplifier. [Fig. 5 1] A configuration diagram showing the relationship between the transmission mode of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 18. [Fig. 52] A configuration diagram showing the relationship between the transmission mode of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification example 19. Fig. 53 is a block diagram showing an example of a transmission conductor selection circuit of Modification 19. Fig. 54 is a block diagram showing an example of a receiver of a modification 19. [Fig. 55] A configuration diagram showing the relationship between the transmission mode of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 20. Fig. 56 (a) and (b) are explanatory views for explaining the principle of identification of the suspension state in the modification 21. [Fig. 57] Fig. 57 (a) and (b) are explanatory views for explaining the principle of identification of the suspension state in the modification 21. [Fig. 58] A distribution diagram for explaining the principle of identification of the suspended state in Modification 21. [FIG. 59] The relationship between the transmission mode of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 22 (the detection area is narrow -158-201122922 state) Figure. [Fig. 60] A configuration diagram showing the relationship between the transmission pattern of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 22 (the detection area is in a wide state). [Fig. 6 1] A configuration diagram showing the relationship between the transmission pattern of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 24. [Fig. 62] A configuration diagram showing the relationship between the transmission pattern of the spreading code of the transmitting unit and the signal receiving form of the signal of the receiving unit in the modification 25. [Fig. 63] A block configuration diagram of an example of the receiving unit of the modification 2-6. [Fig. 64] Block configuration of an example of the absolute helium detection circuit of the modification 26 [Fig. 65] Fig. 65(a) shows a case where the spread code is supplied from the side of the transmission conductor. Figure 65 (b) shows the relationship between the position of the conductor under test, the position of the detection signal, and the phase delay (level/phase). The relationship between the two is shown. Illustrating. [Fig. 66] Fig. 66 (a) is a view showing a pattern of the case where the spreading code is supplied from both sides of the transmission conductor in the modification 27, Fig. 66 (b). An explanatory diagram showing the relationship between the bit of the received conductor in this case, the level of the detection signal, and the phase delay (level/phase). [Fig. 6] A characteristic diagram for explaining the principle of taking out the finger pressure of the indicator in the modification 28. [Fig. 6 8] The state diagram for the finger energy of the fetching indicator in the modification 28 is set to the frequency of the pseudo-frequency.) -159-201122922 The principle of the pressure is explained. 69] A characteristic diagram for explaining the principle of the instruction pressure for taking out the pointer in Modification 28. [Fig. 70] An explanatory diagram showing an example in which the number of the spread spectrum codes is the same as the number of the transmission conductors as a modification 29. [Fig. 7] Block configuration diagram of an example of the correlation calculation circuit of the modification 29 [Fig. 72] A configuration diagram of the pointer detection apparatus according to the modification 30. [Fig. 7] A schematic diagram of the signal receiving portion of the modification 30. Fig. 74 is a schematic diagram showing the configuration of the receiving unit in the modification 31. Fig. 75 (a) is a schematic structural view of a pointer detecting device of a cross-point electrostatic coupling method of the prior art, and Fig. 75 (b) is a waveform diagram of an output signal. [Description of main component symbols] 1 '2, 3: pointer detecting device 1 1 , 41 1 : transmitting conductor group 12, 412, 512, 612, 712, 812: transmitting conductor 13, 413: signal conductor group 14 414' 514, 614, 714: signal conductor 15 : first substrate 1 6 : spacer 17 : second substrate 1 9 : finger (indicator) -160 - 201122922 21, 221, 222 : spread spectrum code supply circuit 22, 202, 382, 402: transmission conductor selection circuits 22a, 202a, 231a, 231b: switch 23: clock generation circuit 24: spread spectrum code generation circuit 25, 125, 3 8 3, 403: transmission block 26 : P SK modulation circuit 27: FSK modulation circuit 31, 131, 231, 384, 404, 415, 813: receiving circuit 3 1 a, 1 3 1 a : switch 32, 232, 332, 333, 432 Amplifying circuits 32a, 232a, 332a, 3 3 3 a : I/V converting circuits 32b, 232b, 532: amplifiers 32c, 232c: capacitors 32d, 23 2d: switching switches 33, 43 3 : A/D converting circuit 34 134, 3 04, 3 14 : correlation 値 calculation circuits 34a, 3 04 a, 3 3 4a: signal delay circuits 34a 丨 34 34 64 64 64 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 34 ~34b", 3 4 bx ' 3 04b i ~ 3 04b63 ' 334b64_ correlator 3 4c ' 34ci ~ 34c ", 1 3 4 cx, 304c〗 ~ 304C64, 3 3 4c64 : Correlation 値 calculus code generation circuit conductor selection 334b1~3 3 4 c 1 ~ -161 - 201122922 34d, 3 04d, 3 3 4d : related memory circuit 34f, ~34f16: multiplier 3 4 g : adder 3 5 : position detecting circuit 3 6, 136, 2 3 6 ' 3 3 6 : detection block 40 : control circuit 100 , 400 , 500 , 600 , 700 , 800 : sensing unit 126 : PSK demodulation circuit 1 27 : FSK demodulation circuit 134e : register 200 201: Transmitting units 250, 350, 360, 361, 386, 396, 397, 405, 407 420, 43 0: differential amplifiers 300, 301, 310, 320, 330, 340: receiving unit 3 3 2b: capacitor 381, 406, 431: code inverters 382a, 384a, 402a, 815: switch group 382a, 382382a4, 402a, ~ 402a3: switch 4 0 1 : code inverter 43 3 a' 43 7: A/D conversion 43 4 : Adder group 434a : Adder 43 5 : Capacitor 43 6 : 1 / V converter circuit -162 - 201122922 4 8 1 : Gain adjustment circuit 4 8 2 : Gain 値 setting circuit 48 3 : Absolute 値 detection Circuit 48 3 a : Totalizer 4 8 3 b : Integrator 484 : Automatic gain control circuit 501 ' 6 0 1··Substrate 5 1 3 : 1st protective layer 5 1 5 : 2nd protective layer 5 1 6 : Protective sheet 5 1 7 : first transparent electrode film 518 : second transparent electrode film 602 : metal layer 6 0 3 : insulating layer 722 , 822 : conductor portion 723 , 8 2 3 : island-shaped conductor portion - 163-
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2009288273AJP5295090B2 (en) | 2009-12-18 | 2009-12-18 | Indicator detection device |
| Publication Number | Publication Date |
|---|---|
| TW201122922Atrue TW201122922A (en) | 2011-07-01 |
| TWI591515B TWI591515B (en) | 2017-07-11 |
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| TW099124741ATWI591515B (en) | 2009-12-18 | 2010-07-27 | Indicator detection device |
| Country | Link |
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| US (3) | US8462136B2 (en) |
| EP (3) | EP2336854B1 (en) |
| JP (1) | JP5295090B2 (en) |
| KR (1) | KR101446373B1 (en) |
| CN (1) | CN102103429B (en) |
| IL (3) | IL206609A (en) |
| TW (1) | TWI591515B (en) |
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