COMPLEMENTARY HIGH-SPEED DATA-TRANSMISSION SPEED CHANNEL FOR CDMA TELECOMMUNICATION SYSTEMS BACKGROUND OF THE INVENTION I. Field of the Invention The present invention relates to wireless telecommunications. More particularly, the present invention relates to a novel and improved method for implementing a high transmission speed over the air type. II. Description of the Related Technique The IS-95 standard of the Telecommunications Industry Association (TIA) and its derivatives such as IS-95A and ANSI J-STD-008 (collectively referred to herein as IS-95), define an adequate air interface to implement an efficient cellular bandwidth digital telephone system. For this purpose, IS-95 provides a method for establishing multi-radio frequency (RF) traffic channels, each having a data transmission rate of up to 14.4 kilobits per second. Traffic channels can be used to conduct voice telephony or to conduct digital data communications including the transfer of small files, email and facsimile. Although 14.4 kilobits per second is suitable for this type of lower data rate applications, the growing popularity of more intense data applications such as the global network and video conferencing have created a demand for such speeds of higher transmission. To meet this new demand, the present invention is directed to providing an interface on the air capable of higher transmission speeds. Figure 1 illustrates a highly simplified digital cellular telephone system, configured in a manner consistent with the use of the IS-95. During the operation, telephone calls and other communications are conducted by exchanging data between the subscriber units 10 and the base stations 12 using RF signals. Communications are further conducted from the base stations 12 through the base station controllers (BSC) 14 and the mobile switching center (MSC) 16 to either the public switched telephone network (PSTN) 18 or to another subscriber unit 10. BSC's 14 and MSC 16 typically provide control of call processing mobility and call addressing functionality. In a system in accordance with IS-95, the RF signals exchanged between the subscriber units 10 and the base stations 12 are processed according to multiple code access (CDMA) signal processing techniques. The use of signal processing techniques by CDMA allows the adjacent base stations 12 to use the same RF bandwidth, which, when combined with the use of transmission power control, makes the amplitude of the transmitter more efficient. band of the IS-95 than other cell phone systems. CDMA processing is considered a "spread spectrum" technology because the CDMA signal is broadcasted over a wider RF bandwidth quantity than that generally used for the non-spread spectrum systems. The diffusion bandwidth for an IS-95 system is 1.2288 Mhz. In U.S. Patent 5,103,450 entitled "System and Method for Generating Signal Wave Forms in a CDMA Cellular Telephone System", ("System and Method for Generating Signal Waveforms in a CDMA Cellular Telephone System") assigned to the assignee of this invention and incorporated herein by reference, a digital wireless telecommunications system based on CDMA is described substantially configured in accordance with the use of the IS-95. It is anticipated that the demand for higher transmission speeds will be greater for the forward link than for the reverse link because a typical user is expected to receive more data than it generates. The forward link signal is the RF signal transmitted from a base station 12 to one or more subscriber units 10. The reverse link signal is the RF signal transmitted from the subscriber unit 10 to a base station 12 Figure 2 illustrates the signal processing associated with a forward link traffic channel of the IS-95, which is a portion of the forward link signal of the IS-95. The forward link traffic channel is used for the transmission of user data from a base station 12 to a particular subscriber unit 10. During normal operation, the base station 12 generates multiple forward link traffic channels. , each of which is used for communication with a particular subscriber unit 10. Additionally, the base station 12 generates various control channels that include a pilot channel, a synchronization channel and a paging channel. The forward link signal is the sum of the traffic channels and the control channels. As shown in Figure 2, the user data is entered into node 30 and processed in blocks of 20 milliseconds (ms) called structures. The amount of data in each structure can be one of the four values, each lower value being approximately half the next higher value. Also, two possible sets of structure sizes can be used, which are referred to as speed set one and speed set two. For speed set two the amount of data contained in the larger structure or "full speed" corresponds to a transmission speed of 13.35 kilobits per second. For the speed set one the amount of data contained in the full speed structure corresponds to a transmission speed of 8.6 kilobits per second. Smaller-sized structures are referred to as half-speed, quarter-speed, and one-eighth-speed structures. The various frame rates are used to adjust the changes in voice activity experienced during a normal conversation. The CRC generator 36 aggregates CRC data with the amount of CRC data generated, depending on the size of the structure and the speed set. The final byte generator 40 adds eight final bits of known logical state to each structure to aid during the decoding process. For full speed structures, the number of final bits and bits of CRC raises the transmission speed up to 9.6 and 14.4 kilobits per second for the set of speed one and the set of speed two. The data from the final byte generator 40 is coded convolutionally by the encoder 42 to generate code symbols 44. The constrained length average velocity encoding (K) is performed 9. The perforation 48 removes 2 out of every 6 code symbols for the structures of speed set two, which effectively reduces the coding carried out at 2/3 speed. In this way, at the exit of the perforation 48 the code symbols are generated at 19.2 kilograms per second (ksps) for both full velocity structures of both the velocity set one and the velocity set two. The block interleaver 50 carries out the interleaving of blocks in each structure and the interleaved code symbols are modulated with a Walsh channel code from the Walsh code generator 54 which generates sixty-four Walsh symbols for each code symbol. A particular Walsh channel code VI i is selected from a set of sixty-four Walsh channel codes and is typically used for the duration of an interface between a particular subscriber unit 10 and a base station 12. The Walsh symbols are duplicated then and a copy is modulated with a broadcast PN code in phase (PNX) from the broadcast code generator 52 and the other copy is modulated with a PN quadrature diffusion code (PNQ) from the broadcast generator. diffusion codes 53. The in-phase data is then filtered by low pass through the LPF 58 and modulated with a sinusoidal in-phase carrier signal. In a similar way, the quadrature phase data is filtered by low pass through the LPF 60 and modulated with a sinusoidal carrier in quadrature phase. The two modulated carrier signals are then summed to form the signal s (t) and transmitted as the forward link signal. SUMMARY OF THE INVENTION The present invention is a novel and improved method for implementing an air interface of transmission speed. A transmission system provides a set of channels in phase and a set of channels in quadrature phase. The set of in-phase channels is used to provide a complete set of orthogonal average speed and traffic control channels. The set of phase quadrature channels is used to provide a high speed complementary channel and an extended set of medium speed channels that are orthogonal to each other and the original average speed channels. The high speed complementary channel is generated on a set of medium speed channels by the use of a short channel code. The average velocity channel is generated by the use of a set of long channel codes. BRIEF DESCRIPTION OF THE DRAWINGS The features, objects and advantages of the present invention will become more apparent from the detailed description set forth below when taken in conjunction with the drawings in which similar reference characters are identified correspondingly through of all and where: Figure 1 is a block diagram of a cell phone system; Figure 2 is a block diagram of the forward link signal processing associated with the IS-95 standard; Figure 3 is a block diagram of a transmission system configured in accordance with an embodiment of the invention; Figure 4 is a list of the Walsh code set of 64 symbols and associated indices used in a preferred embodiment of the invention; Figure 5 is a block diagram of the channel coding carried out according to an embodiment of the invention; Figure 6 is a block diagram of a reception system configured in accordance with an embodiment of the invention; and Figure 7 is a block diagram of a decoding system configured in accordance with one embodiment of the invention. DETAILED DESCRIPTION OF THE PREFERRED MODALITIES Figure 3 is a block diagram of a transmission system configured in a manner consistent with the use of the invention. Typically, the transmission system will be used to generate the forward link signal in a cellular telephone system and will therefore be incorporated into a base station 12. In the exemplary configuration shown, the transmission system generates a forward link signal which includes a complete set of IS-95 or medium speed channels as well as a complementary high-speed channel. Additionally, in the described embodiment, an extended set of IS-95 channels is provided. Alternative embodiments of the invention could provide more than one high-speed complementary channel or fail to provide the use of an additional set of channels of the IS-95 or both. Also, although the proportion of channels of the IS-95 is preferred, other embodiments of the invention may incorporate other types of channel and processing protocols. In the exemplary embodiment provided, the transmission system provides a set of channels in phase 90 and a set of channels in quadrature of phase 92. The set of channels in phase 90 is used to provide the complete set of traffic and control channels of the orthogonal IS-95. The orthogonal channel does not interfere with each other when it is transmitted through the same path. The set of quadrature channels of phase 92 is used to provide a high-speed complementary channel and an extended set of channels of the IS-95 that are orthogonal to each other and the original IS-95 channels. In the preferred embodiment of the invention, all the signals and data shown in Figure 3 are formed by positive and negative integer values, represented by binary digital data or voltages, which correspond to low logic and high logic, respectively. For the set of channels in phase 90, the control channel system of the IS-95 100 carries out various functions associated with one of the control channels of the IS-95 standard, including coding and interleaving, the processing of which is described in the IS-95 incorporated herein for reference. In this case, since the Walsh channel code is used ^ the processing will be in accordance with the use of a paging channel. The resulting code symbols of the control channel system of the IS-95 100 are modulated with a Walsh code from the Walsh! Generator. 102 by the multiplier 104. The Walsh generators 102 are used to generate the orthogonal phase channels. The Walsh generator 102 repeatedly generates a Walsh code of index 1 (Walsh from a set of Walsh codes of indices 0 to 63 (Walsh0 S3) Figure 4 is a list of the Walsh code set of 64 symbols and associated indices , used in a preferred embodiment of the invention A Walsh chip corresponds to a Walsh symbol and a Walsh chip value of 0 corresponds to a positive integer (+) while a Walsh chip value of 1 corresponds to a negative integer (- Under the IS-95, the Walshx code corresponds to the paging channel. The Walsh symbols generated by modulation with the Walsh code are adjusted for gain by channel gain 108 (2). The pilot channel is generated by the gain adjustment of a positive value 1 using the channel gain 108 (1). No coding is carried out for the pilot channel according to IS-95, since the Walsh0 code used for the pilot channel is all values plus 1 and therefore equals no modulation. Additional control channels are generated in a similar manner, through the use of additional IS-95 control channel systems, additional Walsh generators and additional channel gains (all not shown). Such control channels include a synchronization channel, which is modulated with the Walsh32 code. The processing associated with each type of control channel of the IS-95 is described in IS-95. The processing associated with one of the IS-95 traffic channels in the set of in-phase channels is illustrated with the traffic channel system of IS-95 110, which performs various functions associated with a channel of IS-95 traffic that includes convolutional coding and intercalation, as described above, in order to generate a sequence of symbols at 19.2 kilograms per second. The code symbols from the IS-95 110 traffic channel system are modulated with the Walsh63 code of 64 symbols from the Walsh generator 112 112 by the multiplier 114 in order to generate a sequence of symbols at 1.2288 Megawords per second. The Walsh symbols from the multiplier 114 are adjusted by gain by the gain adjustment 108 (64). The results of all the gain adjustments, including the gain settings 108 (1) - (64) are summed by the totalizer 120 that generates data in phase O1. Each gain adjustment 108 increases or decreases the gain of the particular channel with which it is associated. The gain adjustment can be carried out in response to a variety of factors including energy control commands from the subscriber unit 10 processing the associated channel or differences in the type of data being transmitted on the channel. By keeping the transmission energy of each channel to the minimum necessary for proper communication, the interference is reduced and the total transmission capacity is increased. In one embodiment of the invention, the gain settings 108 are configured by a control system(not shown), which could take the form of a microprocessor. Within the set of quadrature phase channels 92, an extended set of 64-2N trafchannels of the IS-95 is provided through the use of channel systems of the IS-95 124. N is an integer value based on the number of Walsh channels assigned to the complementary channel and described in more detail below. Each code symbol from the channel systems of IS-95 124 (2) - (64-2N) is modulated with a Walsh code from Walsh generators 126 by multipliers 128, except for the trafchannel system of the IS-95 124 (1), which is placed on the Walsh0 channel and therefore does not require modulation. To provide the high-speed complementary channel, the complementary channel system 132 generates code symbols at a rate Rs, which are 2N times the full-speed IS-95 trafchannel. Each code symbol is modulated with a complementary Walsh code (Walshs) from the generator of complementary Walsh codes 134 by using the multiplier 140. The result of the multiplier 140 is adjusted by gain by the gain adjustment 130. The results of the set of gain settings 130 are summed by the totalizer 150 which produces quadrature data of DQ phase. It should be understood that the extended set of trafchannels of the IS-95 could be completely or partially replaced with one or more additional complementary channels. The processing carried out by the complementary channel system 132 is described in more detail below. The Walsh code generated by the complementary Walsh code generator 134 depends on the number of Walsh codes assigned to the high-speed complementary channel in the set of quadrature channels 92. In the preferred embodiment of the invention, the number of Walsh channels allocated The complementary high-speed channel can be any value of 2N where N =. { 2, 3, 4, 5, 6.}. . The Walsh codes are 64 / 2N long symbols, instead of the 64 symbols used with the Walsh codes of the IS-95. In order that the high-speed complementary channel is orthogonal to the other quadrature-phase channels with the Walsh codes of 64 symbols, 2N of the possible 64 quadrature-phase channels with Walsh codes of 64 symbols can not be used for the others channels in phase quadrature. Table I provides a list of possible Walsh codes for each value of N and the corresponding sets of Walsh codes of 64 assigned symbols.
TABLE IThe + and - indicate a positive or negative integer value, where the preferred integer is 1. As is apparent, the number of Walsh symbols in each Walshs code varies as N varies and in all cases is less than the number of symbols in the Walsh channel codes of IS-95. In this way, the complementary channel is formed by the use of a short Walsh channel code and the channels of the IS-95 are formed by the use of longer Walsh channel codes. Without taking into account the length of the Walshs code, in the described modality of the invention, the symbols are applied at a speed of 1.2288 Megachips per second (Mcps). In this way, Walsh codes of shorter length are repeated more frequently. The Dt and DQ data channels are multiplied in a complex way, like the first real and imaginary terms, respectively, with PNj and PNQ diffusion codes, as the second real and imaginary terms, respectively, producing Xt of term in phase (or real ) and XQ term in quadrature phase (or imaginary). The PNX and PNQ broadcast codes are generated by broadcast code generators 152 and 154. The PNX and PNQ broadcast codes are applied to 1.2288 Mcps. Equation (1) illustrates the complex multiplication carried out. (XI + jXQ) = (DI + jDQ) (PNI + jPNQ) (1) The term Xt in phase is then filtered by low pass to a band amplitude of 1.2288 Mhz (not shown) and is overconverted by its multiplication with the Carrier in phase COS (? ct). In a similar way, the term XQ in quadrature phase is filtered by low pass to a band amplitude of 1.2288 Mhz (not shown) and is overconverted by its multiplication with the quadrature carrier phase SIN (? ct). The overconverted terms X: and XQ are summed, producing the forward link signals s (t). Complex multiplication allows the set of phase quadrature channels 92 to remain orthogonal to the set of channels in phase 90 and therefore to be provided without adding additional interference to the other channels transmitted on the same path with perfect reception phase recovery. In this way, a complete set of sixty-four Walsl channels is orthogonally added to the original set of channels of the IS-95 and this set of channels can be used for the complementary channel. Additionally, by implementing the complementary channel in the orthogonal phase quadrature channel set 92, a subscriber unit 10 configured to process the normal forward link signal of the IS-95 will still be able to process the IS channels. -95 within the set of channels in phase 90 thus providing the high-speed transmission channel while maintaining backup compatibility with previously existing systems. Although the embodiment of the invention shown in Figure 3 uses a single set of carriers in phase and quadrature phase to generate the set of channels in phase and quadrature phase, separate sets of sinusoids could be used in order to generate independent the sets of channels in phase and in quadrature phase, with the second set of carriers displaced from the first set by 90 °. For example, the DQ data could be applied to the second set of carrier sinusoids where the DQ phase diffusion data (PNI) is applied to COS (? Ct-90 °) and the DQ phase quadrature diffusion data (PNQ) is apply to SIN (? ct-90 °). The resulting signals are then summed to produce the set of quadrature channels of phase 92, which in turn are summed with the set of channels in phase 90. The use of the Walsh channels as set out in Table I also allows the simplified implementation of the complementary channel within the set of channels in quadrature of phase 92. In particular, the use of the Walsh codes listed in Table I allows the complementary channel to use complete subsets of Walsh codes;, of 64 symbols without the need to generate each and every one of those Walsh codes. For example, when N = 5, the Walsh codes specified by Table I assign a set of 32 Walsh1 codes of 64 symbols for the complementary channel. That is, all Walsh codes of 64 symbols sorted by pairs or all Walsh codes of 64 symbols sorted by odd are assigned for the complementary channel. This leaves the channels ordered by odd or even by even indexes, respectively, to implement the extended set of IS-95 traffic channels. In Figure 3, the complementary channel uses the odd Walsh code channels of 64 symbols when Walshs =. { +, -} and even channels are available for the extended set of IS-95 traffic channels. In another example, when N = 4, the associated Walshg codes assign a set of sixteen Walsh codes of 64 symbols. This leaves a set of forty-eight remaining Walsh1 codes to implement the extended traffic channels of the IS-95 or to implement additional complementary channels. In general, the use of the Walshs code corresponding to a particular N value assigns 2N Walsh ^ codes of 64 symbols to the complementary channel through the use of a single, shorter Walshg code. The assignment of complete subsets of Walsl codes through the use of a single Walsh code is facilitated by the uniform distribution of the Walshx codes of 64 symbols within the subset. For example, when N = 5, the Walsh1 codes are separated by 2, and when N = 4, the Walshx codes are separated by 4. By providing only a complete set of phase quadrature channels 92 for the implementation of the complementary channel, The allocation of a large set of Walshx channels can be carried out in a uniform manner and, therefore, implemented by the use of a single Walsh code. Also, the assignment of a subset of Walshx codes of 64 symbols using a single shorter Walsh code reduces the complexity associated with the proportion of a high speed complementary channel. For example, carrying out a real modulation by using the Walsh1 code set of 64 symbols and the sum of the resulting modulated data would require a substantial increase in the processing resources of the signal compared to the use of the single Walshg generator used in the implementation of the invention described herein. The sets of Walsh1 channels evenly spaced could not be assigned as easily if the complementary channel were placed in the set of channels in phase 90 of the forward link of the previously existing IS-95, or in the in-phase or quadrature channels of phase with QPSK modulation. This is because certain Walsh1 channels of sixty-four symbols are already assigned to control functions such as paging, pilot and synchronization channels on the in-phase channel. In this way, the use of a new Walsh code space in phase quadrature allows the simplified implementation of the complementary channel. Also, the use of a single Walsh code improves the performance of the high-speed complementary channel because the variation in the amplitude of the complementary channel is minimized. In the mode described here, the amplitude is simply based on the positive or negative integer associated with the Walsh code. This is in contrast to the modulation performance with a set of 2N Walshx codes of 64 symbols, which would result in the set of amplitudes 0, +2, -2, +4, -4, ..., 2N and - 2N. Among other improvements, the reduction in amplitude variation reduces the peak-to-average power ratio, which increases the range at which the forward link signal can be received for a given maximum transmit power of the base station 12, or another forward link transmission system.
Figure 5 is a block diagram of the complementary channel system 132 of Figure 1 when configured in accordance with one embodiment of the invention. The user data is received through the control sum generator CRC 200, which adds checksum information to the received data. In the preferred embodiment of the invention, data is processed in 20 ms structures as carried out for IS-95 and 16 bits of checksum data are added. The final bits 202 add eight final bits to each structure. The emission of the final bits 202 is received at a data rate D by the convolutional encoder 204, which carries out the convolutional coding at speed Rc in each structure. Rc differs for different embodiments of the invention as described in more detail below. The block interleaver 206 interleaves the code symbols from the convolutional encoder 204 and the repeater 208 repeats the sequence of code symbols from the interleaver 206 in a repetition amount M. The repetition amount M varies in different embodiments of the invention , and will typically depend on the coding rate Rc and the speed of the complementary channel Rs (see figure 3). The amount of repetition is discussed below in an additional way. The correlator 210 receives the code symbols of the repeater 208 and converts the logical zeros and logic ones into positive and negative integer values, which are output at the speed of the complementary channel Rs. Table II provides a list of data entry rates D, coding rates Rc, repetition amounts M, and complementary channel rates Rs that can be used in different embodiments of the invention. In some modalities multiple speeds are used. TABLE IIThree input speeds D of the encoder are shown for the complementary channel: 38.4, 76.8 and 153.6 kilobits per second. For each of these input speeds D of the encoder, a set of encoder speeds Rc, N values, and repetition amounts M are provided, which achieve the desired input speed D of the encoder. Additionally, the Walshs symbol rate is provided in relation to code symbols, which corresponds to the length of the Walshs code. Also, the number of input bits of the encoder is provided by 20 structures, since it is the number of code symbols transmitted by 20 ms structures. The actual data rate will be equal to the input speed D of the encoder, minus the overhead required for the CRC bits and the final bits and any other control information provided. The use of Reed-Soloman coding is also contemplated in addition to, or in lieu of, the encoding of the CRC checksum. In general, it is desirable to use the largest possible N value for the complementary channel in order to broadcast the complementary channel over the largest number of Walsh channels. The diffusion of the complementary channel over a larger set of Walsl channels reduces the interference effect between channels, between the two corresponding Walshx channels, on the set of channels in phase 90 and the set of channels in quadrature of phase 92. This interference between channels is created by the imperfect phase alignment experienced during the reception process. By broadcasting the complementary channel over a larger set of Walsb ^ channels, the amount of inter-channel interference experienced by any Walsh channel is reduced in particular in the set of channels in phase 90, because the portion of the complementary channel in that channel Walshx is small. Also, the diffusion of the complementary channel on a larger set of channelsWalshj with a higher total channel symbol speed, allows a greater diversity of symbols, which improves the performance in the conditions of the fading channel. When the number of Walsh channels required for the desired input speed D of the encoder using coding at 1/2 speed is less than the number of Walsh channels available by at least a factor of two, performance is improved by broadcasting the signal over more Walsh channels. The highest channel symbol rate for the largest number of Walsh channels is obtained by using a 1/4 speed code, instead of 1/2 speed, or by repetition of sequence, or both. The 1/4 speed code provides additional coding gain over that of a 1/2 speed code under benign and fading channel conditions and the repeat sequence provides improved performance in fading channel conditions due to the growing diversity. In a preferred embodiment of the invention, a complementary channel having an encoder input speed of 76.8 kilobits per second is provided by the use of N = 5, a coder speed Rc of 1/4, and a repetition rate of M = 2 Such an implementation provides data transfer rates of the order of an ISDN channel that includes sufficient bandwidth for signaling. Also, the use of N = 5 maintains 32 additional Walsh1 channels to provide extended channels of the IS-95. The actual sustainable transmission rate of the complementary channel will vary depending on a variety of environmental conditions including the multiple path amount experienced by forward link transmission. The complementary transmission rate depends on the multiple path amount because the forward link signals arriving through different paths are no longer orthogonal and therefore interfere with each other. This interference increases with increasing transmission speeds due to the additional transmission power required. In this way, the greater the multipath interference experienced, the lower the sustainable transmission rate of the complementary channel. Accordingly, a lower transmission rate is preferred for the complementary channel in high multi-trajectory environments. In one embodiment of the invention, a control system is contemplated which measures the various environmental factors and which selects the optimum processing characteristics of the complementary channel. Also, the use of a signal cancellation to remove noise due to multi-path transmissions is contemplated. In copending US Patent Application Serial No. 08 / 518,217 entitled "Method and System for Processing a Plurality of Multiple Access Transmissions", ("Method and System for Processing to Plurality of Multiple Access Transmissions") assigned to the assignee hereof invention and incorporated herein by reference, there is disclosed a method and apparatus for carrying out such noise cancellation. Figure 6 is a block diagram of a receiving processing system for processing the high speed complementary channel according to an embodiment of the invention. Typically, the reception processing system will be implemented in a subscriber unit 10 of a cellular telephone system. During the operation, the RF signals received by the antenna system 300 are subconverted with a phase carrier 302 and a quadrature phase carrier 304 which generate digitized phase reception samples Rj- and phase quadrature reception samples RQ . These reception samples are provided to the displayed finger processor module and to other finger processors (not shown) in accordance with the use of an incidence receiver. Each error processor processes a case of the complementary forward link signal, each case being generated by multiple trajectory phenomena. The phase and quadrature phase Rx and RQ samples are multiplied with the complex conjugate of the PN diffusion codes generated by the phase diffusion code generator 306 and the phase quadrature diffusion code generator 308, producing the reception terms Yx and YQ. The reception terms Yx and YQ are modulated with the Walshs code generated by the Walsh generator 310 and the resulting modulated data are summed over the number of Walsh symbols in the Walsh code by the totalizers 312. Additionally, the reception terms Yt and YQ are added and filtered(averaged) by pilot filters 316. The emissions of the totalizers 312 are then multiplied with the complex conjugate of the filter pilot data and the resulting quadrature term is used in the flexible decision data of the complementary channel 320. The data supplementary decision decisions 320 may then be combined with flexible decision data from other finger processors (not shown) and decoded flexible decision data, combined. Fig. 7 is a block diagram of the decoding system used to decode supplementary flexible decision data 320 according to one embodiment of the invention. The flexible decision data is received by the accumulator 400, which accumulates samples of the flexible decision data by the repetition amount M. The accumulated data is then de-interleaved by the deinterleaver of blocks 402 and decoded by the 404 decoder. The various types of decoders are well known and include Viterbi decoders. The user data in the hard decision data, from the decoder at gate 404, is then verified with the checksum data from CRC by the CRC verifier system 406 and the resulting user data is issued together with the results of verification indicating whether the user data were consistent with the checksum data. The receiving processing system or the user can then determine whether they use the user data based on the results of the CRC checksum. In this way, a high-speed data transmission system particularly suitable for use in conjunction with the forward link of the IS-95 has been described. The invention can be incorporated both in wireless, terrestrial and satellite based communication systems, as well as communication systems connected by cable, over which sinusoidal signals such as coaxial cable system are transmitted. Also, although the invention is described in the context of a bandwidth signal of 1.2288 MHz, the use of other bandwidths is consistent with the operation of the invention that includes systems of 2.5 MHz and 5.0 MHz. Similarly, Although the invention is described by the use of transmission rates in the order of 10 kbps and 70 kbps, the use of other channel speeds may be employed. In a preferred embodiment of the invention, the various systems described herein are implemented by the use of semiconductor integrated circuits coupled through capacitive, inductive and conductive connections, the use of which is well known in the art.
The foregoing description is provided to enable any person skilled in the art to make or use the present invention. The various modifications to these modalities will be readily apparent to those skilled in the art and the generic principles defined herein may be applied to other modalities without the use of the inventive faculty. In this manner, the present invention is not intended to be limited to the modalities shown herein but to be in accordance with the broadest scope consistent with the principles and novel features set forth herein.