【０００１】[0001]
【発明の属する技術分野】この発明は、商用電源の交流
電力を３相の自励式整流器により直流電力に変換して負
荷に給電するＰＷＭ制御自励式整流装置の制御方法に関
する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a control method of a PWM control self-excited rectifier for converting AC power of a commercial power supply into DC power by a three-phase self-excited rectifier and supplying power to a load.
【０００２】[0002]
【従来の技術】図５は、この種のＰＷＭ制御自励式整流
装置の従来例を示すブロック構成図である。図５におい
て、１は商用電源、１０はＰＷＭ制御自励式整流装置、
２はＰＷＭ制御自励式整流装置１０の出力に接続される
インバータなどの負荷である。2. Description of the Related Art FIG. 5 is a block diagram showing a conventional example of this type of PWM control self-excited rectifier. In FIG. 5, 1 is a commercial power supply, 10 is a PWM control self-excited rectifier,
Reference numeral 2 denotes a load such as an inverter connected to the output of the PWM control self-excited rectifier 10.
【０００３】ＰＷＭ制御自励式整流装置１０は、ＩＧＢ
Ｔなどの自己消弧形半導体素子とダイオードとを逆並列
し、これをブリッジ接続した自励式整流器の主回路１
１、自励式整流器の交流リアクトル１２、自励式整流器
の出力の平滑用のコンデンサ１３、商用電源１の相電圧
を検出する相電圧検出器１４、商用電源１のＲ相の相電
圧を絶縁変換する絶縁変換器１５、絶縁変換器１５を介
した商用電源１のＲ相の相電圧の位相に同期した角度信
号（θ，θ＝０°〜３６０°）を発生する角度信号発生
手段１６、該角度信号（θ）に基づいた正弦波を発生す
る正弦波発生器１７、該角度信号に１２０°を加算した
値（θ1）に基づいた正弦波を発生する正弦波発生器１
８、電圧設定器１９の電圧設定値とコンデンサ１３の両
端の直流電圧を絶縁変換器２０を介して検出した電圧検
出値との偏差により電圧調節動作をする電圧調節器２
１、電圧調節器２１の出力と正弦波発生器１７の出力と
を乗算器２２で乗算して得られるＲ相電流設定値（ｉR
*）と電圧調節器２１の出力と正弦波発生器１８の出力
とを乗算器２３で乗算して得られるＴ相電流設定値（ｉ
T*）とからＳ相電流設定値（ｉS*）を求め、このｉ
R*，ｉS*，ｉT*と電流検出器２４で得られたＲ相
電流検出値（ｉR），Ｓ相電流検出値（ｉS），Ｔ相電
流設定値（ｉT）とのそれぞれの偏差を電流調節器２
５，２６，２７で調節演算をし、電流調節器２５，２
６，２７それぞれの出力である各相の電圧指令値（ｖR
*，ｖS*，ｖT*）とキャリア信号発生器２８の出力
とにより比較器２９においてパルス幅変調（ＰＷＭ）制
御を行い、この比較器２９の出力をゲート駆動回路３０
により自励式整流器の主回路１１のそれぞれの自己消弧
形半導体素子にゲート信号を与える構成である。The PWM control self-excited rectifier 10 is an IGB
Self-extinguishing type semiconductor element such as T and diode are anti-parallel
And the main circuit 1 of the self-excited rectifier
1. Self-excited rectifier AC reactor 12, Self-excited rectifier
For smoothing the output of the power supply and the phase voltage of the commercial power supply 1
, A phase voltage detector 14 for detecting the R phase of the commercial power supply 1
Insulation converter 15 for insulating conversion of pressure, via insulation converter 15
Signal synchronized with the phase of the R-phase voltage of the commercial power supply 1
Signal (θ, θ = 0 ° -360 °)
Means 16 for generating a sine wave based on the angle signal (θ)
Sine wave generator 17 adds 120 ° to the angle signal
Value (θ1) That generates a sine wave based on
8. Both the voltage setting value of the voltage setting device 19 and the capacitor 13
Voltage detection which detects the DC voltage at the end through the insulation converter 20
A voltage controller 2 that performs a voltage adjustment operation according to a deviation from the output value
1. The output of the voltage regulator 21 and the output of the sine wave generator 17
Phase current set value (i) obtained by multiplyingR
*), The output of the voltage regulator 21 and the output of the sine wave generator 18
And a T-phase current set value (i
T*) And the S-phase current set value (iS*), And this i
R*, IS*, IT*And the R phase obtained by the current detector 24
Current detection value (iR), S-phase current detection value (iS), T-phase
Flow setting value (iT) And the current controller 2
The adjustment operation is performed at 5, 26, 27, and the current adjusters 25, 2
6 and 27, the voltage command value of each phase (vR
*, VS*, VT*) And the output of the carrier signal generator 28
Pulse width modulation (PWM) control in the comparator 29
And outputs the output of the comparator 29 to the gate drive circuit 30.
Self-extinguishing of the main circuit 11 of the self-excited rectifier
In this configuration, a gate signal is applied to the semiconductor device.
【０００４】上述のＰＷＭ制御自励式整流装置１０は周
知の技術を用いたものであり、ここでは詳細動作の説明
を省略する。The above-described PWM control self-excited rectifier 10 uses a well-known technique, and a detailed description of the operation will be omitted.
【０００５】[0005]
【発明が解決しようとする課題】従来のＰＷＭ制御自励
式整流装置１０の制御方法によると、この自励式整流装
置の採用の目的である負荷２から商用電源１への電力の
回生を行えること及び商用電源１から見た力率をほぼ１
にすることなどから、自励式整流器の主回路１１の入力
交流電流を前記目的に沿った制御をするためには、キャ
リア信号発生器２８の出力の振幅を１とすると前述の各
相の電圧指令値（ｖR*，ｖS*，ｖT*）の振幅は１
以下にすることが望ましい。According to the control method of the conventional PWM control self-excited rectifier 10, the power regeneration from the load 2 to the commercial power supply 1, which is the purpose of adopting the self-excited rectifier, can be performed. Power factor seen from commercial power supply 1 is almost 1
Therefore, in order to control the input AC current of the main circuit 11 of the self-excited rectifier in accordance with the above purpose, if the amplitude of the output of the carrier signal generator 28 is set to 1, the voltage command of each phase described above is set. the value(v R *, v S * , v T *) amplitude of 1
It is desirable to make the following.
【０００６】例えば、商用電源１を３φ４４０Ｖ（Ａ
Ｃ）とすると、ＰＷＭ制御自励式整流装置１０の出力の
定常状態での直流電圧が６８０Ｖ（ＤＣ）程度が望まし
く、この直流電圧より得られる上述の制御方法による交
流電圧は２４０Ｖ（ＡＣ）となり、一方、前記商用電源
１の相電圧は２５４Ｖ（ＡＣ）であることから、電流調
節器２５，２６，２７がこの電圧差に起因して飽和状態
になることがあり、その結果、自励式整流器の主回路１
１の入力交流電流が歪み、該入力交流電流の高調波成分
が増加するという問題があった。For example, when the commercial power supply 1 is connected to a 3φ440 V (A
C), the DC voltage in the steady state of the output of the PWM control self-excited rectifier 10 is desirably about 680 V (DC), and the AC voltage obtained from the DC voltage by the above-described control method is 240 V (AC). On the other hand, since the phase voltage of the commercial power supply 1 is 254 V (AC), the current regulators 25, 26, and 27 may become saturated due to this voltage difference. Main circuit 1
1 has a problem that the input AC current is distorted and the harmonic component of the input AC current increases.
【０００７】この発明の目的は、上記問題点を解決する
ＰＷＭ制御自励式整流装置の制御方法を提供することに
ある。An object of the present invention is to provide a control method for a PWM control self-excited rectifier which solves the above problems.
【０００８】[0008]
【課題を解決するための手段】商用電源の交流電力を３
相の自励式整流器により直流電力に変換して負荷に給電
する自励式整流装置であって、前記自励式整流器の出力
の直流電圧を検出し、この直流電圧が所定の値になるよ
うに電圧の調節演算をし、この電圧の調節演算により得
られた電流指令値（直流量）と前記商用電源の位相に同
期した角度信号とにより各相電流指令値（交流量）を演
算し、この各相電流指令値に追従するように前記商用電
源の各相電流を検出して電流の調節演算をし、この各相
の電流の調節演算により得られた各相の電圧指令値（交
流量）とキャリア信号とによりＰＷＭ制御された各相ゲ
ート信号を生成し、この各相ゲート信号により前記自励
式整流器の自己消弧形半導体素子を制御するＰＷＭ制御
自励式整流装置の制御方法において、この第１の発明
は、前記各相の電圧指令値（交流量）の内のいずれかの
相の零位相を基準として６０°（電気角）ごとの期間に
分割し、それぞれの６０°期間中の各相の電圧指令値
（交流量）のうちその絶対値が最大である相の電圧指令
値を、該電圧指令値の極性と同一極性の前記キャリア信
号の振幅値から減算し、この減算値に所定の係数を乗じ
た補助指令値を求め、この６０°期間中のそれぞれの相
の新たな電圧指令値は、当該する相の電圧指令値（交流
量）と前記補助指令値とを加算した値とし、前記各相の
新たな電圧指令値と前記キャリア信号とによりＰＷＭ制
御された新たな各相ゲート信号を生成し、また第２の発
明は、前記各相の電圧指令値（交流量）の内のいずれか
の相の零位相を基準として、該電圧指令値の３倍の周波
数で所定の振幅を有する補助正弦波信号を生成し、それ
ぞれの相の新たな電圧指令値は、当該する相の電圧指令
値（交流量）と前記補助正弦波信号とを加算した値と
し、前記各相の新たな電圧指令値と前記キャリア信号と
によりＰＷＭ制御された新たな各相ゲート信号を生成す
る。[MEANS FOR SOLVING THE PROBLEMS] The AC power of the commercial power supply is 3
A self-commutated rectifier for converting a DC power into a DC power by a self-excited rectifier of a phase and feeding the load to a load. An adjustment operation is performed, and a phase current command value (AC amount) is calculated based on a current command value (DC amount) obtained by the voltage adjustment operation and an angle signal synchronized with the phase of the commercial power supply. Each phase current of the commercial power supply is detected so as to follow the current command value, and a current adjustment operation is performed. A voltage command value (AC amount) of each phase obtained by the current adjustment operation of each phase and a carrier are calculated. The PWM control self-excited rectifier control method of generating each phase gate signal subjected to PWM control based on the signals and controlling the self-extinguishing type semiconductor device of the self-excited rectifier by the respective phase gate signals. The invention relates to the voltage of each phase The reference value is divided into periods at intervals of 60 ° (electrical angle) based on the zero phase of one of the phases of the reference value (AC amount), and the voltage command value (AC amount) of each phase during each 60 ° period is calculated. The voltage command value of the phase having the maximum absolute value is subtracted from the amplitude value of the carrier signal having the same polarity as the polarity of the voltage command value, and an auxiliary command value obtained by multiplying the subtracted value by a predetermined coefficient is obtained. The new voltage command value of each phase during the 60 ° period is a value obtained by adding the voltage command value (AC amount) of the relevant phase and the auxiliary command value, and the new voltage command value of each phase is obtained. And the carrier signal generates a new gate signal for each phase which is PWM-controlled. The second invention is based on the zero phase of any one of the voltage command values (AC amount) of each phase. As an auxiliary sine wave signal having a predetermined amplitude at a frequency three times the voltage command value. The new voltage command value of each phase is a value obtained by adding the voltage command value (AC amount) of the corresponding phase and the auxiliary sine wave signal, and the new voltage command value of each phase and the carrier A new gate signal is generated for each phase, which is PWM-controlled by the signals.
【０００９】この発明の制御方法によれば、自励式整流
器が発生する交流電圧の線間電圧を正弦波に保つ条件
で、後述の数式で得られる補助指令値または前記３倍の
周波数の補助正弦波信号を、従来の制御方法の各相の電
圧指令値（交流量）に加算した値を新たな各相の電圧指
令値とすることで、より低い直流電圧から所望の交流電
圧を得ることが可能となる。According to the control method of the present invention, under the condition that the line voltage of the AC voltage generated by the self-excited rectifier is maintained as a sine wave, the auxiliary command value obtained by the following mathematical expression or the auxiliary sine of the triple frequency is used. By adding the wave signal to the voltage command value (AC amount) of each phase in the conventional control method as a new voltage command value of each phase, a desired AC voltage can be obtained from a lower DC voltage. It becomes possible.
【００１０】[0010]
【発明の実施の形態】図１は、この発明の第１の実施例
を示すＰＷＭ制御自励式整流装置のブロックであり、図
５に示した従来例と同一機能を有するものには同一符号
を付して説明を省略する。図１において、ＰＷＭ制御自
励式整流装置４０には、電流調節器２５，２６，２７そ
れぞれの出力である各相の電圧指令値（ｖR*，
ｖS*，ｖT*）の内のいずれかの相の零位相を基準と
して６０°（電気角）ごとの期間に分割し、それぞれの
６０°期間中の各相の電圧指令値（ｖR*，ｖS*，ｖ
T*）の内、その絶対値が最大である相の電圧指令値
（ｖR*，ｖS*，ｖT*）を、この相の電圧指令値
（ｖR*，ｖS*，ｖT*）の極性と同一極性のキャリ
ア信号の振幅値から減算し、この減算値に所定の係数を
乗じた補助指令値Ｖ0を求め、該６０°期間中のそれぞ
れの相の新たな電圧指令値（ｖRR*，ｖSS*，ｖTT*）
は、当該する電圧指令値（ｖR*，ｖS*，ｖT*）と
前記補助指令値Ｖ0とを加算した値とする電圧指令値変
換回路４１を備えている。FIG. 1 is a block diagram of a PWM control self-excited rectifier according to a first embodiment of the present invention, in which components having the same functions as those of the conventional example shown in FIG. The description is omitted here. In FIG. 1, a PWM command self-excited rectifier 40 has a voltage command value (vR* ,
vS* , vT* ), the phase is divided into periods at intervals of 60 ° (electrical angle) based on the zero phase of any of the phases, and the voltage command value (vR ) of each phase during each 60 ° period* , VS* , v
T*) of the voltage command value of the phase absolute value is maximum(v R *, v S * , v T *) a voltage command value of the phase(v R *, v S * , v T* ) Is subtracted from the amplitude value of the carrier signal having the same polarity as the polarity, and an auxiliary command value V0 obtained by multiplying the subtracted value by a predetermined coefficient is obtained. A new voltage command value of each phase during the 60 ° period is obtained. (VRR* , vSS* , vTT* )
It is the voltage-command values(v R *, v S * , v T *) and the and a voltage command value conversion circuit 41 to the assist command value V0 and a value obtained by adding a.
【００１１】図２は、この電圧指令値変換回路４１の動
作を説明する説明図である。図２において、電圧指令値
変換回路４１には図２（イ）に示す如く正弦波状の電圧
指令値（ｖR*，ｖS*，ｖT*）が入力され、この図
の場合には、電圧指令値（ｖR*）の零位相を基準とし
て６０°ごとの期間に分割している。電圧指令値（ｖR
*）の０°〜６０°の期間では、電圧指令値（ｖS*）
の絶対値が残りの電圧指令値（ｖR*，ｖT*）より大
きいので、この期間の補助電圧指令値Ｖ0はキァリア信
号の振幅を±αとすると、式（１）で表される。FIG. 2 is an explanatory diagram for explaining the operation of the voltage command value conversion circuit 41. 2, the voltage command value conversion circuit 41 a sinusoidal voltage command value as shown in FIG. 2(b) (v R *, v S *, v T *) is input, in the case of this figure, The voltage command value (vR* ) is divided into periods at intervals of 60 ° with reference to the zero phase. Voltage command value (vR
* ) In the 0 ° to 60 ° period, the voltage command value (vS* )
Is larger than the remaining voltage command values (vR* , vT* ), the auxiliary voltage command value V0 during this period is expressed by equation (1) if the amplitude of the carrier signal is ± α. .
【００１２】[0012]
【数１】Ｖ0＝Ｋ0×（−α−ｖS*） …（１） ここで、Ｋ0は比例定数である。同様に、電圧指令値
（ｖR*）の６０°〜１２０°の期間の前記Ｖ0は、式
（２）で表される。V1 = K0 × (−α−vS* ) (1) where K0 is a proportionality constant. Similarly, the V0 which period 60 ° to 120 ° of the voltage command values (vR*) is represented by the formula (2).
【００１３】[0013]
【数２】Ｖ0＝Ｋ0×（α−ｖR*） …（２） 同様に、電圧指令値（ｖR*）の１２０°〜１８０°の
期間の前記Ｖ0は、式（３）で表される。V0 = K0 × (α−vR* ) (2) Similarly, V0 in the period of 120 ° to 180 ° of the voltage command value (vR* ) is expressed by the following equation (3). It is represented by
【００１４】[0014]
【数３】Ｖ0＝Ｋ0×（−α−ｖT*） …（３） 同様に、電圧指令値（ｖR*）の１８０°〜２４０°の
期間の前記Ｖ0は、式（４）で表される。V0 = K0 × (−α−vT* ) (3) Similarly, V0 in the 180 ° to 240 ° period of the voltage command value (vR* ) is expressed by the following equation (4). ).
【００１５】[0015]
【数４】Ｖ0＝Ｋ0×（α−ｖS*） …（４） 同様に、電圧指令値（ｖR*）の２４０°〜３００°の
期間の前記Ｖ0は、式（５）で表される。V0 = K0 × (α−vS* ) (4) Similarly, V0 in the 240 ° to 300 ° period of the voltage command value (vR* ) is expressed by the following equation (5). It is represented by
【００１６】[0016]
【数５】Ｖ0＝Ｋ0×（−α−ｖR*） …（５） 同様に、電圧指令値（ｖR*）の３００°〜３６０°の
期間の前記Ｖ0は、式（６）で表される。V0 = K0 × (−α−vR* ) (5) Similarly, V0 in the period of 300 ° to 360 ° of the voltage command value (vR* ) is expressed by the formula (6) ).
【００１７】[0017]
【数６】Ｖ0＝Ｋ0×（α−ｖT*） …（６） 図２（ハ）に示す如く、上記式（１）〜式（６）で求め
た各期間の補助電圧指令値Ｖ0とそれぞれの期間の電圧
指令値（ｖR*，ｖS*，ｖT*）とを加算した値から
図２（ロ）に示すような波形が得られ、この波形の新た
な電圧指令値（ｖRR*，ｖSS*，ｖTT*）とキャリア信
号発生器２８の出力とを比較器２９に入力してＰＷＭ制
御を行うようにしている。V0 = K0 × (α−vT* ) (6) As shown in FIG. 2C, the auxiliary voltage command value for each period obtained by the above equations (1) to (6) A waveform shown in FIG. 2B is obtained from the value obtained by adding V0 and the voltage command values (vR* , vS* , vT* ) in each period, and a new voltage command of this waveform is obtained. The values (vRR* , vSS* , vTT* ) and the output of the carrier signal generator 28 are input to a comparator 29 to perform PWM control.
【００１８】この第１の実施例の制御方法は、前記式
（１）〜式（６）に示す補助電圧指令値Ｖ0を求める簡
単な加算演算と、６０°の期間ごとに求めたＶ0に電圧
指令値（ｖR*，ｖS*，ｖT*）を加算する簡単な加
算演算とにより実施できる。また、前記式（１）〜式
（６）に示した比例定数Ｋ0は、キァリア信号の振幅
（±α）を１とすると、Ｋ0＝１．５程度が実用上好適
であり、新たな電圧指令値から得られる線間電圧はそれ
ぞれの相電圧の差であるから、正弦波状の波形となり、
より低い直流電圧から所望の交流電圧を得ることが可能
である。In the control method of the first embodiment, a simple addition operation for obtaining the auxiliary voltage command value V0 shown in the above-mentioned equations (1) to (6) and V0 obtained for every 60 ° period are performed. voltage command value(v R *, v S * , v T *) can be carried out by a simple addition operation for adding to. Further, assuming that the amplitude (± α) of the carrier signal is 1, the proportional constant K0 shown in the equations (1) to (6) is practically preferably about K0 = 1.5. Since the line voltage obtained from the voltage command value is the difference between the respective phase voltages, it becomes a sinusoidal waveform,
It is possible to obtain a desired AC voltage from a lower DC voltage.
【００１９】図３は、この発明の第２の実施例を示すＰ
ＷＭ制御自励式整流装置のブロックであり、図５に示し
た従来例と同一機能を有するものには同一符号を付して
説明を省略する。図３において、ＰＷＭ制御自励式整流
装置５０には、電流調節器２５，２６，２７それぞれの
出力である各相の電圧指令値（ｖR*，ｖS*，
ｖT*）に、例えば、電圧指令値（ｖR*）に同期した
３倍の周波数で所定の振幅を有する補助正弦波信号を生
成し、それぞれの相の新たな電圧指令値（ｖRR*，ｖSS
*，ｖTT*）は、当該する相の電圧指令値（ｖR*，ｖ
S*，ｖT*）と前記補助正弦波信号とを加算する電圧
指令値変換回路５１を備えている。FIG. 3 shows a second embodiment of the present invention.
FIG. 5 shows a block diagram of the WM control self-excited rectifier.
Those having the same functions as those of the conventional example are denoted by the same reference numerals.
Description is omitted. In FIG. 3, PWM control self-excited rectification
The device 50 includes the current regulators 25, 26, and 27 respectively.
Output voltage command value of each phase (vR*, VS*,
vT*) Includes, for example, a voltage command value (vR*)
Generates an auxiliary sine wave signal with a predetermined amplitude at three times the frequency
And a new voltage command value (vRR*, VSS
*, VTT*) Is the voltage command value (vR*, V
S*, VT*) And the auxiliary sine wave signal
A command value conversion circuit 51 is provided.
【００２０】図４は、この電圧指令値変換回路５１の動
作を説明する説明図である。図４において、電圧指令値
変換回路５１には図４（イ）に示す如く正弦波状の電圧
指令値（ｖR*，ｖS*，ｖT*）が入力され、図４
（ハ）に示す如く、電圧指令値（ｖR*）の零位相を基
準として３倍の周波数で所定の振幅を有する補助正弦波
信号（Ｖ1，式（７）参照）を生成し、この補助正弦波
信号Ｖ1と電圧令値（ｖR*，ｖS*，ｖT*）とを加
算した値から図４（ロ）に示すような波形が得られ、こ
の波形の新たな電圧指令値（ｖRR*，ｖSS*，ｖTT*）
とキャリア信号発生器２８の出力とを比較器２９に入力
してＰＷＭ制御を行うようにしている。FIG. 4 is an explanatory diagram for explaining the operation of the voltage command value conversion circuit 51. 4, a voltage command value (vR* , vS* , vT* ) in the form of a sine wave is input to the voltage command value conversion circuit 51 as shown in FIG.
As shown in (c), an auxiliary sine wave signal (V1 , see equation (7)) having a predetermined amplitude at a frequency tripled with respect to the zero phase of the voltage command value (vR* ) is generated. auxiliary sinusoidal signal V1 and the voltage command value(v R *, v S * , v T *) and the waveform as shown in FIG. 4 (b) is obtained from a value obtained by adding a new voltage command waveform Value (vRR* , vSS* , vTT* )
And the output of the carrier signal generator 28 are input to a comparator 29 to perform PWM control.
【００２１】この第２の実施例の制御方法では、先ず、
角度信号発生手段１６の出力の角度信号θから、例え
ば、ＲＯＭテーブルなどにより式（７）に示す補助正弦
波信号（Ｖ1）を生成する。In the control method of the second embodiment, first,
From the angle signal θ output from the angle signal generating means 16, an auxiliary sine wave signal (V1 ) shown in Expression (7) is generated by, for example, a ROM table or the like.
【００２２】[0022]
【数７】Ｖ1＝Ｋ1×ｓｉｎ（３・θ） …（７） ここで、Ｋ1はＶ1の振幅を決める比例定数である。式
（７）に示すＶ1に電圧指令値（ｖR*，ｖS*，ｖT
*）を加算する簡単な加算演算により新たな電圧指令値
（ｖRR*，ｖSS*，ｖTT*）が得られる。V1 = K1 × sin (3 · θ) (7) where K1 is a proportional constant that determines the amplitude of V1 . Voltage command value V1 represented by the formula(7) (v R *, v S *, v T
* ), New voltage command values (vRR* , vSS* , vTT* ) are obtained by a simple addition operation.
【００２３】また、前記式（７）示した比例定数Ｋ
1は、キァリア信号の振幅（±α）を１とすると、Ｋ1
＝０．３程度が実用上好適であり、新たな電圧指令値か
ら得られる線間電圧はそれぞれの相電圧の差であるか
ら、正弦波状の波形となり、より低い直流電圧から所望
の交流電圧を得ることが可能である。Also, the proportionality constant K shown in the above equation (7)
1 is K1 where the amplitude (± α) of the carrier signal is1.
= 0.3 is practically preferable, and the line voltage obtained from the new voltage command value is a difference between the respective phase voltages, so that the waveform becomes a sinusoidal waveform, and a desired AC voltage is converted from a lower DC voltage. It is possible to get.
【００２４】[0024]
【発明の効果】この発明によれば、ＰＷＭ制御自励式整
流装置の出力の直流電圧から商用電源が所望する交流電
圧を得るためには、前記直流電圧を従来の制御方法に比
して低く設定することが簡単な加算演算で可能となり、
その結果、ＰＷＭ制御自励式整流装置の低価格化，小型
化に寄与できる。According to the present invention, in order to obtain a desired AC voltage from a commercial power supply from the DC voltage output from the PWM control self-excited rectifier, the DC voltage is set lower than in the conventional control method. Can be performed by a simple addition operation,
As a result, it is possible to contribute to cost reduction and size reduction of the PWM control self-excited rectifier.
【図１】この発明の第１の実施例を示すＰＷＭ制御自励
式整流装置のブロック構成図FIG. 1 is a block diagram of a PWM control self-excited rectifier according to a first embodiment of the present invention.
【図２】図１の動作を説明する説明図FIG. 2 is an explanatory diagram for explaining the operation of FIG. 1;
【図３】この発明の第２の実施例を示すＰＷＭ制御自励
式整流装置のブロック構成図FIG. 3 is a block diagram showing a PWM control self-excited rectifier according to a second embodiment of the present invention;
【図４】図３の動作を説明する説明図FIG. 4 is an explanatory diagram for explaining the operation of FIG. 3;
【図５】従来例を示すＰＷＭ制御自励式整流装置のブロ
ック構成図FIG. 5 is a block diagram of a PWM control self-excited rectifier showing a conventional example.
１…商用電源、２…負荷、１０，４０，５０…ＰＷＭ制
御自励式整流装置、１１…自励式整流器の主回路、１２
…交流リアクトル、１３…コンデンサ、１４…相電圧検
出器、１５，２０…絶縁変換器、１６…角度信号発生手
段、１７，１８…正弦波発生器、１９…電圧設定器、２
１…電圧調節器、２２，２３…乗算器、２４…電流検出
器、２５〜２７…電流調節器、２８…キャリア信号発生
器、２９…比較器、３０…ゲート駆動回路、４１，５１
…電圧指令値変換回路。DESCRIPTION OF SYMBOLS 1 ... Commercial power supply, 2 ... Load, 10, 40, 50 ... PWM control self-excited rectifier, 11 ... Main circuit of self-excited rectifier, 12
... AC reactor, 13 ... capacitor, 14 ... phase voltage detector, 15, 20 ... insulation converter, 16 ... angle signal generating means, 17, 18 ... sine wave generator, 19 ... voltage setting device, 2
DESCRIPTION OF SYMBOLS 1 ... Voltage regulator, 22, 23 ... Multiplier, 24 ... Current detector, 25-27 ... Current regulator, 28 ... Carrier signal generator, 29 ... Comparator, 30 ... Gate drive circuit, 41, 51
... voltage command value conversion circuit.
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8268216AJPH10117481A (en) | 1996-10-09 | 1996-10-09 | Control method of PWM control self-excited rectifier |
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8268216AJPH10117481A (en) | 1996-10-09 | 1996-10-09 | Control method of PWM control self-excited rectifier |
| Publication Number | Publication Date |
|---|---|
| JPH10117481Atrue JPH10117481A (en) | 1998-05-06 |
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8268216APendingJPH10117481A (en) | 1996-10-09 | 1996-10-09 | Control method of PWM control self-excited rectifier |
| Country | Link |
|---|---|
| JP (1) | JPH10117481A (en) |
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110190760A (en)* | 2019-05-28 | 2019-08-30 | 上海联影医疗科技有限公司 | High pressure generator fairing |
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH07200084A (en)* | 1993-12-28 | 1995-08-04 | Hitachi Ltd | Power converter |
| JPH07337019A (en)* | 1994-06-02 | 1995-12-22 | Fuji Electric Co Ltd | Control method for self-excited rectifier |
| JPH08214550A (en)* | 1995-02-01 | 1996-08-20 | Hitachi Ltd | PWM converter control device |
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH07200084A (en)* | 1993-12-28 | 1995-08-04 | Hitachi Ltd | Power converter |
| JPH07337019A (en)* | 1994-06-02 | 1995-12-22 | Fuji Electric Co Ltd | Control method for self-excited rectifier |
| JPH08214550A (en)* | 1995-02-01 | 1996-08-20 | Hitachi Ltd | PWM converter control device |
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110190760A (en)* | 2019-05-28 | 2019-08-30 | 上海联影医疗科技有限公司 | High pressure generator fairing |
| CN110190760B (en)* | 2019-05-28 | 2020-12-15 | 上海联影医疗科技股份有限公司 | High voltage generator rectifier |
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