【発明の詳細な説明】〔産業上の利用分野〕本発明は、ディジタル無線通信に用いられる増幅装置に
関し、特に、包路線変動を有する信号を増幅する増幅装
置である。DETAILED DESCRIPTION OF THE INVENTION [Field of Industrial Application] The present invention relates to an amplifying device used in digital wireless communication, and particularly to an amplifying device for amplifying a signal having envelope fluctuation.
一般に、通信に用いられる変調波を増幅する方法として
は、増幅器の線形性を重視して変調波を増幅する方法と
、電力効率を重視して変調波を増幅する方法とがある。Generally, as methods for amplifying modulated waves used in communication, there are two methods: a method of amplifying modulated waves with emphasis on linearity of an amplifier, and a method of amplifying modulated waves with emphasis on power efficiency.
信号の振幅特性の線形性を重視する場合は、増幅器の出
力をある程度下げて、増幅器の振幅特性が線形性を保つ
ような令頁域において変調波を増幅する。この場合は、
信号の帯域外スペクトル特性を良好に保って増幅するこ
とができる。このように、出力を下げた状態で増幅器を
動作させることを出力バックオフをとるという。If the linearity of the amplitude characteristic of the signal is important, the output of the amplifier is lowered to some extent and the modulated wave is amplified in a narrow range where the amplitude characteristic of the amplifier maintains linearity. in this case,
It is possible to amplify the signal while maintaining good out-of-band spectral characteristics. Operating the amplifier with the output reduced in this way is called output back-off.
一方、増幅器の飽和領域（非線形領域）を用いて変調波
を増幅することにより、信号を高い電力効率で増幅する
ことができる。On the other hand, by amplifying the modulated wave using the saturation region (nonlinear region) of the amplifier, the signal can be amplified with high power efficiency.
ところで、帯域制限された線形変調波を、帯域外スペク
トルを劣化させることなく、且つ電力効率良く増幅する
ものとして、本出願人は、特願昭６３−１１４０９８
Ｆ増幅装置」を既に提案している。これは、線形変調波
を２系統の定包絡線変調波に分解し、この２系統の定包
絡線変調波をそれぞれ増幅した後に合成する技法である
。By the way, the present applicant has proposed a method for amplifying band-limited linear modulated waves without deteriorating the out-of-band spectrum and with good power efficiency, in Japanese Patent Application No. 114098/1983.
We have already proposed the F amplifier. This is a technique in which a linearly modulated wave is decomposed into two systems of constant envelope modulated waves, and these two systems of constant envelope modulated waves are amplified and then combined.
第７図は、この技法を用いた増幅装置の一具体例を示す
。FIG. 7 shows a specific example of an amplification device using this technique.
図において、入力信号波５（ｔ）は、直交検波器７１に
より２つの直交変調信号成分Ｉ （ｔ） 、 Ｑ（ｔ）
に分解される。In the figure, an input signal wave 5(t) is divided into two orthogonally modulated signal components I (t) and Q(t) by a quadrature detector 71.
It is decomposed into
波形生成用演算回路７２は、この２つの直交変調信号成
分１ （ｔ） 、 Ｑ（ｔ）に基づいて、２系統の直
交変調信号ｘ、（ｔ）、 Ｑｔ（ｔ）およびＩｚ（ｔ）
、 Ｑ２（ｔ）を生成する。ここで、２系統の直交変調
信号Ｉ＋（ｔ）、 Ｑｔ（ｔ）およびＬ（ｔ）、
Ｑｚ（ｔ）は、これらを合成することにより入力信号波
５（ｔ）が再生されるように生成される。The waveform generation arithmetic circuit 72 generates two systems of orthogonal modulation signals x, (t), Qt(t) and Iz(t) based on these two orthogonal modulation signal components 1 (t) and Q(t).
, generates Q2(t). Here, two systems of orthogonal modulation signals I+(t), Qt(t) and L(t),
Qz(t) is generated such that the input signal wave 5(t) is reproduced by combining these.
直交変調器７．３．７４は、それぞれ直交変調信号Ｉｔ
（ｔ）、 Ｑｔ（ｔ）およびＩｚ（ｔ）、 Ｑｚ（ｔ）
によって搬送波を変調して、２系統の定包絡線変調波Ｓ
、（ｔ）および５ｚ（ｔ）を出力する。The quadrature modulators 7, 3, and 74 each receive a quadrature modulation signal It.
(t), Qt(t) and Iz(t), Qz(t)
The carrier wave is modulated by the constant envelope modulated wave S of two systems.
, (t) and 5z(t).
それぞれ増幅器７５．７６を高い電力効率が得られる飽
和領域（非線形領域）において動作させ、この２系統の
定包絡線変調波Ｓ ＋ （ｔ）および５ｚ（ｔ）を増幅
する。その後、合成器７７によって、増幅器７５．７６
の出力を合成し、出力信号波Ｓ、 （ｔ）を得る。The amplifiers 75 and 76 are respectively operated in a saturation region (nonlinear region) where high power efficiency can be obtained, and these two systems of constant envelope modulated waves S + (t) and 5z (t) are amplified. Then, by the combiner 77, the amplifiers 75, 76
The outputs of are combined to obtain an output signal wave S, (t).
しかしながら、上述した技法においては、２系統の直交
変調信号から求められる位相差の計算値α。と、合成器
７７に入力される２系統の定包絡線変調波の間の位相差
αとが一致することを前提としている。そのため、この
２つの位相差α。。However, in the technique described above, the calculated value α of the phase difference obtained from the two systems of orthogonal modulation signals. It is assumed that the phase difference α between the two systems of constant envelope modulated waves input to the synthesizer 77 is the same. Therefore, the phase difference α between these two. .
αが一致しない場合は、入力信号を復元することができ
ないため、帯域外スペクトルが劣化するという欠点を有
している。If α does not match, the input signal cannot be restored, resulting in a disadvantage that the out-of-band spectrum deteriorates.
ところで、実際の回路においては、２系統の定包絡線変
調波が伝送される伝送路の電気的な長さ、（以後、電気
長と称する）は異なっていることが多い。この場合、２
系統の定包絡線変調波が伝送される間、位相差の計算値
α。が正確に保たれないので、合成器７７の２つの入力
の間の位相差αと位相差の計算値α。とは一致しない。By the way, in actual circuits, the electrical lengths (hereinafter referred to as electrical lengths) of transmission paths through which two systems of constant envelope modulated waves are transmitted are often different. In this case, 2
Calculated value α of the phase difference while the constant envelope modulated wave of the system is transmitted. The phase difference α between the two inputs of the synthesizer 77 and the calculated value of the phase difference α. does not match.
また、初期において２系統の伝送路の電気長が一致する
ように調整した場合においても、使用中の外部の温度変
化や経年変化によって電気長に差が生じることが予想さ
れる。Further, even if the electrical lengths of the two transmission lines are initially adjusted to match, it is expected that the electrical lengths will differ due to external temperature changes during use or changes over time.
本発明は、このような点にかんがみて創作されたもので
あり、包路線変動を有する信号を帯域外スペクトルを劣
化させることな（、電力効率よく増幅するようにした増
幅装置を提供することを目的としている。The present invention was created in view of these points, and aims to provide an amplification device that amplifies signals having envelope fluctuations without degrading the out-of-band spectrum (and with high power efficiency). The purpose is
第１図は、本発明による増幅装置の構成図である。FIG. 1 is a block diagram of an amplifying device according to the present invention.
図において、波形生成用演算手段は、変調信号が導入さ
れ、２系統の定包絡線変調波のそれぞれに対応する第１
変調信号および第２変調信号を出力する。In the figure, the waveform generation calculation means has a first waveform into which a modulation signal is introduced and which corresponds to each of two systems of constant envelope modulated waves.
A modulated signal and a second modulated signal are output.
第１変調手段は、第１変調信号を入力として、これに対
応する第１変調波を出力する。The first modulation means receives the first modulation signal as input and outputs a first modulation wave corresponding to the first modulation signal.
位相補正手段は、第２変調信号の位相を補正する。The phase correction means corrects the phase of the second modulation signal.
第２変調手段は、位相補正手段の出力を入力として、こ
れに対応する第２変調波を出力する。The second modulation means receives the output of the phase correction means as input and outputs a second modulated wave corresponding thereto.
２つの増幅手段は、第１変調波、第２変調波のそれぞれ
を飽和領域において増幅する。The two amplification means amplify each of the first modulated wave and the second modulated wave in the saturation region.
合成手段は、両増幅手段によって増幅された２つの変調
波を加算する。The combining means adds the two modulated waves amplified by both amplifying means.
第１位相差検出手段は、第１変調信号および第２変調信
号に基づいて、２系統の定包絡線変調波の位相差を検出
する。The first phase difference detection means detects the phase difference between the two systems of constant envelope modulated waves based on the first modulation signal and the second modulation signal.
第２位相差検出手段は、２つの増幅手段の出力の位相差
を検出する。The second phase difference detection means detects the phase difference between the outputs of the two amplification means.
比較手段は、第１位相差検出手段、第２位相差検出手段
のそれぞれにおいて検出された２つの位相差を比較して
２系統の定包絡線変調波の位相差と２つの増幅手段の出
力の位相差との間に生じた位相誤差を検出する。The comparison means compares the two phase differences detected by each of the first phase difference detection means and the second phase difference detection means, and determines the phase difference between the two constant envelope modulated waves and the output of the two amplification means. Detects the phase error that occurs between the phase difference and the phase difference.
従って、全体として、比較手段により検出された位相誤
差に基づいて、位相補正手段により第２変調信号の位相
を補正するように構成する。Therefore, as a whole, the phase correction means corrects the phase of the second modulation signal based on the phase error detected by the comparison means.
変調信号が入力される波形生成用演算手段は、第１変調
信号および第２変調信号を出力する。ここで、第１変調
信号および第２変調信号は、これらを合成することによ
り入力された変調信号が再生されるように生成する。The waveform generation calculation means to which the modulation signal is input outputs a first modulation signal and a second modulation signal. Here, the first modulation signal and the second modulation signal are generated so that the input modulation signal is reproduced by combining them.
２つの変調手段は、それぞれが対応する変調信号によっ
て搬送波を変調して２系統の定包絡線変調波を出力する
。これら２系統の定包絡線変調波は、それぞれ電力効率
の高い飽和領域において動作する増幅手段によって増幅
された後、合成手段によって加算され、出力信号となる
。The two modulation means each modulate the carrier wave with a corresponding modulation signal and output two systems of constant envelope modulated waves. These two systems of constant envelope modulated waves are each amplified by an amplifying means operating in a saturation region with high power efficiency, and then added by a combining means to form an output signal.
第１位相差検出手段により、第１変調信号と第２変調信
号に基づいて、２系統の定包絡線変調波の位相差が検出
される。また、第２位相差検出手段により、２つの増幅
手段の出力の間の位相差が検出される。The first phase difference detection means detects the phase difference between the two systems of constant envelope modulated waves based on the first modulation signal and the second modulation signal. Further, the second phase difference detection means detects the phase difference between the outputs of the two amplification means.
この第１位相差検出手段と第２位相差検出手段によって
検出された２つの位相差は、比較手段により比較され、
２つの位相差の間に生じた位相誤差が検出される。この
位相誤差に基づいて、位相差補正制御手段により、２系
統の定包絡線変調波の位相差と２つの増幅手段の出力の
位相差とが所定の関係となるように、第２変調信号の位
相が補正される。The two phase differences detected by the first phase difference detection means and the second phase difference detection means are compared by a comparison means,
A phase error occurring between the two phase differences is detected. Based on this phase error, the phase difference correction control means adjusts the second modulation signal so that the phase difference between the two systems of constant envelope modulated waves and the phase difference between the outputs of the two amplification means have a predetermined relationship. The phase is corrected.
本発明にあっては、入力された変調信号に基づいて２系
統の定包絡線変調波を生成し、この２系統の定包絡線変
調波をそれぞれ増幅した後に合成することにより、搬送
波を入力された変調信号で変調した信号を線形増幅した
場合と同様の波形を得る。In the present invention, two systems of constant envelope modulated waves are generated based on the input modulated signal, and these two systems of constant envelope modulated waves are respectively amplified and then combined, thereby generating a carrier wave. A waveform similar to that obtained when a signal modulated with a modulated signal is linearly amplified is obtained.
また、比較手段により検出された位相誤差に基づいて、
位相補正手段により第２変調信号の位相が補正される。Also, based on the phase error detected by the comparison means,
The phase of the second modulation signal is corrected by the phase correction means.
これにより、２系統の定包絡線変調波の位相差と２つの
増幅手段の出力の位相差との間に生じた位相誤差を補正
することができるので、合成手段によって信号が正確に
復元される。As a result, it is possible to correct the phase error that occurs between the phase difference between the two systems of constant envelope modulated waves and the phase difference between the outputs of the two amplifying means, so that the signal can be accurately restored by the combining means. .
以下、図面に基づいて本発明の実施例について詳細に説
明する。Hereinafter, embodiments of the present invention will be described in detail based on the drawings.
第２図は、本発明の第１実施例における増幅装置の構成
を示す。FIG. 2 shows the configuration of an amplifier device in a first embodiment of the present invention.
第３図は、本発明の第２実施例における増幅装置の構成
を示す。FIG. 3 shows the configuration of an amplifier device in a second embodiment of the present invention.
Ｉ、第１実施例の構成および動作第２図において、直列並列変換回路１１は、入力された
直列の変調信号を２つの並列の直交変調信号！（ｔ）、
Ｑ（ｔ）に変換する。ここで、直交変調信号１（ｔ
）、 Ｑ（ｔ）によって搬送波を変調した信号を入力信
号波Ｓ ｉ （ｔ）と称する。I. Configuration and operation of the first embodiment In FIG. 2, the serial/parallel conversion circuit 11 converts the input serial modulation signal into two parallel orthogonal modulation signals! (t),
Convert to Q(t). Here, orthogonal modulation signal 1 (t
), Q(t) to modulate the carrier wave is called an input signal wave S i (t).
波形生成用演算回路１２は、この直交変調信号Ｉ （ｔ
） 、 Ｑ（ｔ）を用いて、２系統の直交変調信号１
＋（ｔ）、 Ｑ＋Ｄ）およびＴｚ（ｔ）、 Ｑｚ（
ｔ）を生成する。The waveform generation arithmetic circuit 12 generates this quadrature modulation signal I (t
), Q(t), two systems of orthogonal modulation signals 1
+(t), Q+D) and Tz(t), Qz(
t).
ここで、第４図に、直交変調信号Ｉ （ｔ）、 ＱＤ
）と２系統の直交変調信号１＋（ｔ）、Ｑ＋（Ｌ）およ
び１ｚ（ｔ）、 Ｑｚ（ｔ）の関係を示す。図において
、反時計回りの方向が位相の正の方向であるものとする
。Here, FIG. 4 shows orthogonal modulation signals I (t), QD
) and two systems of orthogonal modulation signals 1+(t), Q+(L) and 1z(t), Qz(t). In the figure, it is assumed that the counterclockwise direction is the positive phase direction.
図のように、２系統の直交変調信号１１（ｔ）、 Ｑ
ｌ（Ｌ）およびＩ ｚ（ｔ） 、 Ｑｚ（ｔ）に対応す
る定包絡線変調波Ｓ 、 （ｔ）および５２（ｔ）を合
成することにより入力信号波Ｓ ｉ （Ｌ）が再生され
る。As shown in the figure, two systems of orthogonal modulation signals 11(t), Q
The input signal wave S i (L) is reproduced by combining constant envelope modulated waves S , (t) and 52 (t) corresponding to l (L), I z (t), and Qz (t). .
波形生成演算回路１２においては、入力信号波Ｓ ｉ
（ｔ）の位相φ。と２系統の定包絡線変調波Ｓ＋（ｔ）
、 ５ｚ（ｔ）のそれぞれの位相φ１．φ２とが所定
の関係を満たすように、直交変調信号１＋（ｔ）。In the waveform generation calculation circuit 12, the input signal wave S i
(t) phase φ. and two systems of constant envelope modulated waves S+(t)
, 5z(t), each phase φ1. orthogonal modulation signal 1+(t) such that φ2 satisfies a predetermined relationship.
Ｑｌ（ｔ）およびＩｔ（ｔ）、 Ｑｚ（ｔ）が生成され
る。Ql(t), It(t), and Qz(t) are generated.
以後、直交変調信号１＋（ｔ）、 Ｑｌ（ｔ）およびＩ
ｚ（ｔ）、 Ｑｚ（ｔ）から求められる２系統の定包
絡線変調波の位相差（φ、−φ８）を位相差の計算値を
位相差α。と称する。Hereafter, orthogonal modulation signals 1+(t), Ql(t) and I
The phase difference (φ, -φ8) between the two systems of constant envelope modulated waves obtained from zz(t) and Qz(t) is the calculated value of the phase difference α. It is called.
直交変調器１３は、このようにして得られた直交変調信
号ｒ＋（ｔ）、 Ｑｌ（ｔ）によって搬送波を変調して
定包絡線変調波Ｓ ＋ （ｔ）を生成する。The orthogonal modulator 13 modulates the carrier wave with the thus obtained orthogonal modulation signals r+(t) and Ql(t) to generate a constant envelope modulated wave S + (t).
直交変調器１４は、位相補正回路２２を介して導入され
た直交変調信号Ｔｚ（ｔ）、 ＱＺ（ｔ）に基づいて定
包絡線変調波５Ｚ（ｔ）を生成する。The quadrature modulator 14 generates a constant envelope modulated wave 5Z(t) based on the quadrature modulated signals Tz(t) and QZ(t) introduced via the phase correction circuit 22.
増幅器１５．１６は、それぞれ定包絡線変調波５ｔ（ｔ
）および５ｚ（ｔ）を高い電力効率が得られる飽和領域
において増幅する。以後、増幅器１５，１６の出力をそ
れぞれ定包絡線変調波５ａｔ（ｔ） 、 ｓ１□（１
） と称する。Amplifiers 15 and 16 each generate a constant envelope modulated wave 5t (t
) and 5z(t) are amplified in the saturation region where high power efficiency is obtained. Thereafter, the outputs of the amplifiers 15 and 16 are converted into constant envelope modulated waves 5at(t) and s1□(1
).
定包絡線変調波Ｓ ａｔ （ｔ） 、 Ｓ ａｘ（ｔ
）は、合成器１７により合成されて、出力信号波Ｓ。（
１）として出力される。Constant envelope modulated waves S at (t), S ax(t
) are synthesized by the synthesizer 17 to produce an output signal wave S. (
1) is output.
位相比較回路１８は、２系統の直交変調信号Ｉ＋（ｔ）
、 ＱｌＤ）およびＬ（ｔ）、 Ｑｇ（ｔ）に基づ
いて、位相差の計算値α。が９０度のときにトリガパル
スＴを出力し、位相誤差検出回路２１に供給している。The phase comparator circuit 18 receives two systems of orthogonal modulation signals I+(t)
, QlD) and L(t), Qg(t), the calculated value of the phase difference α. A trigger pulse T is output when the angle is 90 degrees, and is supplied to the phase error detection circuit 21.
位相比較回路１９は、２系統の定包絡線変調波Ｓ、、（
ｔ）、Ｓ、□（１）の位相差を検出する。位相比較回路
１９の出力は、ローパスフィルタ２０を透過することに
より高周波成分が取り除かれて、２系統の定包絡線変調
波Ｓ、＋（ｔ）、Ｓ、□（１）の位相差αに対応した信
号となる。以後、ローパスフィルタ２０の出力を位相差
検出信号５ｐ（ｔ）と称する。この位相差検出信号５ｐ
（Ｕ は、位相誤差検出回路２１に導入されている。The phase comparator circuit 19 generates two systems of constant envelope modulated waves S, (
t), S, □(1) is detected. The output of the phase comparison circuit 19 passes through a low-pass filter 20 to remove high frequency components, and corresponds to the phase difference α between the two constant envelope modulated waves S, +(t), S, □(1). This will be a signal. Hereinafter, the output of the low-pass filter 20 will be referred to as a phase difference detection signal 5p(t). This phase difference detection signal 5p
(U is introduced into the phase error detection circuit 21.
ここで、位相比較回路１９は、入力信号の位相差αが９
０度あるいは２７０度のときに出力の値が“０゛となる
ような特性を持つものとする。また、入力信号の位相差
αが０度のとき出力の値は最大となり、一方、位相差α
が１８０度のとき最小となる。Here, the phase comparison circuit 19 calculates that the phase difference α of the input signal is 9.
It is assumed that the output value is 0 degrees when the input signal phase difference α is 0 degrees or 270 degrees.The output value is maximum when the input signal phase difference α is 0 degrees; α
is minimum when is 180 degrees.
第５図に、２系統の定包絡線変調波Ｓｉ＋（ｔ） 。FIG. 5 shows two systems of constant envelope modulated waves Si+(t).
Ｓ、ｚ（ｔ）の関係を示す。The relationship between S and z(t) is shown.
位相差検出信号Ｓ、（ｔ）の値は、第５図（ａ）のよう
に、２系統の定包絡線変調波Ｓ、＋（ｔ） 、 Ｓ、
ｚ（ｔ）の位相差αが９０度のとき“０パとなる。また
、第５図（ｂ）のように、位相差αが９０度よりも大き
いときは位相差検出信号５ｐ（ｔ）の値は負となり、一
方、第５図（Ｃ）のように、９０度よりも小さいときは
正となる。The value of the phase difference detection signal S,(t) is, as shown in FIG. 5(a), two systems of constant envelope modulated waves S,+(t), S,
When the phase difference α of z(t) is 90 degrees, it becomes “0”. Also, as shown in FIG. 5(b), when the phase difference α is larger than 90 degrees, the phase difference detection signal 5p(t) The value of is negative, and on the other hand, when it is smaller than 90 degrees, as shown in FIG. 5(C), it is positive.
位相誤差検出回路２１は、トリガパルスＴが発生した時
点において、位相差検出信号５ｐ（ｔ）の値を調べるこ
とにより位相誤差を検出する。トリガパルスＴが発生し
たときに、位相差検出信号５ｐ（１）の値が“０°°で
あれば位相誤差δの値は０“。The phase error detection circuit 21 detects a phase error by checking the value of the phase difference detection signal 5p(t) at the time when the trigger pulse T is generated. When the trigger pulse T is generated, if the value of the phase difference detection signal 5p(1) is 0°, the value of the phase error δ is 0.
である。一方、位相差検出信号５ｐ（ｔ）が正の値であ
れば位相誤差δは負の方向に生じていることが分かる。It is. On the other hand, if the phase difference detection signal 5p(t) has a positive value, it can be seen that the phase error δ occurs in the negative direction.
また、位相差検出信号Ｓ、（ｔ）が負の値であれば位相
誤差δは正の方向に生じていることが分かる。位相誤差
検出回路２１は、この位相誤差の検出結果を位相誤差制
御回路２２に供給する。Furthermore, it can be seen that if the phase difference detection signal S,(t) has a negative value, the phase error δ occurs in the positive direction. The phase error detection circuit 21 supplies the detection result of this phase error to the phase error control circuit 22.
位相誤差制御回路２２は、位相誤差δの値が負である場
合は、定包絡線変調波Ｓ３□（１）の位相が相対的に進
み過ぎていると判断する。このとき位相誤差制御回路２
２は、定包絡線変調波Ｓ。（１）の位相が遅れるように
、直交変調信号１．（ｔ）、 Ｑ２（ｔ）に補正を加
える。一方、位相誤差δの値が正である場合は、逆に定
包絡線変調波５ａ２（ｔ）の位相が進むように、直交変
調信号１ｚ（ｔ）、 Ｑｚ（ｔ）に補正を加える。If the value of the phase error δ is negative, the phase error control circuit 22 determines that the phase of the constant envelope modulated wave S3□(1) is relatively advanced. At this time, the phase error control circuit 2
2 is a constant envelope modulated wave S. (1) so that the phase of the quadrature modulated signal 1. (t) and Q2(t) are corrected. On the other hand, if the value of the phase error δ is positive, correction is applied to the orthogonal modulation signals 1z(t) and Qz(t) so that the phase of the constant envelope modulated wave 5a2(t) advances.
このようにして、伝送路の電気長が異なることによって
発生した位相誤差を補正する。In this way, phase errors caused by different electrical lengths of the transmission lines are corrected.
■、第２実施例の構成および動作第３図において、第２実施例による増幅装置は合成手段
としてハイブリッド２３を用い、微分回路２４を付加し
て構成されている。また、ハイブリッド２３の出力端子
の一方は終端回路２５を介して終端されている。(2) Structure and operation of the second embodiment In FIG. 3, the amplifier according to the second embodiment uses a hybrid 23 as a synthesizing means and is constructed by adding a differentiating circuit 24. Further, one of the output terminals of the hybrid 23 is terminated via a termination circuit 25.
ハイブリッド２３の入力端子■１と入力端子Ｉ２には、
それぞれ定包絡線変調波Ｓ、＋（ｔ）、ｓ、□（１）が
導入されている。ハイブリッド３７は、定包絡線変調波
Ｓ、Ｉ（ｔ）と定包絡線変調波Ｓ、ｚ（ｔ）の位相を９
０度だけ遅れさせたものとを合成し、出力信号波Ｓ。（
１）として出力する。The input terminal ■1 and input terminal I2 of the hybrid 23 have
Constant envelope modulated waves S, +(t), s, and □(1) are introduced, respectively. The hybrid 37 changes the phase of the constant envelope modulated wave S, I(t) and the constant envelope modulated wave S, z(t) by 9.
The output signal wave S is synthesized with the signal delayed by 0 degrees. (
Output as 1).
このため、波形生成演算回路３２においては、９０度だ
け位相を進ませた直交変調信号１２（＋９゜。Therefore, in the waveform generation calculation circuit 32, the orthogonal modulation signal 12 whose phase is advanced by 90 degrees (+9 degrees).
（ｔ）、 ＱＺ（。、。）（ｔ）が生成される。変調器
２４により、この直交変調信号１２（４９゜＋（ｔ）
＋ ＱＺ（−９０１−（１）によって搬送波を変調し、
定包絡線変調波Ｓ２３．、。、（ｔ）が得られる。(t), QZ(.,.)(t) are generated. The modulator 24 generates this orthogonal modulation signal 12 (49°+(t)
+ Modulate the carrier wave by QZ(-901-(1),
Constant envelope modulated wave S23. ,. , (t) are obtained.
第６図に、定包絡線変調波Ｓ ｒ （ｔ）と定包絡線変
調波Ｓ Ｚ （＋９０） （ｔ）および出力信号波Ｓ。FIG. 6 shows the constant envelope modulated wave S r (t), the constant envelope modulated wave S Z (+90) (t), and the output signal wave S.
（１）の関係を示す。The relationship (1) is shown below.
図のように、ハイブリッド２３において、定包絡線変調
波Ｓ＋（ｔ）と定包絡線変調波Ｓ２（。ｑｏ）（ｔ）と
を合成することにより、定包絡線変調波５ｔ（ｔ）およ
び５ｚ（ｔ）を合成した場合と同様の出力信号波５ｏ（
ｔ）を得る。As shown in the figure, in the hybrid 23, by combining the constant envelope modulated wave S+(t) and the constant envelope modulated wave S2(.qo)(t), constant envelope modulated waves 5t(t) and 5z The output signal wave 5o(
t) is obtained.
位相比較回路１８は、２系統の直交変調信号Ｉ＋（ｔ）
、 Ｑ＋（ｔ）および１２（＋９゜＋（ｔ） 、 ＱＺ
＋、９゜、（ｔ）に基づいて、位相差の計算値α。が１
８０度のときにトリガパルスＴを出力し、位相誤差検出
回路２１に供給している。The phase comparator circuit 18 receives two systems of orthogonal modulation signals I+(t)
, Q+(t) and 12(+9°+(t) , QZ
Calculated value α of phase difference based on +, 9°, (t). is 1
A trigger pulse T is output when the angle is 80 degrees, and is supplied to the phase error detection circuit 21.
ここで、直交変調信号Ｉｔ（ｔ）、 Ｑ＋（ｔ）および
１２（。、。＋（ｔ） 、 ＱＺ１４９゜、（ｔ）から
求めた位相差の計算値α。が１８０度になる場合は、上
述した第１実施例において、位相差の計算値α。が９０
度になる場合に対応している。Here, if the calculated value α of the phase difference obtained from the orthogonal modulation signals It(t), Q+(t) and 12(., .+(t), QZ149°, (t) becomes 180 degrees, then In the first embodiment described above, the calculated value α of the phase difference is 90.
It corresponds to cases where it becomes a degree.
位相比較回路１９は、上述したような余弦関数的な位相
比較特性を持っているので、ローパスフィルタ２０の出
力は、２系統の定包絡線変調波５ａｔ（ｔ） 、 Ｓ
−２（１）の位相差αが１８０度のとき極小且つ最小と
なるように変化する。このようなローパスフィルタ４０
の出力を、微分回路２４により１８０度のとき０”とな
るように変換して、位相差検出信号５９（１）として、
位相誤差検出回路２１に供給する。Since the phase comparison circuit 19 has a cosine function-like phase comparison characteristic as described above, the output of the low-pass filter 20 is composed of two systems of constant envelope modulated waves 5at(t) and S.
When the phase difference α of -2(1) is 180 degrees, it changes to become the minimum. Such a low pass filter 40
The output of is converted by the differentiating circuit 24 so that it becomes 0'' at 180 degrees, and is used as the phase difference detection signal 59(1).
The signal is supplied to the phase error detection circuit 21.
これにより、上述した第１実施例と同様に、位相誤差検
出回路２１により、位相差検出信号５Ｐ（１）の値に基
づいて位相誤差δが検出される。Thereby, similarly to the first embodiment described above, the phase error detection circuit 21 detects the phase error δ based on the value of the phase difference detection signal 5P(1).
同様にして、この位相誤差δに基づいて、位相誤差制御
回路４２により、直交変調信号１２（。、。。Similarly, based on this phase error δ, the phase error control circuit 42 controls the orthogonal modulation signal 12 (...,...).
（Ｌ） 、 ＱＺ（。、。）（ｔ）に補正が加えられ
る。(L), QZ(.,.)(t) are corrected.
■、実施例のまとめ上述した第１実施例のように、位相比較回路１９・、ロ
ーパスフィルタ２０により、２系統の定包絡線変調波Ｓ
ａ＋（ｔ） 、 Ｓａ□（１）の位相差αに対応した値
を持つ位相差検出信号５ｐ（ｔ）が生成される。(2) Summary of the Embodiment As in the first embodiment described above, the phase comparison circuit 19 and the low-pass filter 20 generate two systems of constant envelope modulated waves S.
A phase difference detection signal 5p(t) having a value corresponding to the phase difference α between a+(t) and Sa□(1) is generated.
また、位相比較回路１８は、位相差の計算値α。Further, the phase comparison circuit 18 calculates the calculated value α of the phase difference.
が９０度のときに、トリガパルス′ｒを発生する。When the angle is 90 degrees, a trigger pulse 'r is generated.
また、第２実施例のように、合成手段としてハイプリン
ト２３を用いた場合は、微分回路２４を付加して構成し
、微分回路２４の出力を位相差検出信号５ｐ（ｔ）とす
る。一方、位相比較回路１８により位相差の計算値α。Further, when the high print 23 is used as the synthesis means as in the second embodiment, a differentiating circuit 24 is added and the output of the differentiating circuit 24 is used as the phase difference detection signal 5p(t). On the other hand, the phase comparison circuit 18 calculates the phase difference α.
が１８０度のときトリガパルスＴを生成する。Trigger pulse T is generated when is 180 degrees.
位相誤差検出回路２１により、トリガパルスＴが発生し
た時点の位相差検出信号５ｐ（ｔ）の値が“０“である
か否かにより、位相誤差δが生じているか否かを判別す
ることが可能となる。また、位相差検出信号５ｐ（ｔ）
の値の符号により、位相誤差δの符号を判別することが
できる。The phase error detection circuit 21 can determine whether a phase error δ has occurred based on whether the value of the phase difference detection signal 5p(t) at the time when the trigger pulse T is generated is "0". It becomes possible. In addition, the phase difference detection signal 5p(t)
The sign of the phase error δ can be determined from the sign of the value of .
位相誤差制御回路２２により、位相誤差δが“０°゛に
なるように直交変調信号１２（ｔ）、 ＱＺ（ｔ） （
あるいはｔｚ＜。９゜＋（ｔ） ＋ ＱＺ（＋９゜１（
ｔ））を補正する。The phase error control circuit 22 controls the quadrature modulation signals 12(t), QZ(t) (
Or tz<. 9゜+(t) + QZ(+9゜1(
t)).
上述のようにして、位相差の計算値α。と２系統の定包
絡線変調波３１１（ｔ） 、 Ｓ、□（１）の位相差
αとが一致するように補正することができる。これによ
り、合成器１７あるいはハイブリッド２３によって合成
された出力信号波５ｏ（ｔ）の波形は、入力信号波Ｓ
ｉ （ｔ）を線形増幅した場合と同様に歪みのない波形
となる。The calculated value α of the phase difference is calculated as described above. The phase difference α between the constant envelope modulated waves 311(t), S, and □(1) of the two systems can be corrected so that they match. As a result, the waveform of the output signal wave 5o(t) synthesized by the synthesizer 17 or the hybrid 23 is the input signal wave S
Similar to the case where i (t) is linearly amplified, a distortion-free waveform is obtained.
ここで、定包絡線変調波を増幅する場合には、飽和領域
においても線形性は保持されるので、増幅器１５．１６
を飽和領域において動作させ、電力効率を高くして増幅
することが可能となる。Here, when amplifying a constant envelope modulated wave, linearity is maintained even in the saturation region, so the amplifier 15.16
It is possible to operate in the saturation region and perform amplification with high power efficiency.
■９発明の変形態様なお、上述した本発明の実施例にあっては、位相差の計
算値α。が９０度（１８０度）のときの位相差検出信号
Ｓ、（ｔ）の値により、位相誤差δの有無および位相誤
差δの符号を判別する場合を考えたが、トリガパルスＴ
を発生させる位相差の値には限られず、位相誤差δを検
出して補正するものであれば適用できる。(9) Modifications of the invention In the embodiment of the invention described above, the calculated value α of the phase difference. We have considered a case where the presence or absence of phase error δ and the sign of phase error δ are determined based on the value of phase difference detection signal S,(t) when T is 90 degrees (180 degrees).
The present invention is not limited to the value of the phase difference that causes .delta., and any value that detects and corrects the phase error .delta.
また、本発明は上述した実施例に限られることはなく、
本発明には各種の変形態様があることは当業者であれば
容易に推考できるであろう。Furthermore, the present invention is not limited to the above-mentioned embodiments,
Those skilled in the art will easily guess that there are various modifications to the present invention.
（発明の効果〕上述したように、本発明によれば、包絡線変動を有する
信号波を２系統の定包絡線変調波に分解し、それぞれの
定包絡線変調波の伝送路の電気長の差によって生じた位
相誤差を補正した後に合成することにより、包路線変動
を有する信号波を線形性を保持し、かつ、高い電力効率
によって増幅することができる。(Effects of the Invention) As described above, according to the present invention, a signal wave having envelope fluctuation is decomposed into two systems of constant envelope modulated waves, and the electrical length of the transmission path of each constant envelope modulated wave is By combining the signals after correcting the phase error caused by the difference, it is possible to maintain the linearity of a signal wave having an envelope fluctuation and amplify it with high power efficiency.
第１図は本発明による増幅装置の構成図、第２図は本発
明の第１実施例による増幅装置の構成図、第３図は本発明の第２実施例による増幅装置の構成図、第４図は直交変調信号の説明図、第５図は増幅後の定包絡線変調波の説明図、第６図は定
包絡線変調波と合成波の関係の説明図、第７図は増幅装
置の構成図である。図において、は直列並列変換回路１．７２は波形生成用演算回路１．１４，７３．７４は直交変調器、１６．７５．７６は増幅器１．７７は合成器２．１９は位相比較回路、はローパスフィルタ、は位相誤差検出回路、は位相誤差制御回路、はハイブリッド、は微分回路、は終端回路、は直交検波器である。第図第図1 is a block diagram of an amplifier according to the present invention, FIG. 2 is a block diagram of an amplifier according to a first embodiment of the present invention, FIG. 3 is a block diagram of an amplifier according to a second embodiment of the present invention, Figure 4 is an explanatory diagram of the orthogonal modulation signal, Figure 5 is an explanatory diagram of the constant envelope modulated wave after amplification, Figure 6 is an explanatory diagram of the relationship between the constant envelope modulated wave and the composite wave, and Figure 7 is the amplification device. FIG. In the figure, is a serial-to-parallel conversion circuit 1. 72 is a waveform generation arithmetic circuit 1. 14, 73.74 are quadrature modulators, 16.75.76 are amplifiers 1. 77 is synthesizer 2. 19 is a phase comparison circuit, is a low-pass filter, is a phase error detection circuit, is a phase error control circuit, is a hybrid, is a differentiation circuit, is a termination circuit, and is a quadrature detector. Figure Figure
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|---|---|---|---|
| JP63239963AJPH0793546B2 (en) | 1988-09-26 | 1988-09-26 | Amplifier |
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP63239963AJPH0793546B2 (en) | 1988-09-26 | 1988-09-26 | Amplifier |
| Publication Number | Publication Date |
|---|---|
| JPH0287708Atrue JPH0287708A (en) | 1990-03-28 |
| JPH0793546B2 JPH0793546B2 (en) | 1995-10-09 |
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP63239963AExpired - Fee RelatedJPH0793546B2 (en) | 1988-09-26 | 1988-09-26 | Amplifier |
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