【０００１】[0001]
【発明の属する技術分野】本発明は、高周波電力の非接
触給電装置及び非接触給電方法に関し、特に、高速コン
ピュータ断層撮像装置（以下、高速CT装置という。）や
高荷役クレーン、又は電気自動車を利用した新交通シス
テムなどに広く適用される高周波電力の非接触給電装置
及び非接触給電方法に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a non-contact power supply apparatus and a non-contact power supply method for high-frequency power, and more particularly, to a high-speed computer tomography apparatus (hereinafter, referred to as a high-speed CT apparatus), a high-loading crane, or an electric vehicle. The present invention relates to a non-contact power supply device and a non-contact power supply method for high-frequency power widely applied to new transportation systems and the like.
【０００２】[0002]
【従来の技術】高速ＣＴ装置では、脳や内臓の断面を撮
像するため、Ｘ線等を放射する撮像部が撮影対象の周囲
を移動する。また、高荷役クレーンでは、コンテナ等の
上げ下ろしを行うため、コンテナ等を吊り上げるモータ
部がレールの上を移動する。このような高速ＣＴ装置及
び高荷役クレーンでは、撮像部やモータ部等の移動体
に、パンタグラフや、給電ケーブルを支持線で吊り下げ
て移動可能にしたいわゆるカーテン状ケーブルによって
駆動電力が供給される。2. Description of the Related Art In a high-speed CT apparatus, an imaging unit that emits X-rays or the like moves around an object to be imaged in order to image a cross section of the brain or internal organs. In a high-loading crane, a motor unit for lifting a container or the like moves on rails in order to raise or lower a container or the like. In such a high-speed CT apparatus and a high loading / unloading crane, driving power is supplied to a moving body such as an imaging unit and a motor unit by a pantograph or a so-called curtain-shaped cable that is movable by suspending a power supply cable with a support wire. .
【０００３】しかしながら、パンタグラフを用いた給電
方法では、移動体の移動に伴い接触部が磨耗するため、
定期的なメンテナンスが必要となったり、磨耗粉が周囲
に付着して絶縁性能を低下させる欠点がある。However, in a power supply method using a pantograph, a contact portion is worn due to movement of a moving body.
There are drawbacks that regular maintenance is required and that the abrasion powder adheres to the surroundings and lowers insulation performance.
【０００４】また、カーテン状ケーブルを用いた給電方
法では、移動体の移動に伴いケーブルも同時に移動する
ため、ケーブルの長さによって移動範囲が制限された
り、ケーブルの重量によって移動速度が低下する欠点が
ある。特に、高速ＣＴ装置では、撮像部が撮影対象の周
囲で回転運動を行うため、撮像部の移動形態に制限を加
えてケーブルの混線を防止する必要がある。[0004] In the power supply method using a curtain-shaped cable, the cable moves at the same time as the moving body moves, so that the moving range is limited by the length of the cable, and the moving speed is reduced by the weight of the cable. There is. In particular, in the high-speed CT apparatus, since the imaging unit performs a rotating motion around the imaging target, it is necessary to prevent the cross-connection of the cable by restricting the movement form of the imaging unit.
【０００５】そこで、移動体に給電線を接触させて駆動
電力を供給する上記の不具合を解消するため、移動体に
非接触で駆動電力を供給する非接触給電装置が使用され
る。[0005] In order to solve the above-mentioned problem of supplying driving power by bringing a power supply line into contact with a moving body, a non-contact power supply device for supplying driving power to the moving body in a non-contact manner is used.
【０００６】従来の非接触給電装置の構成例を図８、図
９に示す。これらの非接触給電装置は、固定設備である
給電側回路１５（１次側）に流れる交流によって生ずる
磁束を、移動体に設けられる受電側回路１６（２次側）
に鎖交させ、受電側回路１６に誘導起電力を生じさせて
移動体のモータ等に電力を供給するものである。FIGS. 8 and 9 show examples of the configuration of a conventional contactless power supply device. These non-contact power supply devices transmit a magnetic flux generated by an alternating current flowing through a power supply side circuit 15 (primary side) which is a fixed facility to a power receiving side circuit 16 (secondary side) provided on a moving body.
To generate an induced electromotive force in the power receiving side circuit 16 to supply power to a motor or the like of the moving body.
【０００７】図８に示す従来の非接触給電装置は、固定
設備である給電側回路１５と、移動体に設けられる受電
側回路１６とで構成され、給電側回路１５は、商用周波
数の交流電源部１と、交流電源部１から給電される交流
電力を直流電力に変換する直流電源部２と、直流電源部
２から給電される直流電力を周波数1〜50ｋＨｚ程度の
高周波電力に逆変換する電流型インバータ部５ａと、電
流型インバータ部５ａから出力される高周波電力を絶縁
するトランス４と、トランス４で絶縁された高周波電力
を受電側回路１６に非接触で供給する１次導線３と、１
次導線３と並列に設けられて給電側の共振回路を構成す
る１次コンデンサ６ａとを有する。The conventional non-contact power supply device shown in FIG. 8 is composed of a power supply side circuit 15 which is a fixed facility and a power receiving side circuit 16 provided on a moving body. Unit 1, a DC power supply unit 2 for converting AC power supplied from the AC power supply unit 1 to DC power, and a current for inversely converting DC power supplied from the DC power supply unit 2 to high-frequency power having a frequency of about 1 to 50 kHz. Type inverter unit 5a, a transformer 4 for insulating high-frequency power output from the current-type inverter unit 5a, a primary conductor 3 for supplying high-frequency power insulated by the transformer 4 to a power receiving side circuit 16 in a non-contact manner,
A primary capacitor 6a provided in parallel with the secondary conductor 3 and constituting a resonance circuit on the power supply side.
【０００８】一方、移動体に設けられる受電側回路１６
は、給電側回路１５の１次導線３から電磁誘導作用によ
り非接触状態で高周波電力を受電する受電コイル８と、
受電コイル８に並列に設けられて受電側の共振回路を構
成する２次コンデンサ９と、受電コイル８で受電した高
周波電力を整流する整流部７と、整流部７から出力され
る直流電力を直流変換または周波数変換する２次電源部
１０と、２次電源部１０からの電力供給により動作する
移動体走行用のモータ等の負荷１１とを有する。On the other hand, the power receiving side circuit 16 provided in the moving body
A power receiving coil 8 for receiving high-frequency power from the primary conductor 3 of the power supply side circuit 15 in a non-contact state by electromagnetic induction,
A secondary capacitor 9 provided in parallel with the power receiving coil 8 to form a power receiving side resonance circuit; a rectifying unit 7 for rectifying high frequency power received by the power receiving coil 8; The secondary power supply unit 10 includes a secondary power supply unit 10 that performs conversion or frequency conversion, and a load 11 such as a motor for moving a moving body that operates by power supply from the secondary power supply unit 10.
【０００９】このような非接触給電装置では、受電側の
共振回路を構成する２次コンデンサ９が、受電コイル８
及び負荷１１のインダクタンス成分と所定の共振周波数
で共振するように設定される。また、給電側の共振回路
を構成する１次コンデンサ６ａが、１次導線３及び１次
側から見た負荷１１を含む２次側のインダクタンス成分
と、受電側と同じ共振周波数で共振するように設定さ
れ、給電側の電力が効率的に負荷１１へ供給される。In such a non-contact power feeding device, the secondary capacitor 9 constituting the power receiving side resonance circuit is connected to the power receiving coil 8.
The resonance frequency is set so as to resonate with the inductance component of the load 11 at a predetermined resonance frequency. Also, the primary capacitor 6a constituting the resonance circuit on the power supply side resonates with the secondary wire inductance component including the primary conductor 3 and the load 11 viewed from the primary side at the same resonance frequency as the power receiving side. Then, the power on the power supply side is efficiently supplied to the load 11.
【００１０】図９は、従来の非接触給電装置の他の構成
例である。この非接触給電装置では、図８の非接触給電
装置と異なり、電圧型インバータ５ｂにより高周波電力
が生成され、１次コンデンサ６ｂが１次導線３と直列に
接続される。この非接触給電装置においても、給電側と
受電側の共振回路が同じ共振周波数で共振するように構
成され、給電側の電力が効率的に負荷１１へ供給され
る。FIG. 9 shows another configuration example of a conventional non-contact power feeding device. In this non-contact power supply device, unlike the non-contact power supply device of FIG. 8, high-frequency power is generated by the voltage-type inverter 5b, and the primary capacitor 6b is connected in series with the primary conductor 3. Also in this non-contact power supply device, the power supply side and the power receiving side resonance circuits are configured to resonate at the same resonance frequency, and the power supply side power is efficiently supplied to the load 11.
【００１１】図１０は、このような非接触給電装置にお
ける１次導線３と受電コイル８の概略構成図である。図
１０に示すように、１次導線３は、例えば、移動体の移
動範囲に沿ってレール状に敷設され、受電コイル８は、
１次導線３に対して移動可能なＥ型のフェライトコア２
１に、１次導線３が誘起する磁束２２と鎖交するように
巻き付けられる。この場合、受電コイル８及びフェライ
トコア２１を内蔵する移動体は、１次導線３から非接触
で高周波電力を受電し、モータ２３及び車輪２４を駆動
して１次導線３に沿って走行する。FIG. 10 is a schematic configuration diagram of the primary conductor 3 and the power receiving coil 8 in such a non-contact power feeding device. As shown in FIG. 10, for example, the primary conductor 3 is laid in a rail shape along the moving range of the moving body, and the power receiving coil 8 is
E-type ferrite core 2 movable with respect to primary conductor 3
1 is wound so as to link with the magnetic flux 22 induced by the primary conductor 3. In this case, the moving body including the power receiving coil 8 and the ferrite core 21 receives the high-frequency power from the primary conductor 3 in a non-contact manner, and drives the motor 23 and the wheels 24 to travel along the primary conductor 3.
【００１２】[0012]
【発明が解決しようとする課題】このように従来の非接
触給電装置では、負荷１１への給電が効率的に行われる
ように、受電側の２次コンデンサ９が、受電コイル８及
び負荷１１のインダクタンス成分と所定の共振周波数で
共振するように設定され、給電側の１次コンデンサ６ａ
又は６ｂが、１次導線３及び１次側から見た負荷１１を
含む２次側のインダクタンス成分と同じ共振周波数で共
振するように設定される。As described above, in the conventional non-contact power supply device, the secondary capacitor 9 on the power receiving side is connected to the power receiving coil 8 and the load 11 so that the power supply to the load 11 is performed efficiently. The primary capacitor 6a is set to resonate with the inductance component at a predetermined resonance frequency, and
Or, 6b is set so as to resonate at the same resonance frequency as the inductance component on the secondary side including the primary conductor 3 and the load 11 viewed from the primary side.
【００１３】一方、モータなどの回転機負荷は、起動時
にすべりが大きくなり、定格よりも大きな電力が必要に
なる。また、高荷役クレーン等のモータでは、荷物重量
により吊り上げ負荷が変化する。このため、負荷１１の
等価的な抵抗成分は駆動に伴って大きく変動する。On the other hand, a rotating machine load such as a motor has a large slip at the time of startup, and requires a power larger than a rated power. Further, in a motor such as a heavy cargo handling crane, the lifting load changes depending on the load weight. For this reason, the equivalent resistance component of the load 11 fluctuates greatly with driving.
【００１４】しかしながら、従来の非接触給電装置で
は、給電側の１次コンデンサ6ａ、６ｂ及び受電側の２
次コンデンサ９の容量値を固定しているため、負荷１１
の等価的な抵抗成分が変化した場合に、給電側及び受電
側の共振回路の共振周波数が変化してしまい、給電側及
び受電側の共振回路の共振周波数と電流型インバータ部
５ａ又は電圧型インバータ部５ｂの駆動周波数のずれが
大きくなる。However, in the conventional non-contact power supply device, the primary capacitors 6a and 6b on the power supply side and the two
Since the capacitance value of the secondary capacitor 9 is fixed, the load 11
When the equivalent resistance component changes, the resonance frequencies of the resonance circuits on the power supply side and the power reception side change, and the resonance frequency of the resonance circuit on the power supply side and the power reception side and the current-type inverter unit 5a or the voltage-type inverter. The deviation of the driving frequency of the portion 5b increases.
【００１５】このため、電流型インバータ部５ａ又は電
圧型インバータ部５ｂから供給する電力の力率が「１」
から大きくずれ、供給する皮相電力（電圧×電流）に対
して負荷１１で消費される電力の効率が低下し、効率的
な電力伝送を行うことが困難になる。Therefore, the power factor of the electric power supplied from the current-type inverter unit 5a or the voltage-type inverter unit 5b is "1".
, The efficiency of the power consumed by the load 11 with respect to the apparent power (voltage × current) supplied decreases, and it becomes difficult to perform efficient power transmission.
【００１６】そこで、本発明の目的は、負荷の等価的な
抵抗成分が変化しても、電流型インバータ部又は電圧型
インバータ部から供給する電力の力率を維持し、効率的
な電力伝送を行うことができる非接触給電装置及び非接
触給電方法を提供することにある。Therefore, an object of the present invention is to maintain a power factor of power supplied from a current-type inverter unit or a voltage-type inverter unit even if an equivalent resistance component of a load changes, thereby achieving efficient power transmission. An object of the present invention is to provide a non-contact power supply device and a non-contact power supply method that can be performed.
【００１７】[0017]
【課題を解決するための手段】上記の目的を達成するた
めに、本発明の一つの側面は、高周波電力を非接触で負
荷に供給する非接触給電装置において、高周波電力を生
成する高周波電源部と、高周波電源部が生成した高周波
電力を高周波磁束に変換する１次導線と、１次導線が変
換した高周波磁束と鎖交して誘導起電力を生成し、誘導
起電力を負荷に供給する受電コイルと、負荷の抵抗成分
を検出する抵抗検出回路と、抵抗検出回路が検出した負
荷の抵抗成分に応じて、高周波電源部が生成する高周波
電力の周波数を制御する周波数制御部とを有することを
特徴とする。In order to achieve the above object, one aspect of the present invention is a high-frequency power supply for generating high-frequency power in a non-contact power supply apparatus for supplying high-frequency power to a load in a non-contact manner. And a primary conductor for converting high-frequency power generated by the high-frequency power supply unit into high-frequency magnetic flux, and a power receiving unit for generating induced electromotive force by interlinking with the high-frequency magnetic flux converted by the primary conductor and supplying the induced electromotive force to the load. A coil, a resistance detection circuit that detects a resistance component of the load, and a frequency control unit that controls a frequency of high-frequency power generated by the high-frequency power supply unit according to the resistance component of the load detected by the resistance detection circuit. Features.
【００１８】本発明によれば、抵抗検出回路が検出した
負荷の抵抗成分に応じて、高周波電源部が生成する高周
波電力の周波数を制御するので、高周波電源部から出力
される高周波電力の力率をほぼ「１」近くにすることが
できる。従って、高周波電源部が供給する皮相電力（電
圧×電流）に対して負荷で消費される電力の効率が高く
なり、効率的な電力伝送を行うことができる。According to the present invention, since the frequency of the high-frequency power generated by the high-frequency power supply is controlled in accordance with the resistance component of the load detected by the resistance detection circuit, the power factor of the high-frequency power output from the high-frequency power supply is controlled. Can be made substantially close to “1”. Accordingly, the efficiency of the power consumed by the load with respect to the apparent power (voltage × current) supplied by the high-frequency power supply unit increases, and efficient power transmission can be performed.
【００１９】また、上記の発明における好ましい態様と
して、高周波電源部は、スイッチング素子で構成される
高周波インバータと、周波数制御部から出力される信号
に応答して、スイッチング素子の導通のタイミングを制
御するタイミング制御回路とを有することを特徴とす
る。In a preferred aspect of the present invention, the high-frequency power supply unit controls the conduction timing of the switching element in response to a high-frequency inverter including a switching element and a signal output from the frequency control unit. And a timing control circuit.
【００２０】更に、高周波電源部は、１次導線と共に共
振回路を構成する１次コンデンサを有し、高周波インバ
ータは、駆動周波数が共振回路の共振周波数になるよう
に制御されることを特徴とする。Further, the high-frequency power supply section has a primary capacitor that forms a resonance circuit together with the primary conductor, and the high-frequency inverter is controlled so that the driving frequency becomes the resonance frequency of the resonance circuit. .
【００２１】本発明によれば、高周波インバータの駆動
周波数が共振回路の共振周波数になるように制御される
ので、高周波電源部から負荷側を見たインピーダンスが
ほぼ純抵抗成分になる。従って、高周波電源部から負荷
側に供給する電力の力率をほぼ「１」近くにして効率的
な電力伝送を行うことができる。According to the present invention, since the driving frequency of the high-frequency inverter is controlled to be the resonance frequency of the resonance circuit, the impedance when the load side is viewed from the high-frequency power supply becomes substantially a pure resistance component. Therefore, the power factor of the power supplied from the high-frequency power supply unit to the load side can be made substantially close to “1”, and efficient power transmission can be performed.
【００２２】また、上記の発明における好ましい態様と
して、高周波電源部は、スイッチング素子で構成される
高周波インバータと、周波数制御部から出力される信号
に応答してインダクタンス値が制御される可飽和インダ
クタとを有することを特徴とする。In a preferred aspect of the present invention, the high-frequency power supply includes a high-frequency inverter including a switching element and a saturable inductor whose inductance is controlled in response to a signal output from the frequency controller. It is characterized by having.
【００２３】更に、高周波電源部は、１次導線及び可飽
和インダクタと共に共振回路を構成する１次コンデンサ
を有し、可飽和インダクタは、共振回路の共振周波数が
高周波インバータの駆動周波数になるように制御される
ことを特徴とする。Further, the high-frequency power supply section has a primary capacitor which forms a resonance circuit together with the primary conductor and the saturable inductor, and the saturable inductor has a resonance frequency of the resonance circuit equal to a driving frequency of the high-frequency inverter. It is characterized by being controlled.
【００２４】本発明によれば、可飽和インダクタは、共
振回路の共振周波数が高周波インバータの駆動周波数に
なるように制御されるので、高周波電源部から負荷側を
見たインピーダンスがほぼ純抵抗成分になる。従って、
高周波電源部から負荷側に供給する電力の力率をほぼ
「１」近くにして効率的な電力伝送を行うことができ
る。According to the present invention, the saturable inductor is controlled so that the resonance frequency of the resonance circuit becomes equal to the drive frequency of the high-frequency inverter. Become. Therefore,
By setting the power factor of the power supplied from the high-frequency power supply unit to the load side to approximately "1", efficient power transmission can be performed.
【００２５】また、上記の発明における好ましい態様と
して、高周波電源部は、スイッチング素子で構成される
高周波インバータと、周波数制御部から出力される信号
に応答して容量値が制御される可変キャパシタとを有す
ることを特徴とする。In a preferred aspect of the present invention, the high-frequency power supply includes a high-frequency inverter including a switching element and a variable capacitor whose capacitance is controlled in response to a signal output from the frequency controller. It is characterized by having.
【００２６】更に、高周波電源部は、１次導線及び可変
キャパシタと共に共振回路を構成する１次コンデンサを
有し、可変キャパシタは、共振回路の共振周波数が高周
波インバータの駆動周波数になるように制御されること
を特徴とする。Further, the high-frequency power supply has a primary capacitor constituting a resonance circuit together with the primary conductor and the variable capacitor, and the variable capacitor is controlled such that the resonance frequency of the resonance circuit becomes the driving frequency of the high-frequency inverter. It is characterized by that.
【００２７】本発明によれば、可変キャパシタは、共振
回路の共振周波数が高周波インバータの駆動周波数にな
るように制御されるので、高周波電源部から負荷側を見
たインピーダンスがほぼ純抵抗成分になる。従って、高
周波電源部から負荷側に供給する電力の力率をほぼ
「１」近くにして効率的な電力伝送を行うことができ
る。According to the present invention, since the variable capacitor is controlled such that the resonance frequency of the resonance circuit becomes equal to the drive frequency of the high-frequency inverter, the impedance seen from the high-frequency power supply to the load side becomes substantially a pure resistance component. . Therefore, the power factor of the power supplied from the high-frequency power supply unit to the load side can be made substantially close to “1”, and efficient power transmission can be performed.
【００２８】[0028]
【発明の実施の形態】以下、図面を参照して本発明の実
施の形態例を説明する。しかしながら、かかる実施の形
態例が、本発明の技術的範囲を限定するものではない。Embodiments of the present invention will be described below with reference to the drawings. However, such embodiments do not limit the technical scope of the present invention.
【００２９】図１は、本発明の実施の形態の非接触給電
装置の構成図である。本実施の形態の非接触給電装置
は、固定設備である給電側回路１５（１次側）と、移動
体に設けられる受電側回路１６（２次側）とで構成さ
れ、給電側回路１５は、商用周波数の交流電源部１と、
交流電源部１から給電される交流電力を直流電力に変換
する直流電源部２と、直流電源部２から出力される直流
電力を周波数1〜50ｋＨｚ程度の高周波電力に逆変換す
る電流型インバータ部５ａと、電流型インバータ部５ａ
から出力される高周波電力を絶縁するトランス４と、ト
ランス４で絶縁された高周波電力を受電側回路１６に非
接触で供給する１次導線３と、１次導線３と並列に設け
られて給電側の共振回路を構成する１次コンデンサ６ａ
とを有する。FIG. 1 is a configuration diagram of a contactless power supply device according to an embodiment of the present invention. The contactless power supply device according to the present embodiment includes a power supply side circuit 15 (primary side) which is a fixed facility and a power reception side circuit 16 (secondary side) provided in a moving body. , A commercial frequency AC power supply unit 1,
DC power supply unit 2 for converting AC power supplied from AC power supply unit 1 to DC power, and current-type inverter unit 5a for inversely converting DC power output from DC power supply unit 2 to high-frequency power having a frequency of about 1 to 50 kHz. And the current type inverter section 5a
4 that insulates the high-frequency power output from the power supply, the primary conductor 3 that supplies the high-frequency power insulated by the transformer 4 to the power receiving side circuit 16 in a non-contact manner, and the power supply side that is provided in parallel with the primary conductor 3. Primary capacitor 6a constituting the resonance circuit of FIG.
And
【００３０】また、給電側回路１５には、負荷１１の等
価的な抵抗成分の変化に応じて電流型インバータ部５ａ
の駆動周波数を変化させる周波数コントローラ１３と、
周波数コントローラ１３からの信号により電流型インバ
ータ部５ａの導通のタイミングを制御する周波数制御装
置１２とを有する。The power supply side circuit 15 includes a current type inverter 5a in accordance with a change in an equivalent resistance component of the load 11.
A frequency controller 13 for changing the driving frequency of
And a frequency control device 12 that controls the timing of conduction of the current-type inverter unit 5a by a signal from the frequency controller 13.
【００３１】電流型インバータ部５ａは、ブリッジ接続
されたサイリスタ又はＧＴＯ（ゲート・ターンオフ・サ
イリスタ）等のスイッチング素子により構成され、周波
数制御装置１２から出力されるゲート信号のタイミング
でスイッチング素子が制御され、ゲート信号のタイミン
グに対応した周波数の高周波電力を出力する。The current type inverter section 5a is composed of a switching element such as a thyristor or a GTO (gate turn-off thyristor) connected in a bridge, and the switching element is controlled at the timing of a gate signal output from the frequency control device 12. And outputs high-frequency power having a frequency corresponding to the timing of the gate signal.
【００３２】一方、受電側回路１６は、給電側回路１５
の１次導線３から電磁誘導作用により非接触状態で高周
波電力を受電する受電コイル８と、受電コイル８に並列
に設けられて受電側の共振回路を構成する２次コンデン
サ９と、負荷１１の等価的な抵抗成分を検出する抵抗検
出回路１４と、受電コイル８で受電した高周波電力を整
流する整流部７と、整流部７から出力される直流電力を
直流変換または周波数変換する２次電源部１０と、２次
電源部１０からの電力供給により動作する移動体走行用
のモータ等の負荷１１とを有する。On the other hand, the power receiving side circuit 16 is
A power receiving coil 8 for receiving high-frequency power in a non-contact state from the primary conductor 3 by electromagnetic induction, a secondary capacitor 9 provided in parallel with the power receiving coil 8 to form a power receiving side resonance circuit, and a load 11. A resistance detection circuit 14 for detecting an equivalent resistance component, a rectification unit 7 for rectifying high-frequency power received by the power receiving coil 8, and a secondary power supply unit for DC-converting or frequency-converting DC power output from the rectification unit 7. And a load 11 such as a motor for moving a mobile object that operates by power supply from the secondary power supply unit 10.
【００３３】抵抗検出回路１４は、具体的には、受電コ
イル８及び２次コンデンサ９に並列に接続される負荷電
圧計及び直列に接続される負荷電流計、又はインピーダ
ンス・メータなどにより、抵抗検出回路１４から負荷側
を見たインピーダンスを求め、そのインピーダンスから
整流部７及び２次電源部１０の抵抗成分を差し引いて負
荷１１の等価的な抵抗成分を求める。そして、負荷１１
の等価的な抵抗成分を、無線通信等により非接触で給電
側回路１５の周波数コントローラ１３に送信する。Specifically, the resistance detection circuit 14 detects the resistance using a load voltmeter connected in parallel to the power receiving coil 8 and the secondary capacitor 9 and a load ammeter connected in series, or an impedance meter. The impedance seen from the load side is obtained from the circuit 14, and the resistance components of the rectifier 7 and the secondary power supply 10 are subtracted from the impedance to obtain an equivalent resistance component of the load 11. And the load 11
Is transmitted to the frequency controller 13 of the power supply side circuit 15 in a non-contact manner by wireless communication or the like.
【００３４】このように本実施の形態の非接触給電装置
では、抵抗検出回路１４により負荷１１の等価的な抵抗
成分を検出し、検出した抵抗成分の情報を周波数コント
ローラ１３に送り、周波数制御装置１２は、周波数コン
トローラ１３からの指令信号により、電流型インバータ
部５ａから負荷側を見たインピーダンスがほぼ純抵抗成
分になるように、電流型インバータ部５ａの駆動周波数
を制御する。As described above, in the contactless power supply device of the present embodiment, the equivalent resistance component of the load 11 is detected by the resistance detection circuit 14, and information on the detected resistance component is sent to the frequency controller 13. Reference numeral 12 controls the drive frequency of the current-type inverter unit 5a in accordance with a command signal from the frequency controller 13 such that the impedance when the load is viewed from the current-type inverter unit 5a is substantially a pure resistance component.
【００３５】このため、電流型インバータ部５ａから負
荷側に供給する電力の力率をほぼ「１」近くに制御する
ことができ、供給する皮相電力（電圧×電流）に対して
負荷１１で消費される電力の効率をほぼ１００％近くに
して、効率的な電力伝送を行うことができる。For this reason, the power factor of the electric power supplied from the current-type inverter unit 5a to the load side can be controlled to approximately "1", and the apparent power (voltage × current) supplied to the load 11 is consumed. Power efficiency can be made nearly 100%, and efficient power transmission can be performed.
【００３６】図２は、本発明の実施の形態の非接触給電
装置の他の構成例である。この非接触給電装置では、図
１の非接触給電装置と異なり、電圧型インバータ部５ｂ
により高周波電力が生成され、給電側回路１５の１次コ
ンデンサ６ｂが１次導線３と直列に接続される。FIG. 2 shows another configuration example of the non-contact power supply device according to the embodiment of the present invention. This contactless power supply device differs from the contactless power supply device of FIG.
As a result, high-frequency power is generated, and the primary capacitor 6 b of the power supply side circuit 15 is connected in series with the primary conductor 3.
【００３７】本実施の形態の非接触給電装置において
も、負荷１１の等価的な抵抗成分に応じて電圧型インバ
ータ部５ｂの駆動周波数を制御することにより、電圧型
インバータ部５ｂから負荷側に供給する電力の力率をほ
ぼ「１」近くに制御することができ、効率的な電力伝送
を行うことができる。Also in the contactless power supply device of the present embodiment, the driving frequency of the voltage type inverter unit 5b is controlled according to the equivalent resistance component of the load 11, so that the voltage type inverter unit 5b supplies the load to the load. The power factor of the power to be transmitted can be controlled to be almost "1", and efficient power transmission can be performed.
【００３８】次に、本発明の実施の形態の非接触給電装
置において、負荷１１の抵抗成分ＲＬが変化した場合の
力率位相θ及び駆動周波数ｆｒの変化の様子を、従来例
と比較しながら説明する。Next, in the contactless power supply device according to the embodiment of the present invention, the change of the power factor phase θ and the drive frequency fr when the resistance component RL of the load 11 changes will be compared with the conventional example. explain.
【００３９】図３は、図１及び図８に示した非接触給電
装置の等価回路である。この等価回路では、図１及び図
８の電流型インバータ部５ａの出力電圧をＶ５、電流型
インバータ部５ａの出力抵抗をＲ０、１次導線３のイン
ダクタンス成分をＬax及びＬline、受電コイル８の抵抗
成分をＲ１、受電コイル８の１次側漏れインダクタンス
をＬ１、受電コイル８の１次／２次結合インダクタンス
をＬＭ、受電コイル８の２次側漏れインダクタンスをＬ
２、受電コイル８の２次コイル及び整流部７並びに２次
電源部１０の抵抗成分をＲ２、負荷１１の抵抗成分をＲ
Ｌとする。FIG. 3 is an equivalent circuit of the non-contact power supply device shown in FIGS. In this equivalent circuit, the output voltage of the current-type inverter 5a in FIGS. 1 and 8 is V5, the output resistance of the current-type inverter 5a is R0, the inductance components of the primary conductor 3 are Lax and Lline, the resistance of the receiving coil 8 is The component is R1, the primary leakage inductance of the receiving coil 8 is L1, the primary / secondary coupling inductance of the receiving coil 8 is LM, and the secondary leakage inductance of the receiving coil 8 is L.
2. The resistance component of the secondary coil and the rectification unit 7 of the receiving coil 8 and the secondary power supply unit 10 is R2, and the resistance component of the load 11 is R2.
L.
【００４０】図３に示す等価回路において、従来のよう
に、電流型インバータ部５ａの駆動周波数ｆｒを、例え
ば、２６ｋＨｚに固定して運転動作をさせて負荷抵抗Ｒ
Ｌを変化させた場合に、電流型インバータ部５ａから負
荷側を見た力率位相θ（deg）の変化の様子を図４に示
す。In the equivalent circuit shown in FIG. 3, the driving frequency fr of the current-type inverter unit 5a is fixed to, for example, 26 kHz, and the load resistance R
FIG. 4 shows how the power factor phase θ (deg) changes when the load side is viewed from the current-type inverter section 5a when L is changed.
【００４１】即ち、図４は、電流型インバータ部５ａの
駆動周波数ｆｒを２６ｋＨｚに固定し、負荷抵抗ＲＬが
１Ωから１０００Ωまで変化した場合に、電流型インバ
ータ部５ａから負荷側を見た力率位相θが、０〜約７０
degと大きく変化していることを示す。That is, FIG. 4 shows a case where the drive frequency fr of the current-type inverter 5a is fixed at 26 kHz and the power factor when the load side is viewed from the current-type inverter 5a when the load resistance RL changes from 1Ω to 1000Ω. Phase θ is 0 to about 70
It shows that it changes greatly with deg.
【００４２】このように、電流型インバータ部５ａの駆
動周波数ｆｒを固定している場合は、負荷の等価的な抵
抗成分が変化した場合に、電流型インバータ部５ａから
負荷側を見た力率位相θが大きく変動するため、電流型
インバータ部５ａでは、負荷での消費電力に対して、最
大１／cos(70deg)＝2.9倍の皮相電力が必要となる。As described above, when the driving frequency fr of the current-type inverter unit 5a is fixed, when the equivalent resistance component of the load changes, the power factor as viewed from the current-type inverter unit 5a to the load side is changed. Since the phase θ fluctuates greatly, the current-type inverter unit 5a needs apparent power that is at most 1 / cos (70 deg) = 2.9 times the power consumption at the load.
【００４３】一方、本実施の形態の非接触給電装置にお
いて、負荷の等価的な抵抗成分を検出し、電流型インバ
ータ部５ａの駆動周波数ｆｒを制御した場合に、負荷の
変動に対応する電流型インバータ部５ａから負荷側を見
た力率位相θ（deg）の変化の様子を図５に示す。On the other hand, in the non-contact power supply device of the present embodiment, when the equivalent resistance component of the load is detected and the driving frequency fr of the current type inverter unit 5a is controlled, the current type corresponding to the load variation is controlled. FIG. 5 shows how the power factor phase θ (deg) changes when the load side is viewed from the inverter unit 5a.
【００４４】即ち、図５は、負荷抵抗ＲＬが１Ωから１
０００Ωまで変化した場合に、電流型インバータ部５ａ
の駆動周波数ｆｒを図示のように変化させると、電流型
インバータ部５ａから負荷側を見た力率位相θの変動が
約2deg以内に抑えられることを示す。That is, FIG. 5 shows that the load resistance RL is changed from 1Ω to 1Ω.
000Ω, the current-type inverter 5a
When the driving frequency fr is changed as shown in the figure, it is shown that the fluctuation of the power factor phase θ when the load side is viewed from the current-type inverter unit 5a can be suppressed within about 2 deg.
【００４５】従って、負荷の等価的な抵抗成分を検出
し、電流型インバータ部５ａの駆動周波数ｆｒを制御し
た場合には、負荷抵抗の変動に対して力率位相θの変動
が約2deg以内となり、電流型インバータ部５ａに負荷で
の消費電力とほぼ同等の皮相電力を供給すればよい。Therefore, when the equivalent resistance component of the load is detected and the driving frequency fr of the current-type inverter unit 5a is controlled, the variation of the power factor phase θ is within about 2 deg with respect to the variation of the load resistance. It is sufficient to supply apparent current approximately equal to the power consumed by the load to the current-type inverter unit 5a.
【００４６】このように本実施の形態の非接触給電装置
では、電流型インバータ部５ａから負荷側を見たインピ
ーダンスがほぼ純抵抗成分になるように、電流型インバ
ータ部５ａの駆動周波数を制御するので、電流型インバ
ータ部５ａから負荷側に供給する電力の力率をほぼ
「１」近くにすることができる。従って、供給する皮相
電力（電圧×電流）に対して負荷１１で消費される電力
の効率をほぼ１００％近くにして、効率的な電力伝送を
行うことができる。As described above, in the contactless power supply device of the present embodiment, the drive frequency of the current-type inverter unit 5a is controlled so that the impedance seen from the current-type inverter unit 5a to the load side becomes substantially a pure resistance component. Therefore, the power factor of the electric power supplied from the current-type inverter unit 5a to the load side can be made substantially close to "1". Therefore, the efficiency of the power consumed by the load 11 with respect to the apparent power (voltage × current) to be supplied can be made nearly 100%, and efficient power transmission can be performed.
【００４７】次に、本発明の実施の形態の非接触給電装
置の他の構成例を図６に示す。この非接触給電装置は、
図１とほぼ同様の構成であるが、１次導線３と直列に可
飽和インダクタ１５を設け、可飽和インダクタ１５のイ
ンダクタンス値を、抵抗検出回路１４が検出する負荷１
１の等価的な抵抗成分に対応して変化させる。なお、電
流型インバータ部５ａの駆動周波数ｆｒは、所定の値に
固定される。Next, another configuration example of the non-contact power supply device according to the embodiment of the present invention is shown in FIG. This wireless power transfer device
Although the configuration is substantially the same as that of FIG. 1, a saturable inductor 15 is provided in series with the primary conductor 3, and the inductance value of the saturable inductor 15 is detected by the resistance detection circuit 14.
It is changed corresponding to the equivalent resistance component of 1. The drive frequency fr of the current-type inverter 5a is fixed at a predetermined value.
【００４８】図６の非接触給電装置において、給電側回
路１５の共振回路は、１次コンデンサ６ａと１次導線３
及び可飽和インダクタ１５で構成され、その共振周波数
ｆｏ（Ｈｚ）は、次式（１）で表される。In the contactless power supply device shown in FIG. 6, the resonance circuit of the power supply side circuit 15 includes a primary capacitor 6a and a primary conductor 3
And the saturable inductor 15, and its resonance frequency fo (Hz) is expressed by the following equation (1).
【００４９】 ｆｏ＝１／〔２π・[（Ｌ＋Ｌｓ）・Ｃ]1/2〕 … 式（１） 但し、式（１）において、Ｌは、受電側回路１６を含む
１次導線３のインダクタンス値（単位はＨ）、Ｌｓは、
可飽和インダクタ１５のインダクタンス値、Ｃは、１次
コンデンサ6ａの静電容量（単位はＦ）である。Fo = 1 / [2π · [(L + Ls) · C]1/2 ] (1) where L is the inductance value of the primary conductor 3 including the power receiving side circuit 16. (Unit is H), Ls is
The inductance value C of the saturable inductor 15 is the capacitance (unit: F) of the primary capacitor 6a.
【００５０】本実施の形態の非接触給電装置では、抵抗
検出回路１４で検出した負荷１１の等価的な抵抗成分に
対応して、可飽和インダクタ１５のインダクタンス値を
制御することにより、給電側回路１５の共振回路の共振
周波数ｆｏを電流型インバータ５ａの駆動周波数ｆｒに
一致させることが可能となる。In the contactless power supply device of the present embodiment, the power supply side circuit is controlled by controlling the inductance value of the saturable inductor 15 in accordance with the equivalent resistance component of the load 11 detected by the resistance detection circuit 14. The resonance frequency fo of the 15 resonance circuits can be matched with the drive frequency fr of the current-type inverter 5a.
【００５１】このため、電流型インバータ部５ａから負
荷側に供給する電力の力率をほぼ「１」近くにすること
ができ、供給する皮相電力（電圧×電流）に対して負荷
１１で消費される電力の効率をほぼ１００％近くにし
て、効率的な電力伝送を行うことができる。For this reason, the power factor of the power supplied from the current-type inverter unit 5a to the load side can be made substantially close to “1”, and the apparent power (voltage × current) supplied to the load 11 is consumed. Power efficiency can be made nearly 100%, and efficient power transmission can be performed.
【００５２】図７は、本発明の実施の形態の非接触給電
装置の他の構成例である。この非接触給電装置は、図２
とほぼ同様の構成であるが、１次導線３と直列に可変キ
ャパシタ１６を設け、抵抗検出回路１４が検出する負荷
１１の等価的な抵抗成分に対応して、可変キャパシタ１
６の容量値を変化させる。なお、電圧型インバータ部５
ｂの駆動周波数ｆｒは、所定の値に固定される。FIG. 7 shows another configuration example of the non-contact power supply device according to the embodiment of the present invention. FIG.
However, a variable capacitor 16 is provided in series with the primary conductor 3, and the variable capacitor 1 corresponds to the equivalent resistance component of the load 11 detected by the resistance detection circuit 14.
6 is changed. The voltage type inverter unit 5
The drive frequency fr of b is fixed to a predetermined value.
【００５３】図７の非接触給電装置において、給電側回
路１５の共振回路は、１次コンデンサ６ｂと可変キャパ
シタ１６及び１次導線３で構成され、その共振周波数ｆ
ｏ（Ｈｚ）は、次式（２）で表される。In the contactless power supply device of FIG. 7, the resonance circuit of the power supply side circuit 15 is composed of the primary capacitor 6b, the variable capacitor 16 and the primary conductor 3, and has a resonance frequency f.
o (Hz) is represented by the following equation (2).
【００５４】 ｆｏ＝１／〔２π・[Ｌ・（Ｃ＋Ｃｓ）]1/2〕 … 式（２） 但し、式（２）において、Ｌは、受電側回路１６を含む
１次導線３のインダクタンス値（単位はＨ）、Ｃは、１
次コンデンサ6ｂの容量値（単位はＦ）、Ｃｓは、可変
キャパシタ１６の容量値である。Fo = 1 / [2π · [L · (C + Cs)]1/2 ] (2) where L is the inductance value of the primary conductor 3 including the power receiving side circuit 16. (Unit is H), C is 1
The capacitance value (unit is F) of the next capacitor 6b and Cs is the capacitance value of the variable capacitor 16.
【００５５】本実施の形態の非接触給電装置では、抵抗
検出回路１４で検出した負荷１１の等価的な抵抗成分に
対応して、可変キャパシタ１６の容量値を制御すること
により、給電側回路１５の共振回路の共振周波数ｆｏを
電圧型インバータ５ｂの駆動周波数ｆｒに一致させるこ
とが可能となる。In the contactless power supply device of the present embodiment, by controlling the capacitance value of the variable capacitor 16 in accordance with the equivalent resistance component of the load 11 detected by the resistance detection circuit 14, the power supply side circuit 15 Can be matched with the drive frequency fr of the voltage-type inverter 5b.
【００５６】このため、電圧型インバータ部５ｂから負
荷側に供給する電力の力率をほぼ「１」近くに制御する
ことができ、供給する皮相電力（電圧×電流）に対して
負荷１１で消費される電力の効率をほぼ１００％近くに
して、効率的な電力伝送を行うことができる。Therefore, the power factor of the power supplied from the voltage-type inverter unit 5b to the load side can be controlled to be substantially close to “1”, and the apparent power (voltage × current) supplied to the load 11 is consumed. Power efficiency can be made nearly 100%, and efficient power transmission can be performed.
【００５７】本発明の保護範囲は、上記の実施の形態に
限定されず、特許請求の範囲に記載された発明とその均
等物に及ぶものである。The scope of protection of the present invention is not limited to the above embodiments, but extends to the inventions described in the claims and their equivalents.
【００５８】[0058]
【発明の効果】以上、本発明によれば、抵抗検出回路が
検出した負荷の抵抗成分に応じて、高周波電源部が生成
する高周波電力の周波数を制御するので、高周波電源部
から出力される高周波電力の力率をほぼ「１」近くにす
ることができる。従って、高周波電源部が供給する皮相
電力（電圧×電流）に対して負荷で消費される電力の効
率が高くなり、効率的な電力伝送を行うことができる。As described above, according to the present invention, the frequency of the high-frequency power generated by the high-frequency power supply is controlled in accordance with the resistance component of the load detected by the resistance detection circuit. The power factor of the electric power can be made substantially close to “1”. Accordingly, the efficiency of the power consumed by the load with respect to the apparent power (voltage × current) supplied by the high-frequency power supply unit increases, and efficient power transmission can be performed.
【００５９】また、本発明によれば、高周波インバータ
の駆動周波数が共振回路の共振周波数になるように制御
されるので、高周波電源部から負荷側を見たインピーダ
ンスがほぼ純抵抗成分になる。従って、高周波電源部か
ら負荷側に供給する電力の力率をほぼ「１」近くにして
効率的な電力伝送を行うことができる。Further, according to the present invention, since the driving frequency of the high-frequency inverter is controlled to be equal to the resonance frequency of the resonance circuit, the impedance viewed from the high-frequency power supply to the load side becomes substantially a pure resistance component. Therefore, the power factor of the power supplied from the high-frequency power supply unit to the load side can be made substantially close to “1”, and efficient power transmission can be performed.
【００６０】また、本発明によれば、可飽和インダクタ
は、共振回路の共振周波数が高周波インバータの駆動周
波数になるように制御されるので、高周波電源部から負
荷側を見たインピーダンスがほぼ純抵抗成分になる。従
って、高周波電源部から負荷側に供給する電力の力率を
ほぼ「１」近くにして効率的な電力伝送を行うことがで
きる。Further, according to the present invention, the saturable inductor is controlled such that the resonance frequency of the resonance circuit is equal to the drive frequency of the high-frequency inverter. Become an ingredient. Therefore, the power factor of the power supplied from the high-frequency power supply unit to the load side can be made substantially close to “1”, and efficient power transmission can be performed.
【００６１】更に、本発明によれば、可変キャパシタ
は、共振回路の共振周波数が高周波インバータの駆動周
波数になるように制御されるので、高周波電源部から負
荷側を見たインピーダンスがほぼ純抵抗成分になる。従
って、高周波電源部から負荷側に供給する電力の力率を
ほぼ「１」近くにして効率的な電力伝送を行うことがで
きる。Further, according to the present invention, since the variable capacitor is controlled so that the resonance frequency of the resonance circuit becomes equal to the driving frequency of the high-frequency inverter, the impedance when the load is viewed from the high-frequency power supply section is substantially a pure resistance component. become. Therefore, the power factor of the power supplied from the high-frequency power supply unit to the load side can be made substantially close to “1”, and efficient power transmission can be performed.
【図１】本発明の実施の形態の非接触給電装置の構成図
（１）である。FIG. 1 is a configuration diagram (1) of a contactless power supply device according to an embodiment of the present invention.
【図２】本発明の実施の形態の非接触給電装置の構成図
（２）である。FIG. 2 is a configuration diagram (2) of the wireless power supply device according to the embodiment of the present invention.
【図３】非接触給電装置の等価回路図である。FIG. 3 is an equivalent circuit diagram of the wireless power supply device.
【図４】従来の非接触給電装置の特性図である。FIG. 4 is a characteristic diagram of a conventional wireless power supply device.
【図５】本発明の実施の形態の非接触給電装置の特性図
である。FIG. 5 is a characteristic diagram of the wireless power supply device according to the embodiment of the present invention.
【図６】本発明の実施の形態の非接触給電装置の構成図
（３）である。FIG. 6 is a configuration diagram (3) of the wireless power supply device according to the embodiment of the present invention.
【図７】本発明の実施の形態の非接触給電装置の構成図
（４）である。FIG. 7 is a configuration diagram (4) of the wireless power supply device according to the embodiment of the present invention.
【図８】従来の非接触給電装置の構成図（１）である。FIG. 8 is a configuration diagram (1) of a conventional wireless power supply device.
【図９】従来の非接触給電装置の構成図（２）である。FIG. 9 is a configuration diagram (2) of a conventional wireless power supply device.
【図１０】１次導線及び受電コイルの概略構成図であ
る。FIG. 10 is a schematic configuration diagram of a primary conductor and a power receiving coil.
１ 交流電源部 ２ 直流電源部 ３ １次導線 ４ トランス ５ａ 電流型インバータ部 ５ｂ 電圧型インバータ部 ６ａ、６ｂ １次コンデンサ ７ 整流部 ８ 受電コイル ９ ２次コンデンサ １０ ２次電源部 １１ 負荷 １２ 周波数制御装置 １３ 周波数コントローラ １４ 抵抗検出回路 １５ 可飽和インダクタ １６ 可変キャパシタ DESCRIPTION OF SYMBOLS 1 AC power supply part 2 DC power supply part 3 Primary conductor 4 Transformer 5a Current type inverter part 5b Voltage type inverter part 6a, 6b Primary capacitor 7 Rectification part 8 Receiving coil 9 Secondary capacitor 10 Secondary power supply part 11 Load 12 Frequency control Device 13 Frequency controller 14 Resistance detection circuit 15 Saturable inductor 16 Variable capacitor
───────────────────────────────────────────────────── フロントページの続き (72)発明者 若元 郁夫 広島県広島市西区観音新町四丁目６番22号 三菱重工業株式会社広島研究所内 (72)発明者 戸中 英樹 広島県広島市西区観音新町四丁目６番22号 三菱重工業株式会社広島研究所内 Ｆターム(参考） 5H007 AA02 AA07 CB04 CB09 CB25 CC32 DA03 DA05 DA06 DC05 EA09 5H105 AA20 BA09 BB05 CC02 CC12 CC19 DD10 EE19 ──────────────────────────────────────────────────続 き Continuing from the front page (72) Ikuo Wakamoto, Inventor 4-62-22 Kannon Shinmachi, Nishi-ku, Hiroshima-shi, Hiroshima Inside Mitsubishi Heavy Industries, Ltd. F-term (reference) in Mitsubishi Heavy Industries, Ltd. Hiroshima R & D Co., Ltd. 4-chome No. 6-22 No. 5H007 AA02 AA07 CB04 CB09 CB25 CC32 DA03 DA05 DA06 DC05 EA09 5H105 AA20 BA09 BB05 CC02 CC12 CC19 DD10 EE19
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001064308AJP2002272134A (en) | 2001-03-08 | 2001-03-08 | Non-contact feeding device of high frequency power, and method therefor |
| Publication Number | Publication Date |
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| Date | Code | Title | Description |
|---|---|---|---|
| A300 | Withdrawal of application because of no request for examination | Free format text:JAPANESE INTERMEDIATE CODE: A300 Effective date:20080513 |