CN1985436A - Traction-free LO generation systems and methods - Google Patents

Abstract

The present invention provides a system and method for generating an LO signal for an RF transmitter that eliminates the risk of LO pulling. Filtering techniques are employed to select the desired harmonic of the VCO signal, which is typically the third harmonic. The required in-phase and quadrature LO signals can be obtained using dividers. Any harmonic relation between the transmit signal and the VCO frequency is avoided and no intermediate signal near the VCO frequency needs to be generated, thus avoiding pulling of the VCO.

Description

Translated fromChinese

无牵引LO产生系统和方法Traction-free LO generation systems and methods

本发明涉及本机振荡器或者单管芯射频收发器的LO牵引。更具体来说，本发明涉及以至少一种方式为收发器产生LO信号的系统和方法。最具体来说，本发明涉及以至少一种方式产生LO信号的系统和方法，其中不会牵引收发器中的发射机的VCO。The present invention relates to local oscillator or LO pulling for single die radio frequency transceivers. More specifically, the present invention relates to systems and methods for generating LO signals for transceivers in at least one manner. Most particularly, the present invention relates to systems and methods for generating an LO signal in at least one manner without pulling the VCO of a transmitter in a transceiver.

当今的无线电收发器在单个芯片中包含了其大多数功能。这样就允许高规模集成，从而使得在消费产品中使用射频(RF)收发器是非常成本有效的。但是，当全部RF功能被置于单个管芯中时，“LO牵引”和“VCO牵引”就成为了芯片设计者们需要解决的问题。Today's radio transceivers contain most of their functionality in a single chip. This allows high-scale integration, making it very cost-effective to use radio frequency (RF) transceivers in consumer products. However, when all RF functions are placed in a single die, "LO pull" and "VCO pull" become problems for chip designers to solve.

当发送信号的一部分耦合回到频率合成器的压控振荡器(VCO)时发生LO牵引。利用将被发送的信息来调制发送信号，因而VCO也被调制。由于该VCO被用来产生发送信号(例如通过混频器)，因此存在使得发送信号的质量严重降低的反馈环路。由于VCO的可再生特性，即便是最小的耦合都可能对发送信号的质量产生严重的影响。LO pulling occurs when a portion of the transmit signal is coupled back into the frequency synthesizer's voltage-controlled oscillator (VCO). The transmit signal is modulated with the information to be transmitted, thus the VCO is also modulated. Since the VCO is used to generate the transmit signal (eg via a mixer), there is a feedback loop that seriously degrades the quality of the transmit signal. Due to the reproducible nature of the VCO, even the smallest coupling can have a serious impact on the quality of the transmitted signal.

为发送混频器产生LO信号的几种可选方案已经在文献中提出。所有提出的方案均旨在减少VCO的牵引，例如参见Zolfaghari，Alireza和Razavi，Behzad的“A Low-Power 2.4 GHz Transmitter/Receiver CMOS IC”(IEEE-JSSC，第38卷，第2期，2003年2月，第176-183页)以及Darabi，Hooman等人的“A 2.4-GHzCMOS Transceiver for Bluetooth”(IEEE-JSSC，第36卷，第12期，2001年12月，第2016-2023页)。这些所提出的方案采用对发送信号的两级上变换或者采用LO信号的两级产生来避免发送信号(或其谐波)与VCO频率之间的谐波关系。然而，在任一种情况下都存在大量的谐波、次谐波以及混频产物，并且这些混频产物当中的某一些仍然能够导致VCO牵引。在一些所提出的方案中，需要大量的滤波来抑制多余的频谱分量。Several alternatives for generating the LO signal for the transmit mixer have been proposed in the literature. All proposed schemes aim at reducing VCO pull, see for example Zolfaghari, Alireza and Razavi, Behzad, "A Low-Power 2.4 GHz Transmitter/Receiver CMOS IC" (IEEE-JSSC, Vol. 38, No. 2, 2003 February, pp. 176-183) and "A 2.4-GHz CMOS Transceiver for Bluetooth" by Darabi, Hooman et al. (IEEE-JSSC, Vol. 36, No. 12, Dec. 2001, pp. 2016-2023). These proposed schemes employ either two-stage up-conversion of the transmit signal or two-stage generation of the LO signal to avoid the harmonic relationship between the transmit signal (or its harmonics) and the VCO frequency. However, in either case there are a large number of harmonics, sub-harmonics, and mixing products, and some of these mixing products can still cause VCO pulling. In some proposed schemes, extensive filtering is required to suppress unwanted spectral components.

Zolfaghari等人提出在所述上变换处理中使用双中频(IF)。所述频率方法被选择成没有频谱分量与VCO重合，从而以复杂的信号路径为代价避免了所述牵引问题。另一种方法是组合传统的直接上变换发射机与替换的LO产生。同样，其频率方案被选择成使得不产生重合频谱。但是，Darabi等人提出的解决方案需要在信号被放大之前对混频器输出信号进行滤波。如果在进一步放大之前没有应用滤波器，则混频器输出信号将是800MHz方波而不是所需2400MHz信号。这是由两个混频器输入信号之间的谐波关系造成的。因此，该方法要求更为精确的滤波。Darabi等人提出的方法在图1中示出，其包括用于产生输出信号LOI 107和LOQ 108的具有所需2400MHz频率的本机振荡器100。本机振荡器100包括VCO电路101、缓冲器109、分频器102和两个混频器105、106，该分频器102用于产生800MHz同相LO分量I 103和正交分量Q 104信号，所述信号的频率是该VCO的输出的一半。VCO电路101产生1600MHz信号，该信号随后通过缓冲器109被提供到分频器电路102，该分频器电路102产生具有800MHz频率(或者说VCO 101的输出频率的一半)的同相信号I 103和正交信号Q 104。Zolfaghari et al. propose to use dual intermediate frequencies (IFs) in the up-conversion process. The frequency approach is chosen so that no spectral components coincide with the VCO, thereby avoiding the pulling problem at the expense of a complex signal path. Another approach is to combine a traditional direct up-conversion transmitter with an alternative LO generation. Also, its frequency scheme is chosen such that no overlapping spectra are produced. However, the solution proposed by Darabi et al. requires filtering of the mixer output signal before the signal is amplified. If no filter is applied before further amplification, the mixer output signal will be an 800MHz square wave instead of the desired 2400MHz signal. This is caused by the harmonic relationship between the two mixer input signals. Therefore, this method requires more precise filtering. The method proposed by Darabi et al. is shown in FIG. 1, which includes a local oscillator 100 with a desired frequency of 2400 MHz for generating output signals LOI 107 and LOQ 108. The local oscillator 100 comprises a VCO circuit 101, a buffer 109, a frequency divider 102 for generating 800 MHz in-phase LO component I 103 and quadrature component Q 104 signals, and two mixers 105, 106, The frequency of the signal is half of the output of the VCO. VCO circuit 101 generates a 1600 MHz signal which is then provided through buffer 109 to frequency divider circuit 102 which generates an in-phase signal I 103 having a frequency of 800 MHz (or half the output frequency of VCO 101) and quadrature signal Q 104.

因此，需要针对现有技术中的LO牵引问题的解决方案。本发明提供一种在没有牵引VCO的风险情况下为发射机产生LO信号的系统和方法。本发明的系统和方法采用滤波技术来选择VCO信号的所需谐波。所需的同相和正交LO信号可以通过除法器得到。本发明的系统和方法避免了在发送信号和VCO频率之间的任何谐波关系，并且无需产生接近VCO频率的中间信号。因此，本发明的系统和方法避免了VCO的牵引。Therefore, a solution to the LO pulling problem in the prior art is needed. The present invention provides a system and method for generating an LO signal for a transmitter without the risk of pulling the VCO. The systems and methods of the present invention employ filtering techniques to select the desired harmonics of the VCO signal. The required in-phase and quadrature LO signals can be obtained through dividers. The system and method of the present invention avoids any harmonic relationship between the transmit signal and the VCO frequency, and eliminates the need to generate intermediate signals close to the VCO frequency. Thus, the systems and methods of the present invention avoid VCO pull.

VCO产生正弦输入信号，该信号随后被转换成方波、被执行除法以及被滤波，以便获得具有预定输出频率的所需谐波同相I和正交Q信号。The VCO produces a sinusoidal input signal which is then converted to a square wave, divided and filtered to obtain the desired harmonic in-phase I and quadrature Q signals with a predetermined output frequency.

根据本发明的一个方面，本机振荡器被提供来在所需输出频率下产生信号。该本机振荡器包括：振荡电路，其被配置成在低于所需输出频率的第一频率下产生第一同相信号和第一正交信号，第一正交信号具有相对于第一同相信号的相移；一对谐波滤波器，其中一个被耦合来接收第一同相信号，另一个被耦合来接收第一正交信号，该对谐波滤波器被配置成获得这些第一信号当中的每一个的预定谐波；第一和第二发送混频器，其分别被耦合成由所述第一信号当中的每一个的所述所获得的谐波驱动。According to one aspect of the invention, a local oscillator is provided to generate a signal at a desired output frequency. The local oscillator includes an oscillating circuit configured to generate a first in-phase signal and a first quadrature signal at a first frequency lower than a desired output frequency, the first quadrature signal having a relative phase shift of the phase signal; a pair of harmonic filters, one of which is coupled to receive the first in-phase signal and the other coupled to receive the first quadrature signal, the pair of harmonic filters is configured to obtain these first predetermined harmonics of each of the signals; first and second transmit mixers respectively coupled to be driven by said obtained harmonics of each of said first signals.

在一个实施例中，获得方波输入信号的所需谐波，并且从中产生同相信号和正交信号，从而使得该正交信号相对于该同相信号被相移，所述I和Q信号被用于驱动发送混频器。In one embodiment, the desired harmonics of a square wave input signal are obtained and an in-phase signal and a quadrature signal are generated therefrom such that the quadrature signal is phase shifted relative to the in-phase signal, the I and Q signals is used to drive the transmit mixer.

在一个实施例中，所述振荡电路被配置成使用具有高品质因数(Q)和较小面积的LC储能电路。In one embodiment, the oscillating circuit is configured to use an LC tank circuit with a high quality factor (Q) and a small area.

所需谐波优选地是三次谐波。替换实施例采用一个滤波器来选择所需谐波。The desired harmonic is preferably the third harmonic. Alternative embodiments use a filter to select the desired harmonics.

图1示出了用于避免LO牵引的现有技术方法；Figure 1 shows a prior art method for avoiding LO pulling;

图2示出了根据本发明的无牵引LO产生的第一优选实施例；Figure 2 shows a first preferred embodiment of traction-free LO generation according to the present invention;

图3示出了根据本发明的无牵引LO产生的第二优选实施例；Figure 3 shows a second preferred embodiment of traction-free LO generation according to the present invention;

图4示出了根据本发明的无牵引LO产生的第三优选实施例；Figure 4 shows a third preferred embodiment of traction-free LO generation according to the present invention;

图5示出了将对其应用本发明的实施例的无线通信系统的体系结构；以及Figure 5 shows the architecture of a wireless communication system to which an embodiment of the present invention will be applied; and

图6示出了根据本发明的一个实施例的图5的通信系统的无线设备的简化方框图。FIG. 6 shows a simplified block diagram of a wireless device of the communication system of FIG. 5 according to one embodiment of the present invention.

本领域的技术人员应当理解，下面的描述旨在说明而不是限定本发明。本领域的技术人员还应当理解，在本发明的主旨和所附权利要求书的范围内可以有多种变型。在当前的描述中可以省略已知功能和操作的不必要的细节，以免模糊本发明。Those skilled in the art should understand that the following description is intended to illustrate rather than limit the present invention. Those skilled in the art will also appreciate that there are many variations that are possible within the spirit of the invention and the scope of the appended claims. Unnecessary detail of known functions and operations may be omitted from the current description so as not to obscure the present invention.

在第一实施例中，如图2所示产生无牵引LO。运行在1600MHz下的VCO201提供输入212给IQ产生电路200，该输入被除法器202除以2以便产生同相LO分量I 203和正交LO分量Q 204，其包含800MHz的奇次谐波。如图2所示，除法器202的输出信号(优选地是除以2)是方波203、204，其包含这些奇次谐波。在这个第一优选实施例中，本发明的系统和方法将滤波器211应用于方波203、204以便获得这些信号的三次谐波，并且因此得到2400MHz的同相信号LOI 207和正交信号LOQ 208。LOI 207和LOQ 208随后被用于驱动发送和接收混频器。In a first embodiment, a pull-free LO is created as shown in FIG. 2 . VCO 201 operating at 1600 MHz provides input 212 to IQ generation circuit 200, which is divided by 2 by divider 202 to generate in-phase LO component I 203 and quadrature LO component Q 204, which contain the odd harmonics of 800 MHz. As shown in Figure 2, the output signal of the divider 202 (preferably divided by 2) is a square wave 203, 204, which contains these odd harmonics. In this first preferred embodiment, the system and method of the present invention apply a filter 211 to the square waves 203, 204 in order to obtain the third harmonic of these signals, and thus obtain an in-phase signal LOI 207 and a quadrature signal LOQ at 2400 MHz 208. LOI 207 and LOQ 208 are then used to drive transmit and receive mixers.

在该第一实施例中，假定LC储能电路的Q因数是10，并且800MHz基波分量被抑制了28dB。由于三次谐波的信号级比800MHz基波分量低9.5dB(方波的傅立叶系数：1，1/3，1/5，1/7...)，因此所得的2400MHz的LO信号包含-20dBc的800MHz乱真信号。在第一实施例中，在混频后这个多余信号由天线滤波器去除。In this first embodiment, it is assumed that the Q factor of the LC tank is 10, and the 800 MHz fundamental wave component is suppressed by 28 dB. Since the signal level of the third harmonic is 9.5dB lower than the 800MHz fundamental component (Fourier coefficients of the square wave: 1, 1/3, 1/5, 1/7...), the resulting 2400MHz LO signal contains -20dBc 800MHz spurious signal. In a first embodiment, this unwanted signal is removed by an antenna filter after mixing.

为了在发送路径中实现良好的镜像抑制，所述I和Q信号必须具有精确的正交和相等的振幅。第一实施例包括至少一个实现这种匹配的滤波放大器。优选地，多相(LC)滤波器满足所述匹配需求。In order to achieve good image rejection in the transmit path, the I and Q signals must have exact quadrature and equal amplitude. A first embodiment includes at least one filter amplifier to achieve this matching. Preferably, a polyphase (LC) filter satisfies said matching requirements.

在第二实施例中，如图3所示产生无牵引LO，从而避开了第一实施例中的严格的匹配需求。运行在1600MHz下的VCO 201提供输入312给IQ产生电路300，从而在第二实施例中，先于所述除法器(优选地是除以2 202)进行三次谐波滤波211。所述I和Q信号之间的正交关系现在由除法器202确定，其确保了精确的正交。对所述VCO信号的经过削波的(放大的)版本直接执行三次谐波滤波211，从而在第二实施例中所述LC储能电路被调谐到4800MHz。这一更高的频率允许更高的储能电路Q因数，作为一个附加的优点，其具有更小的面积。此外，在该第二实施例中仅需要一个LC储能电路，从而进一步节约了面积。In the second embodiment, a pull-free LO is generated as shown in FIG. 3 , thereby circumventing the strict matching requirement of the first embodiment. The VCO 201 running at 1600 MHz provides an input 312 to the IQ generation circuit 300, so that in the second embodiment third harmonic filtering 211 is performed prior to the divider (preferably divide by 2 202). The quadrature relationship between the I and Q signals is now determined by divider 202, which ensures exact quadrature. Third harmonic filtering 211 is performed directly on the clipped (amplified) version of the VCO signal, so that in the second embodiment the LC tank is tuned to 4800MHz. This higher frequency allows for a higher Q-factor of the tank circuit which, as an added advantage, has a smaller area. Furthermore, only one LC tank circuit is required in this second embodiment, thereby further saving area.

由于除以2 202的再生特质，所述输入正弦信号被转换成方波，因此对滤波后的三次谐波信号或者对所需的I和Q LO信号的额外的放大不是必需的。仅仅在所述滤波之前需要放大(或削波)，以便产生具有足够的三次谐波信号成分的1600MHz信号。该谐波滤波器的输出频谱仍然包含残留的1600MHz分量，但是这个信号被除法器202额外地抑制了6dB。因此，所述LO频谱所包含的1600MHz下的多余信号分量与2400MHz下的LO相比小于26dBc，其中仍然假定Q＝10(由于除法器202的“对称化”效应，在3200MHz处也存在-26dBc的频谱分量)。在第二实施例中，所述多余频谱由天线滤波器或者位于发送链内的滤波器(均未示出)的其中之一过滤。Due to the regenerative nature of dividing by 2202, the input sinusoidal signal is converted to a square wave, so no additional amplification is necessary for the filtered third harmonic signal or for the desired I and Q LO signals. Amplification (or clipping) is only required prior to said filtering in order to produce a 1600 MHz signal with sufficient third harmonic signal content. The output spectrum of the harmonic filter still contains a residual 1600 MHz component, but this signal is additionally suppressed by divider 202 by 6 dB. Thus, the LO spectrum contains less than 26dBc of unwanted signal components at 1600MHz compared to the LO at 2400MHz, still assuming Q=10 (there is also -26dBc at 3200MHz due to the "symmetrization" effect of divider 202 spectrum components). In a second embodiment, the excess spectrum is filtered by one of an antenna filter or a filter located within the transmit chain (neither shown).

在第三实施例中，如图4所示，除以2413的再生属性被用来产生1600MHz方波以输入到第二实施例的三次谐波滤波器211。在第三实施例中，无牵引LO由被调谐到3200MHz的VCO 201产生，其允许更高的Q以及LC储能电路的更小面积，并且该3200MHz信号被输入到IQ产生电路400，其中该3200MHz信号首先被执行除法，所得的1600MHz方波被输入到与第二实施例基本上相同的电路。I 407和Q 408信号的输出频谱与第二实施例的I 307和Q 308信号相当，其在1600MHz和3200MHz处包含与所需的2400MHz信号相比至少低26dB的残留频谱分量。所述1600MHz和3200MHz的频谱由天线滤波器(未示出)进一步抑制。In the third embodiment, as shown in FIG. 4, the regenerative property divided by 2413 is used to generate a 1600 MHz square wave for input to the third harmonic filter 211 of the second embodiment. In a third embodiment, the pull-free LO is generated by the VCO 201 tuned to 3200MHz, which allows higher Q and smaller area of the LC tank circuit, and this 3200MHz signal is input to the IQ generation circuit 400, where the The 3200MHz signal is first subjected to division, and the resulting 1600MHz square wave is input to substantially the same circuit as in the second embodiment. The output spectrum of the I 407 and Q 408 signals is comparable to the I 307 and Q 308 signals of the second embodiment, which contain residual spectral components at 1600MHz and 3200MHz that are at least 26dB lower than the desired 2400MHz signal. The 1600MHz and 3200MHz spectrum are further suppressed by antenna filters (not shown).

在可选的实施例中，在除法器202之前对第一到第三实施例当中的每一个应用进一步的滤波，以便抑制1600MHz基波信号。该进一步的滤波可以通过下面的任何一种方式完成：在除法器输出和滤波器输入之间与例如4GHz的拐角频率的AC耦合，添加第二级甚至第三级滤波，以及应用1600MHz的陷波滤波器。由于信号除法产生对称的边带，因此先于最后的除以2进行滤波。第三实施例的优点在于，牵引VCO的信号分量只在最后的除以2之后才存在(应当注意，这个3200MHz的信号与VCO信号本身100％相关，所以只可能发生“DC牵引”(即相移))。In an alternative embodiment, further filtering is applied to each of the first to third embodiments prior to divider 202 in order to suppress the 1600 MHz fundamental signal. This further filtering can be done by any of the following: AC coupling between the divider output and filter input to a corner frequency of say 4GHz, adding a second or even third stage of filtering, and applying a notch at 1600MHz filter. Since signal division produces symmetric sidebands, it is filtered prior to the final division by 2. The advantage of the third embodiment is that the signal component pulling the VCO is only present after the final divide by 2 (it should be noted that this 3200MHz signal is 100% correlated to the VCO signal itself, so only "DC pulling" (i.e. phase shift)).

本发明的无牵引本机振荡器的设备和方法可以用于无线个人局域网(WPAN)和无线局域网(WLAN)，其中RF发射机包括混频器，该混频器被配置成利用数据信号调制该LO的输出信号。可以应用本发明的网络进一步包括GSM、蓝牙和DECT设备。图5示出了可以应用本发明各实施例的代表性无线网络。根据本发明的原理，提供一个混频器，该混频器被配置成利用数据信号来调制LO的输出信号，从而避免LO的牵引。应当注意到，为了说明的目的，图5示出的网络很小。在实践中，大多数WLAN将包括数量多得多的合并有本发明的移动收发器。The pull-free local oscillator apparatus and method of the present invention can be used in Wireless Personal Area Networks (WPAN) and Wireless Local Area Networks (WLAN) where the RF transmitter includes a mixer configured to modulate the RF transmitter with a data signal. LO output signal. Networks to which the invention can be applied further include GSM, Bluetooth and DECT devices. Figure 5 illustrates a representative wireless network in which embodiments of the invention may be applied. In accordance with the principles of the present invention, a mixer is provided that is configured to modulate an output signal of an LO with a data signal, thereby avoiding pulling by the LO. It should be noted that the network shown in Figure 5 is small for illustrative purposes. In practice, most WLANs will include a much larger number of mobile transceivers incorporating the present invention.

本发明的LO发生器的低功率电路和体系结构可以应用于WPAN和WLAN，并且允许降低其中的无线设备的成本及功耗。为此，本发明提出了一种滤波技术，该滤波技术用来选择VCO信号的所期望的谐波，其具有通过除法器得到的所需的同相和正交LO信号。因此避免了发送信号与所述VCO之间的任何谐波关系，并且避免了产生接近VCO频率的中间信号。The low power circuitry and architecture of the LO generator of the present invention can be applied to WPANs and WLANs and allow for reduced cost and power consumption of wireless devices therein. To this end, the present invention proposes a filtering technique for selecting the desired harmonics of the VCO signal with the desired in-phase and quadrature LO signals obtained through a divider. Any harmonic relationship between the transmitted signal and the VCO is thus avoided and the generation of intermediate signals close to the VCO frequency is avoided.

现在参考图6，图5所示的WPAN/WLAN中的每个设备可以包括具有如图6的方框图所示的体系结构的收发器。每个设备可以包括耦合到至少一个发射机601的控制器602、依据本发明的LO发生器603(200 300 400)以及接收机604。发射机601和接收机604耦合到天线605。所有上述元件可以与其他组件(例如天线)一起集成到单个芯片上。控制器602可以提供自适应编程，从而例如使该收发器适应于不同的调制方案和特定于各种通信协议的数据速率，所述通信协议包括IEEE 802.11、蓝牙和现有技术中已知的任何其他协议。该控制器可以对所述LO发生器进行编程，以便选择特定的谐波，其并不限于三次谐波。Referring now to FIG. 6 , each device in the WPAN/WLAN shown in FIG. 5 may include a transceiver having the architecture shown in the block diagram of FIG. 6 . Each device may comprise a controller 602 coupled to at least one transmitter 601, an LO generator 603 (200 300 400) according to the invention and a receiver 604. Transmitter 601 and receiver 604 are coupled to antenna 605 . All of the above elements can be integrated onto a single chip along with other components such as antennas. The controller 602 can provide adaptive programming, for example, to adapt the transceiver to different modulation schemes and data rates specific to various communication protocols, including IEEE 802.11, Bluetooth, and any other known in the art. other agreements. The controller can program the LO generator to select a particular harmonic, which is not limited to the third harmonic.

虽然已经示出并且描述了本发明的优选实施例，但是本领域技术人员应当理解，本文所述的本机振荡器只是说明性的，在不背离本发明的真实范围的情况下，可以对所述本机振荡器进行多种改变和修改，并且可以用等效元件来替换其中的元件。此外，在不背离本发明的中心范围的情况下，可以进行很多修改以便使本发明的教导适应于特定情况，例如，可以在不同的输出频率下操作所述VCO。因此，本发明并不局限于作为实施本发明的最佳模式而公开的特定实施例，而是包括落入所附权利要求书的范围内的所有实施例。While a preferred embodiment of the present invention has been shown and described, those skilled in the art will appreciate that the local oscillator described herein is illustrative only and that all Various changes and modifications are made to the local oscillator described above, and equivalent elements may be substituted for elements thereof. Furthermore, many modifications may be made to adapt the teachings of the invention to a particular situation without departing from the central scope of the invention, eg the VCO may be operated at different output frequencies. Therefore, it is intended that the invention not be limited to the particular embodiment disclosed as the best mode for carrying out this invention, but that it will include all embodiments falling within the scope of the appended claims.

Claims (36)

1, a kind of pierce circuit, it is used to produce the homophase and the quadrature component of the transmission signal with required frequency, and described circuit comprises:

Oscillator, it is used to export first sinusoidal signal with first frequency; And

The IQ that comprises final divider produces circuit, described IQ produces in-phase signal component and the quadrature phase signal component that circuit is used for receiving first sinusoidal signal and therefrom derives this transmission signal, each described component has required frequency, thereby between the required frequency of this transmission signal and first frequency, there is not harmonic relationships

Wherein, avoided the traction of this oscillator.

2, pierce circuit as claimed in claim 1, wherein, described IQ produces circuit and comprises:

Be used for first sinusoidal signal is transformed into the device of first square-wave signal;

Frequency divider as described final divider, it is used for receiving first square wave and first square wave is carried out division, so that produce the first in-phase signal component and the first quadrature phase signal component of this first square wave, wherein by phase shift, and described first component comprises through carrying out the odd harmonic of first sinusoidal signal behind the division each described first component with respect to another; And

First and second filters, its from this frequency divider receive respectively, amplification and the filtering first in-phase signal component and the first quadrature phase signal component so that the predetermined harmonic wave that obtains this first in-phase signal component and the first quadrature phase signal component respectively is with respectively as the in-phase signal component and the quadrature phase signal component of this transmission signal.

3, pierce circuit as claimed in claim 2, wherein, the described device that is used to change comprises amplifier.

4, pierce circuit as claimed in claim 3, wherein, described frequency divider is the divider divided by 2, and described predetermined harmonic wave is a triple-frequency harmonics.

5, pierce circuit as claimed in claim 4, wherein, the amplitude that the described in-phase signal component of described transmission signal and quadrature phase signal component have accurate quadrature and equate.

6, pierce circuit as claimed in claim 5, wherein, each in the middle of described first and second filters comprises LC accumulator and heterogeneous (LC) filter.

7, pierce circuit as claimed in claim 6, wherein, described first frequency is 1600MHz, described required frequency is 2400MHz, and the Q factor of described LC accumulator equals 10.

8, pierce circuit as claimed in claim 7, wherein, described IQ produces circuit and comprises that further the first-harmonic filter is to suppress the fundamental signal of 1600MHz, described first-harmonic filter is suitable for being coupled to described IQ and produces circuit before described final divider, so that receive the input signal of this final divider, and alternatively offering this final divider through the signal that suppresses as input signal.

9, pierce circuit as claimed in claim 8, wherein, described first-harmonic filter is to select from the group that is made of 1600MHz notch filter, the 3rd filter and third and fourth filter.

10, pierce circuit as claimed in claim 1, wherein, described IQ produces circuit and comprises:

Be used for first sinusoidal signal is transformed into the device of first square wave;

Filter, it is used for this first square wave of reception, amplification and filtering, so that the predetermined harmonic wave that obtains this first square wave is with as second sinusoidal signal with second frequency.

Frequency divider, it receives this second sinusoidal signal and it is carried out division as described final divider, and therefrom produces the described in-phase signal component and the quadrature phase signal component of described transmission signal respectively.

11, pierce circuit as claimed in claim 10, wherein, the described device that is used to change comprises amplifier.

12, pierce circuit as claimed in claim 11, wherein, described frequency divider is the divider divided by 2, and described predetermined harmonic wave is a triple-frequency harmonics.

13, pierce circuit as claimed in claim 12, wherein:

First frequency is 1600MHz;

Second frequency is 4800MHz;

Required frequency is 2400MHz; And

First filter further comprises the LC accumulator that its Q factor equals 10, and described LC accumulator is tuned to 4800MHz.

14, pierce circuit as claimed in claim 13, wherein, described IQ produces circuit and comprises that further the first-harmonic filter is to suppress the fundamental signal of 1600MHz, described first-harmonic filter is suitable for being coupled to described IQ and produces circuit before described final divider, so that receive the input signal of this final divider, and alternatively offering this final divider through the signal that suppresses as input signal.

15, oscillating circuit as claimed in claim 14, wherein, described first-harmonic filter is to select from the group that is made of 1600MHz notch filter, second filter and the second and the 3rd filter.

16, pierce circuit as claimed in claim 1, wherein, described IQ produces circuit and comprises:

First frequency divider, it is used for receiving first square wave, it is carried out division and this first square wave is transformed into first sinusoidal signal;

Filter, it is used for this first square wave of reception, amplification and filtering, so that the predetermined harmonic wave that obtains this first square wave is with as second sinusoidal signal with second frequency; And

Second frequency divider, it receives this second sinusoidal signal and it is carried out division as described final divider, so that therefrom produce the described in-phase signal component and the quadrature phase component of described transmission signal respectively.

17, pierce circuit as claimed in claim 16, wherein, described first and second frequency dividers are the divider divided by 2, and described predetermined harmonic wave is a triple-frequency harmonics.

18, pierce circuit as claimed in claim 17, wherein:

First frequency is 3200MHz;

First square wave has the frequency of 1600MHz;

Second frequency is 4800MHz;

Required frequency is 2400MHz; And

Described filter comprises that further its Q factor is greater than 10 LC accumulator.

19, pierce circuit as claimed in claim 18, wherein, described IQ produces circuit and comprises that further the first-harmonic filter is to suppress the fundamental signal of 1600MHz, described first-harmonic filter is suitable for being coupled to described IQ and produces circuit before described final divider, so that receive the input signal of this final divider, and alternatively offering this final divider through the 1600MHz component that suppresses as input signal.

20, oscillating circuit as claimed in claim 19, wherein, described first-harmonic filter is to select from the group that constitutes by 1600MHz notch filter, second filter, the second and the 3rd filter and with the AC coupling of the corner frequency of 4GHz, and described AC coupling also is suitable for being coupled to described IQ and produces circuit before first filter.

21, a kind of being used to produces the in-phase signal component I of transmission signal and the method for quadrature phase signal component Q, and wherein each component has identical required frequency, and this method may further comprise the steps:

Has first sinusoidal signal of first frequency by oscillator output; And

From first sinusoidal signal, derive in-phase signal component I and the quadrature phase signal component Q that this sends signal, each described component with respect to another by phase shift, each described component has required frequency, thereby between the required frequency of this transmission signal and first frequency, there is not harmonic relationships, thereby avoids the traction of this oscillator.

22, method as claimed in claim 21, wherein, described derivation step further may further comprise the steps:

First sinusoidal signal is transformed into first square wave;

With this first square wave divided by 2 so that obtain the first homophase square-wave component and the first quadrature phase square-wave component, thus make each described first component have with respect to another phase shift and comprise through the odd of carrying out this first frequency behind division ripple all;

Each described first component is amplified (slicing), so that obtain second in-phase signal and second quadrature phase signal; And

Second in-phase signal and second quadrature phase signal are carried out filtering, so that the predetermined harmonic wave that obtains this second in-phase signal and second quadrature phase signal is with respectively as described I and Q signal.

23, method as claimed in claim 22, wherein, described switch process comprises described first sinusoidal signal is amplified (slicing).

24, method as claimed in claim 23, wherein, described predetermined harmonic wave is a triple-frequency harmonics.

25, method as claimed in claim 24, wherein, the amplitude that described I and Q signal have accurate quadrature and equate.

26, method as claimed in claim 25, wherein, described required frequency is 2400MHz, described first frequency is 1600MHz.

27, method as claimed in claim 21, wherein, described derivation step further may further comprise the steps:

Described first sinusoidal signal is transformed into first square wave;

This first square wave is amplified (slicing) to first frequency;

Square wave after this amplification is carried out filtering, so that the predetermined harmonic wave that obtains the square wave after this amplification is with as second sine wave with second frequency; And

With this second sine wave divided by 2, so that obtain described I and Q with required frequency.

28, method as claimed in claim 27, wherein, described switch process comprises described first sinusoidal signal is amplified (slicing).

29, method as claimed in claim 28, wherein, described predetermined harmonic wave is a second harmonic.

30, method as claimed in claim 29, wherein, described first frequency is 1600MHz, and the 3rd frequency is 4800MHz, and required frequency is 2400MHz.

31, method as claimed in claim 30 further may further comprise the steps:

Before described division steps, carry out filter step, so that suppress to be included in 1600MHz fundamental signal wherein to described second sinusoidal signal.

32, method as claimed in claim 21, wherein, described derivation step further may further comprise the steps:

With first sinusoidal signal divided by 2, so that obtain first square wave;

This first square wave is carried out filtering and amplification, so that the predetermined harmonic wave that obtains this first square wave is with as second sinusoidal signal with second frequency; And

With this second sinusoidal signal divided by 2, so that obtain described I and Q with required frequency.

33, method as claimed in claim 32, wherein:

First frequency is 3200MHz;

First square wave has the frequency of 1600MHz;

Second frequency is 4800MHz; And

Required frequency is 2400MHz.

34, method as claimed in claim 33 further may further comprise the steps:

Before carrying out divided by 2 step, to one of them execution filter step of described second square wave and second sinusoidal signal, so that inhibition is included in 1600MHz fundamental signal wherein to described second sine wave.

35, a kind of transceiver comprises:

The local oscillation generator, it comprises the oscillator that is used to export first signal with first preset frequency and comprises that the IQ of divider produces circuit, this divider is used for receiving described sinusoidal signal and therefrom derives homophase square wave and the quadrature square-wave component that sends signal, and wherein each square-wave component has predetermined transmission frequency; And

Controller, its be used to programme first preset frequency of this oscillator and predetermined transmission frequency of this divider so that should be scheduled to not have harmonic relationships between the transmission frequency and first preset frequency, have wherein been avoided the traction of this oscillator.

36, transceiver as claimed in claim 35, wherein, described oscillator comprises voltage controlled oscillator.