Disclosure of Invention
The application aims to provide a current negative feedback phase-locked oscillating circuit for an ultrasonic power supply, the power supply and electronic equipment, and aims to solve at least one of the problems.
In a first aspect, an embodiment of the present application provides a current negative feedback phase-locked oscillation circuit for an ultrasonic power supply, including a multivibrator circuit and a current sensing circuit, where the multivibrator circuit is connected to a dc power supply and the current sensing circuit, the current sensing circuit is connected to an ultrasonic transducer, and the multivibrator circuit is sequentially connected to a driving circuit, a filtering circuit, and the ultrasonic transducer, where:
the multi-vibrator circuit comprises a feedback network, a window comparator, an RS trigger and a digital driver, wherein the multi-vibrator circuit is connected with the driving circuit and is used for converting a direct current signal provided by the direct current power supply into a high-frequency oscillating signal, and the multi-vibrator circuit is also used for driving the filter circuit;
The feedback network comprises a resistor and a capacitor, one end of the resistor is connected with one end of the capacitor, one end of the resistor is also connected to the output end of the current sensing circuit and the second node, the other end of the resistor and the output of the digital drive are connected to the first node, the other end of the capacitor is grounded, and the feedback network is used for generating a positive feedback signal;
The window comparator comprises a resistor group, a first comparator and a second comparator, wherein the resistor group is used for dividing a power supply voltage to obtain a first threshold voltage and a second threshold voltage, the first threshold voltage is connected with a positive phase end of the first comparator, the second threshold voltage is connected with a negative phase end of the second comparator, the negative phase end of the first comparator is connected with the positive phase end of the second comparator and is connected to one end of the capacitor, the resistor group is used for monitoring voltage change of the second node and generating a trigger signal when the voltage of the second node exceeds a threshold value, the outputs of the first comparator and the second comparator are respectively connected to a 0 end and a 1 end of the RS trigger, and the output of the RS trigger is connected to the digital drive;
the digital driver is connected with one end of the resistor in the feedback network through a first node and is used for driving the feedback network;
the window comparator is also used for monitoring voltage change in the feedback network and generating a control signal for triggering the RS trigger so as to generate a positive feedback square wave signal;
The digital drive is used for converting square wave signals into control signals of the drive circuit;
The driving circuit and the filtering circuit are used for generating driving signals to match the working frequency of the ultrasonic transducer;
The current sensing circuit is used for detecting the motion state of the ultrasonic transducer and feeding back the sensing current to the multivibrator circuit.
In an embodiment of the present application, the first threshold voltage is two-thirds of the power supply voltage, and the second threshold voltage is one-third of the power supply voltage.
In an embodiment of the application, the filtering circuit comprises an LC matching network for filtering the output signal of the driving circuit to form the driving signal of the ultrasonic transducer by removing harmonic components in the output signal.
In an embodiment of the application, the fundamental frequency of the multivibrator circuit is the same as the excitation frequency of the ultrasonic transducer.
In an embodiment of the application, the current sensing circuit further comprises a differential variable bridge circuit for detecting current fluctuations in the ultrasonic transducer and inputting the current fluctuations as a feedback signal to the multivibrator circuit.
In an embodiment of the present application, the RS flip-flop includes two input terminals and one output terminal, which are respectively used for receiving the output signal of the window comparator and driving the digitally driven signal, and the RS flip-flop implements phase synchronization by locking the feedback signal.
In an embodiment of the present application, the resistor in the feedback network is an adjustable resistor, the capacitor is an adjustable capacitor, and the feedback network realizes frequency matching and feedback adjustment according to the working frequency of the ultrasonic transducer.
In an embodiment of the present application, the current sensing circuit is configured to input a feedback current to the second node to achieve phase locking.
In a second aspect, an embodiment of the present application provides an ultrasonic power supply, a current negative feedback phase-locked oscillating circuit for an ultrasonic power supply, a dc power supply, a driving circuit, and a filtering circuit.
In a third aspect, an embodiment of the present application provides an electronic device, including an ultrasonic power supply and an ultrasonic transducer as described in the second aspect.
The embodiment of the application has the beneficial effects that the current of the ultrasonic transducer is induced and is input into the feedback network of the multivibrator circuit, so that the current negative feedback control is introduced into the self-oscillation positive feedback circuit. The ultrasonic transducer is incorporated into a feedback loop to realize phase locking, so that the output frequency of the self-oscillation circuit is stabilized, and the sensitivity of the circuit to system parameter deviation and temperature variation is reduced.
Detailed Description
In order to make the technical problems, technical schemes and beneficial effects to be solved more clear, the application is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the application.
The ultrasonic power supply, namely the ultrasonic generator, is a key component of various ultrasonic equipment and is widely applied to the fields of ultrasonic motors, ultrasonic cleaning, ultrasonic welding, ultrasonic processing and the like. The main function of the ultrasonic transducer is to provide electric energy for the ultrasonic transducer, so that most of the input electric power is converted into regular mechanical vibration, namely ultrasonic wave. However, since the ultrasonic transducer has complicated piezoelectric characteristics such as frequency characteristics, impedance characteristics, mechanical quality factors, temperature characteristics, etc., particularly when the load and temperature are drastically changed, transducer parameters may be changed, resulting in impedance changes and resonance frequency drift, thereby affecting the operation efficiency and stability of the system.
Currently, in order to ensure stable operation of an ultrasonic transducer, a phase-locked loop circuit is generally required to lock the output voltage and current. However, the complexity of the existing phase-locked loop circuit is high, which results in a large circuit size and affects the miniaturization and portability of the ultrasonic power supply.
Therefore, a current negative feedback phase-locked oscillation circuit for an ultrasonic power supply, an ultrasonic power supply and an electronic device are provided, and current negative feedback control is introduced into a self-oscillation positive feedback circuit by inducing the current of an ultrasonic transducer and inputting the current into a feedback network of a multivibrator circuit. The ultrasonic transducer is incorporated into a feedback loop to realize phase locking, so that the output frequency of the self-oscillation circuit is stabilized, and the sensitivity of the circuit to system parameter deviation and temperature variation is reduced.
Fig. 1 is a schematic diagram of a current negative feedback lock phase-locked oscillation circuit according to an embodiment of the present application. As shown in fig. 1, the current negative feedback lock phase locked oscillation circuit 100 includes a multivibrator circuit 110 and a current sensing circuit 120. Multivibrator circuit 110 is connected to dc power supply 200 and current sensing circuit 120, current sensing circuit 120 is connected to ultrasonic transducer 500, and multivibrator circuit 110 is connected to driving circuit 300, filter circuit 400, and ultrasonic transducer 500 in this order.
In an embodiment of the present application, the current negative feedback phase-locked oscillation circuit 100 includes a multivibrator circuit 110 and a current sensing circuit 120. The multivibrator circuit 110 receives a dc signal and converts it into a high-frequency oscillation signal through connection to the dc power supply 200. This oscillation signal is processed by the driving circuit 300 and the filtering circuit 400 to finally drive the ultrasonic transducer 500 to generate an efficient ultrasonic output.
In the embodiment of the present application, the current sensing circuit 120 is used for monitoring the operation state of the ultrasonic transducer 500 in real time, and particularly monitoring the current fluctuation generated by the ultrasonic transducer 500. The current sensing circuit 120 can feed back the detected current signal to the multivibrator circuit 110, causing the multivibrator circuit 110 to adjust its output frequency, thereby achieving frequency locking. Specifically, as the load of the ultrasonic transducer 500 changes, the current sensing circuit 120 will capture these changes and feed back the sensed current to the multivibrator circuit 110, ensuring that the ultrasonic transducer 500 remains at the preferred operating frequency.
Through the current negative feedback mechanism, the system can automatically adapt to the frequency change of the ultrasonic transducer 500, and larger frequency deviation caused by load fluctuation is avoided, so that stable phase-locked control is realized. The reliability of the system and the efficiency of the ultrasonic transducer 500 are improved, so that the ultrasonic transducer 500 can maintain the optimal working state under different load conditions.
Referring to fig. 4, a schematic diagram of a current negative feedback lock phase-locked oscillation circuit according to an embodiment of the present application is shown. As shown in fig. 4, multivibrator circuit 110 includes feedback network 111, window comparator 112, RS flip-flop 113, and digital drive 114.
In the embodiment of the present application, the multivibrator circuit 110 is connected to the driving circuit 300, and the multivibrator circuit 110 is used for converting the dc signal provided by the dc power supply 200 into a high-frequency oscillation signal. Multivibrator circuit 110 is also used to drive filter circuit 400. Specifically, the oscillator in multivibrator circuit 110 drives ultrasonic transducer 500 by modulating the dc signal to a high frequency ac signal, and filter circuit 400 is used to eliminate the excessive high frequency noise, ensuring that the system maintains a stable and efficient ultrasonic output during operation.
In the embodiment of the present application, the feedback network 111 includes a resistor R and a capacitor C, one end of the resistor R is connected to one end of the capacitor C, one end of the resistor R is further connected to the output end of the current sensing circuit 120 and the second node VCT, the other end of the resistor R and the output of the digital driver 114 are connected to the first node VRT, the other end of the capacitor C is grounded, and the feedback network 111 is used for generating a positive feedback signal. Specifically, when the current sensing circuit 120 detects a state change of the ultrasonic transducer 500, the feedback network 111 adjusts the change signal to a positive feedback signal, thereby affecting the oscillation frequency to ensure that the entire system remains in a phase-locked state. The resistor R and the capacitor C are selected to adjust the response speed and the frequency characteristic of the feedback signal.
In an embodiment of the present application, the window comparator 112 includes a resistor group, a first comparator, and a second comparator. The resistor group is used for dividing the power supply voltage to obtain a first threshold voltage and a second threshold voltage. The first threshold voltage is connected with the positive phase end of the first comparator, and the second threshold voltage is connected with the negative phase end of the second comparator. The negative phase end of the first comparator is connected with the positive phase end of the second comparator and is connected to one end of the capacitor C, and the negative phase end of the first comparator is used for monitoring the change of the voltage of the second node VCT and generating a trigger signal when the voltage of the second node VCT exceeds a threshold value. The outputs of the first comparator and the second comparator are connected to the 0-set terminal and the 1-set terminal of the RS flip-flop 113, respectively, and the output of the RS flip-flop 113 is connected to the digital driver 114. Specifically, when the voltage of the second node VCT exceeds the set threshold, the window comparator 112 generates a corresponding trigger signal to control the state of the RS flip-flop 113 by comparing the first and second threshold voltages, and further drives the digital driver 114 to change the operating state of the system.
In the embodiment of the application, the first threshold voltage is two-thirds of the power supply voltage VCC, and the second threshold voltage is one-third of the power supply voltage VCC. Specifically, since three resistors in the resistor group in the window comparator 112 have equal resistance values, the first voltage threshold is two-thirds of the power supply voltage VCC, and the second voltage threshold is one-third of the power supply voltage VCC. It can be understood that the voltage division mechanism is implemented through a resistor group, so that the window comparator 112 can divide the power supply voltage in a fixed proportion, so that the circuit can accurately detect different voltage critical points to judge the charge and discharge states of the capacitor C, and the phase locking precision is ensured.
Specifically, the digital driver 114 receives the square wave signal from the RS flip-flop 113, and feeds back a control signal to the feedback network 111 through the first node VRT node to adjust the strength and frequency of the positive feedback signal, thereby implementing control over the multivibrator circuit 110.
In the embodiment of the present application, the digital driver 114 is connected to one end of the resistor R in the feedback network 111 through the first node VRT. Digital drive 114 is used to drive the feedback network. Specifically, the digital driver 114 receives the square wave signal from the RS flip-flop 113 and feeds back a control signal to the feedback network 111 through the VRT node to adjust the strength and frequency of the positive feedback signal, thereby achieving control over the multivibrator circuit 110.
In the embodiment of the present application, the window comparator 112 is further configured to monitor the voltage variation in the feedback network 111 and generate a control signal for triggering the RS flip-flop to generate a positive feedback square wave signal. Specifically, window comparator 112 will continually monitor voltage fluctuations in the feedback network. When the voltage of the feedback network is detected to reach the set threshold value, the feedback network generates a trigger signal to enable the RS trigger 113 to switch states and generate a positive feedback square wave signal to ensure that the oscillating circuit is phase-locked in a required frequency range.
In an embodiment of the present application, the digital driver 114 is used to convert a square wave signal into a control signal for the driver circuit 300. Specifically, the digital driver 114 further modulates the positive feedback square wave signal output by the RS flip-flop 113 into a driving signal, and inputs the driving signal to the feedback network 111, and meanwhile, the positive feedback square wave signal is sent to the driving circuit 300, and the driving circuit 300 generates a corresponding power signal according to the positive feedback square wave signal to match the working frequency of the ultrasonic transducer 500, so that the system maintains in a high-efficiency working state.
In an embodiment of the present application, the driving circuit 300 and the filtering circuit 400 are used to generate driving signals to match the operating frequency of the ultrasonic transducer 500. Specifically, the driving circuit 300 outputs a signal corresponding to the resonance frequency of the ultrasonic transducer 500 by power amplification and modulation based on the high-frequency oscillation signal generated by the multivibrator circuit 110. The filtering circuit 400 filters the driving signal through the LC matching network to remove unwanted higher harmonics and noise, so as to ensure that the output driving signal is pure and the frequency of the driving signal is exactly matched with the working frequency of the ultrasonic transducer, thereby improving the transmission efficiency and the working stability of the system.
In an embodiment of the present application, the current sensing circuit 120 is configured to detect a motion state of the ultrasonic transducer and feedback the sensed current to the multivibrator circuit 110. Specifically, the current sensing circuit 120 obtains the motion state information of the ultrasonic transducer 500, such as displacement, speed or load change, by detecting the current change generated during operation of the transducer in real time. The induced current is input as a feedback signal to the multivibrator circuit 110 for adjusting the oscillation frequency and phase, thereby implementing closed-loop control of the system, ensuring that the system maintains a phase-locked state under various conditions, and avoiding frequency drift or efficiency degradation.
In an embodiment of the present application, the filtering circuit 400 includes an LC matching network, which is used to filter the output signal of the driving circuit 300, and remove harmonic components in the output signal to form the driving signal of the ultrasonic transducer. Specifically, the LC matching network selectively filters unnecessary high-frequency components through resonance characteristics of the inductor and the capacitor, reserves fundamental frequency signals required by the ultrasonic transducer, ensures that output driving signals are pure and stable, and improves the efficiency and reliability of the system.
In an embodiment of the present application, the fundamental frequency of multivibrator circuit 110 is the same as the excitation frequency of ultrasonic transducer 500. Specifically, the multivibrator circuit 110 is designed with the natural frequency of the ultrasonic transducer taken into consideration, and by adjusting the oscillation frequency to match with the excitation frequency of the transducer, efficient energy transfer is achieved, so that the transducer can generate ultrasonic waves at the optimal working frequency.
In an embodiment of the present application, the current sensing circuit 120 further includes a differential variable bridge circuit for detecting current fluctuations in the ultrasonic transducer and inputting the current fluctuations as a feedback signal to the multivibrator circuit. Specifically, the differential variable bridge circuit can accurately detect the current change of the ultrasonic transducer during working, particularly when the load fluctuates or the environmental condition changes, the current sensing circuit transmits the current fluctuation to the multivibrator circuit through the feedback signal, and the working state of the circuit is adjusted in real time, so that the stability of the system is maintained.
In the embodiment of the present application, the RS flip-flop 113 includes two input terminals and one output terminal, which are respectively used for receiving the output signal of the window comparator and the signal for driving the digital driving, and the RS flip-flop 113 performs phase synchronization by locking the feedback signal. Specifically, the RS flip-flop 113 ensures that the digital drive can switch states at appropriate times by synchronously controlling the phase change of the feedback signal according to the input signal from the window comparator, thereby realizing stable phase locking of the multivibrator circuit and ensuring that the system always operates at an appropriate phase.
In the embodiment of the present application, the resistor R in the feedback network 111 is an adjustable resistor, the capacitor C is an adjustable capacitor, and the feedback network realizes frequency matching and feedback adjustment according to the working frequency of the ultrasonic transducer. Specifically, by adjusting the values of the resistor R and the capacitor C, the feedback network can dynamically adjust the amplitude and the phase of the feedback signal to match the working frequency of the ultrasonic transducer, so that the frequency automatic tracking is realized, and the system can still keep phase locking stable under different working conditions.
In the embodiment of the application, the current sensing circuit is used for inputting feedback current to the second node so as to realize phase locking. Specifically, the current sensing circuit detects the operating state of the ultrasonic transducer and transmits current information to the second node of the multivibrator circuit through a feedback signal. The feedback signal is used for adjusting the oscillation frequency of the system, so that the oscillation circuit can timely adjust the frequency according to the actual working condition of the transducer, the phase-locked state is maintained, and the high-efficiency and stable operation of the system is ensured.
Referring to fig. 4 together, the ultrasonic transducer 500 shown in fig. 4 is an equivalent circuit of a piezoelectric ultrasonic transducer. Specifically, the equivalent circuit of the piezoelectric ultrasonic transducer 500 shown in fig. 4 is composed of four elements including an inductance Lm, a capacitance Cm, a resistance Rm, and a capacitance CP. The inductor Lm, the capacitor Cm, the resistor Rm, and the capacitor CP are connected in series to form a dynamic branch, and the capacitor CP forms a static branch and is connected in parallel to the dynamic branch. It will be appreciated that piezoelectric ultrasonic transducers are merely provided as an example of embodiments of the present application, and those skilled in the art may use, for example, piezoelectric ceramic transducers, electromagnetic ultrasonic transducers, or Capacitive Micromachined Ultrasonic Transducers (CMUTs), which may be selectively used according to different application scenarios, and the present application is not limited thereto.
It is understood that inductance Lm represents the inertial properties of the mechanical vibrations of the transducer. Since the piezoelectric transducer, when driven by an electrical signal, produces mechanical vibrations, the inductance is used to simulate the inertial behavior of the vibrating system. Capacitance Cm represents elasticity in the mechanical system, simulating the energy storage capability of the piezoelectric transducer. During vibration, the system stores mechanical energy, and the capacitor Cm is the equivalent capacitor of this energy storage characteristic. The resistor Rm represents the energy loss of the system, simulates the energy loss of the transducer caused by friction, heat loss and other reasons in the working process, and is mainly reflected in the attenuation of mechanical vibration. Capacitance CP represents the static capacitance in the transducer, which is used to simulate the electrical characteristics of the transducer in the absence of mechanical motion. This is the capacitance value between the transducer electrodes, independent of the dynamic vibration characteristics.
It is understood that the inductance Lm, the capacitance Cm, the resistance Rm, and the capacitance CP are connected in series, reflecting the dynamic vibration characteristics of the piezoelectric ultrasonic transducer. And the capacitor CP in the static branch is connected in parallel with the dynamic branch and is used for simulating the electrical behavior of the transducer in the absence of mechanical vibration. The dynamic branch mainly affects the working frequency and power transfer efficiency of the transducer, while the static branch affects the static capacitance of the system.
According to the application, through the combination of the equivalent elements, the response behaviors of the piezoelectric ultrasonic transducer under different frequencies can be accurately simulated, and then the power supply driving circuit can be optimized according to the equivalent model of the circuit, so that the ultrasonic transducer 500 can be ensured to work in an optimal state.
Fig. 5a and 5b are schematic waveforms of the feedback network provided by the embodiment of the present application under different feedback current conditions. The possible operating states of the feedback network 111 at different feedback currents iF are shown. Wherein a represents the change in the initial phase of the feedback current iF.
The steady state of the circuit is analyzed as follows.
It will be appreciated that the operational state of the circuit under 5 different phase currents iF conditions are shown in fig. 5a and 5b, including iF,0、iF,1、iF,2、iF,3、iF,4、iF,5. In the case of the current iF,0, the charge-discharge current iR＝iC of the capacitor C, and thus iF =0 corresponds to the case of a typical multivibrator circuit.
Where T is an oscillation period, and the expression thereof is t=2 RClog (2).
Fourier analysis is performed on (1), and the fundamental wave and harmonic distribution of the current iC can be obtained as follows:
It will be appreciated that the fundamental amplitude of iC dominates, the odd harmonics are significant, and the even harmonics approach zero. Substituting the parameters VCC =12v, r=7.8kΩ, c=2.2 nF gives the fundamental amplitudes of iC approximately 2.94 times, 4.89 times, 6.84 times, and 8.79 times the 3,5, 7, and 9 harmonics. Therefore, the case of the fundamental wave iC is mainly considered in the analysis, and the fundamental wave of iC is denoted as iC,1.
When the feedback current iF is added at the second node VCT, the frequency change of the circuit depends on the phase of the feedback current since the charge-discharge current of iR≠iC,iC will become iC＝iR+iF. Discussion is made according to the case of different initial phases of feedback current:
IF,1, when the initial phase of iF,1 is consistent with the fundamental frequency current iC,1 of the multivibrator, that is, θ=0, the charge-discharge current of the capacitor C increases, and the time for the voltage to reach the threshold is shortened, so that the oscillation frequency is increased. The waveform of the feedback current is in phase with the charge-discharge current of the capacitor C, and the positive feedback effect is strongest. Since iF increases the charge-discharge current to the capacitor, which means that the capacitor C reaches the first threshold and the second threshold voltage faster in each period, the frequency of the oscillator increases.
IF,2, at this time, the initial phase of iF,2 is delayed by 90 ° backward relative to the initial phase of iF,1, that is, when θ=pi/2, the injected and extracted currents cancel each other, so that the oscillation frequency remains unchanged and reaches a steady state. Since the injection and extraction currents of iF are substantially equal in each cycle, their effects on the charge and discharge process of capacitor C cancel each other out. This situation is similar to no obvious positive or negative feedback. The oscillator frequency remains substantially unchanged and the circuit is in steady state operation.
IF,3, at this time, the initial phase of iF,2 is delayed by 180 ° backward relative to the initial phase of iF,1, that is, when θ=pi, the charge-discharge current of the capacitor C is reduced, and the time for reaching the threshold is prolonged, thereby reducing the oscillation frequency. At this time, the feedback current is opposite to the capacitor charge-discharge current. Since iF is opposite to the charge-discharge current iC of the capacitor, the negative feedback effect is obvious. The feedback current counteracts the charge-discharge current of a portion of the capacitor, resulting in the capacitor voltage reaching the first threshold and the second threshold voltage more slowly. The frequency of the oscillator is lower than that of the circuit without feedback current, the oscillation period of the circuit is prolonged, and the oscillation frequency is reduced.
IF,4, where the initial phase of iF,2 is delayed back by 270 ° relative to the initial phase of iF,1, i.e., θ=3pi/2, the circuit can reach steady state similarly to iF,2. The phase of the feedback current is orthogonal to the capacitor charge-discharge current again, but contrary to the case of iF,2, the injection and extraction currents of the feedback current iF in each period cancel each other, so the oscillation frequency of the circuit is not significantly affected. The circuit remains in steady state operation with an oscillation frequency consistent with the typical multivibrator circuit frequency.
It can be seen that the feedback currents iF of different initial phases affect the frequency variation of the multivibrator circuit. The oscillation frequency increases when the initial phase is 0< theta < pi/2, and decreases when pi/2 < theta < pi. Similarly, at pi < theta <3 pi/2, the frequency continues to decrease, while at 3 pi/2 < theta <2 pi, the frequency increases.
In an embodiment of the application, a steady state solution of the circuit occurs atAndThe two phase points can realize phase locking under the action of negative feedback, so that the oscillation frequency is stabilized. By injecting a suitable feedback current iF into the second VCT, the circuit can be automatically adjusted to a steady state, and phase-locked control is realized.
It can be understood that the oscillation frequency f of the current negative feedback phase-locked oscillating circuit 100 for an ultrasonic power supply provided in the embodiment of the present application has only two steady-state solutions, namelyAndTherefore, when the phase or oscillation frequency of the ultrasonic transducer is shifted, the current sensing circuit can timely detect and inject a feedback signal into the multivibrator circuit, so that the circuit can quickly adjust the return-to-steady frequency. The design can effectively improve the anti-interference capability and stability of the circuit, ensure that the ultrasonic transducer can keep better working frequency under different working conditions, and realize efficient energy transfer.
Fig. 2 is a schematic diagram of an ultrasonic power module according to an embodiment of the present application. As shown in fig. 2, the ultrasonic power supply 10 includes a current negative feedback lock phase-locked oscillation circuit 100, a dc power supply 200, a driving circuit 300, and a filter circuit 400. The ultrasonic power supply 10 is connected to the ultrasonic transducer 500.
In the embodiment of the application, the current negative feedback phase-locked oscillation circuit 100 in the ultrasonic power supply 10 and the ultrasonic transducer 500 realize frequency locking through the feedback circuit, so that the ultrasonic power supply 10 can adjust the output frequency in real time, ensure the matching with the resonant frequency of the ultrasonic transducer, and further improve the energy transfer efficiency. The dc power supply 200 provides a basic dc voltage to the circuit, and the driving circuit 300 modulates and filters the dc signal through the filtering circuit 400 to generate a suitable high frequency signal to drive the ultrasonic transducer 500 to generate the desired ultrasonic wave.
Fig. 3 is a schematic diagram of an electronic device module according to an embodiment of the present application. As shown in fig. 3, the electronic device 20 includes the ultrasonic power supply 10 and the ultrasonic transducer 500 as shown in fig. 2.
In the embodiment of the application, the electronic equipment 20 realizes the efficient driving and control of the ultrasonic transducer by optimizing the design of the power supply module, and ensures the stable operation under the complex working environment. In addition, through the design of current negative feedback, equipment can monitor ultrasonic transducer's operating condition in real time, carries out automatically regulated to improve the work efficiency and the life of system.
The current negative feedback phase-locked oscillating circuit 100 for the ultrasonic power supply, the ultrasonic power supply 10 and the ultrasonic transducer 500 provided by the application do not need external manual adjustment through the introduction of negative feedback. When the load or working condition of the ultrasonic transducer changes, the current sensing circuit can detect corresponding current fluctuation, and the oscillation frequency is adjusted through the feedback network, so that the system automatically recovers to a steady state solution. The design simplifies the control structure of the circuit, enhances the self-adaptability and response speed of the circuit, effectively improves the working efficiency and reliability of the ultrasonic power supply, and is suitable for various ultrasonic application scenes.
It will be apparent to those skilled in the art that, for convenience and brevity of description, only the above-described division of each functional module and module is illustrated, and in practical application, the above-described functional allocation may be performed by different functional modules and modules according to needs, i.e. the internal structure of the apparatus is divided into different functional modules or modules to perform all or part of the above-described functions. The functional modules and the modules in the embodiment can be integrated in one processing module, or each module can exist alone physically, or two or more modules can be integrated in one module, and the integrated modules can be realized in a form of hardware or a form of a software functional module. In addition, the specific names of the functional modules and the modules are only for convenience of distinguishing each other, and are not used for limiting the protection scope of the application.
In the foregoing embodiments, the descriptions of the embodiments are emphasized, and in part, not described or illustrated in any particular embodiment, reference is made to the related descriptions of other embodiments.
The foregoing embodiments are merely illustrative of the technical solutions of the present application, and not restrictive, and although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those skilled in the art that modifications may still be made to the technical solutions described in the foregoing embodiments or equivalent substitutions of some technical features thereof, and that such modifications or substitutions do not depart from the spirit and scope of the technical solutions of the embodiments of the present application.