技术领域Technical field
本发明涉及电力电子和半导体器件的设置和控制技术领域，具体涉及一种基于频率自适应移相调制控制的效率最优控制方法及系统。The present invention relates to the technical field of setting and control of power electronics and semiconductor devices, and in particular to an efficiency optimal control method and system based on frequency adaptive phase-shift modulation control.
背景技术Background technique
由于一次侧开关可以实现零电压开关(ZVS Zero Voltage Switch)，二次侧开关可以实现零电流开关(ZCS Zero Current Switch)， LLC谐振变换器引起了人们的强烈兴趣。它具有高效率、高功率密度、低电磁干扰等优点。因此，LLC谐振变换器广泛应用于新能源领域。对于传统的LLC变换器，当工作在谐振频率时，可以通过软开关实现高效率。然而，在宽电压增益应用中，开关频率远离谐振点，导致较大的循环电流损耗和效率降低。此外，在大电流应用中，单相LLC谐振变换器往往需要通过并联更多开关器件或采用大额定电流的无源器件来解决电流应力过大的问题。但是，这可能会引起一些问题，如系统的散热、设备的电流共享和可靠性问题。并联LLC谐振变换器具有电压应力和电流应力小、效率高、电流纹波小等优点，是解决这些问题的理想方案。Since the primary side switch can realize zero voltage switching (ZVS Zero Voltage Switch) and the secondary side switch can realize zero current switching (ZCS Zero Current Switch), LLC resonant converter has aroused strong interest. It has the advantages of high efficiency, high power density, and low electromagnetic interference. Therefore, LLC resonant converters are widely used in new energy fields. For traditional LLC converters, high efficiency can be achieved through soft switching when operating at the resonant frequency. However, in wide voltage gain applications, the switching frequency is far from the resonance point, resulting in larger circulating current losses and reduced efficiency. In addition, in high-current applications, single-phase LLC resonant converters often need to solve the problem of excessive current stress by connecting more switching devices in parallel or using passive devices with large rated currents. However, this may cause issues such as system cooling, device current sharing, and reliability issues. The parallel LLC resonant converter has the advantages of small voltage stress and current stress, high efficiency, and small current ripple, and is an ideal solution to solve these problems.
对于变换器而言，降低成本一直是需要被关注的。而传统的并联LLC谐振变换器存在成本较高的不足，因此，采用LLC变换器和有源桥式并联的混合LLC变换器是一个很好的选择，有效的减少了无源器件的数量，并且通过采用Si基功率器件和SiC 基功率器件混合桥臂的方法，有效的减少了变换器的成本。然而，混合LLC变换器在应用于宽电压范围的应用场景时，存在电压增益范围不够大的不足。此外，由于Si 基功率器件的损耗比SiC 基功率器件大，因此需要采用一种新的控制方法，通过控制流过Si基功率器件和SiC 基功率器件的电流，降低变换器的损耗。For converters, cost reduction has always been a concern. The traditional parallel LLC resonant converter has the disadvantage of higher cost. Therefore, a hybrid LLC converter using an LLC converter and an active bridge parallel connection is a good choice, which effectively reduces the number of passive components and By using a hybrid bridge arm method of Si-based power devices and SiC-based power devices, the cost of the converter is effectively reduced. However, when the hybrid LLC converter is used in a wide voltage range application scenario, the voltage gain range is not large enough. In addition, since the losses of Si-based power devices are larger than those of SiC-based power devices, a new control method needs to be adopted to reduce the losses of the converter by controlling the current flowing through Si-based power devices and SiC-based power devices.
发明内容Contents of the invention
有鉴于此，为了解决现有技术中的上述问题，本申请提出了一种基于频率自适应移相调制控制的效率最优控制方法及系统。In view of this, in order to solve the above-mentioned problems in the prior art, this application proposes an efficiency optimal control method and system based on frequency adaptive phase-shift modulation control.
本申请通过以下技术手段解决上述问题：This application solves the above problems through the following technical means:
本申请第一方面提供一种基于频率自适应移相调制控制的效率最优控制方法，包括如下步骤：The first aspect of this application provides an efficiency optimal control method based on frequency adaptive phase shift modulation control, which includes the following steps:
步骤S100、基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程；Step S100: Establish an equivalent model based on the circuit structure of the LLC resonant part and the auxiliary bridge part of the converter, and establish constraint equations through the relationship between the input voltage, input current, output voltage and output current of the converter;
步骤S200、将变换器电路中的LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量带入所述约束方程，得出变换器的归一化直流电压增益的表达式；Step S200: Bring the fundamental wave component of the LLC resonant part input voltage, the fundamental wave component of the auxiliary bridge part input voltage, the fundamental wave component of the converter output voltage, and the fundamental wave component of the converter output current in the converter circuit into the converter circuit. The above constraint equation is used to obtain the expression of the normalized DC voltage gain of the converter;
步骤S300、将LLC谐振部分及辅助桥式部分的电能参数带入所述变换器的归一化直流电压增益的表达式，求解出变换器的归一化直流电压增益；Step S300: Bring the electric energy parameters of the LLC resonant part and the auxiliary bridge part into the expression of the normalized DC voltage gain of the converter, and solve for the normalized DC voltage gain of the converter;
步骤S400、通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度。Step S400: By applying an intelligent optimization algorithm, while maintaining the normalized DC voltage gain of the converter unchanged, find the frequency and phase shift angle with optimal converter efficiency.
进一步的，所述基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程，包含以下步骤：Further, the equivalent model is established based on the circuit structure of the LLC resonant part and the auxiliary bridge part of the converter, and the constraint equation is established through the relationship between the input voltage, input current, output voltage and output current of the converter, including the following steps :
变换器分为LLC谐振部分和辅助桥式部分，由此可以得到四个约束方程:The converter is divided into LLC resonance part and auxiliary bridge part, from which four constraint equations can be obtained:
； ;
式中，uAB为LLC谐振部分的输入电压，ir1为LLC谐振部分的输入电流，Lr为谐振电感，j为复数单位，ω为角谐振频率，Cr为谐振电容，is为二次侧的电流，n1为LLC谐振部分的变压器变比，Lm1为变压器Tr1的励磁电感，uAC为辅助桥式部分的输入电压，ir2为辅助桥式部分的输入电流，n2为辅助桥式部分的变压器变比，Lm2为变压器Tr2的励磁电感，uo1为LLC谐振部分的二次侧变压器电压，uo2为辅助桥式部分的二次侧变压器电压，uo为输出电压。In the formula, uAB is the input voltage of the LLC resonant part, ir1 is the input current of the LLC resonant part, Lr is the resonant inductance, j is the complex unit, ω is the angular resonant frequency, Cr is the resonant capacitance, and is is two The current on the secondary side, n1 is the transformer ratio of the LLC resonant part, Lm1 is the excitation inductance of the transformer Tr1 , uAC is the input voltage of the auxiliary bridge part, ir2 is the input current of the auxiliary bridge part, n2 is the transformer ratio of the auxiliary bridge part, Lm2 is the excitation inductance of the transformer Tr2 , uo1 is the secondary side transformer voltage of the LLC resonant part, uo2 is the secondary side transformer voltage of the auxiliary bridge part, uo is The output voltage.
进一步的，所述LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量，表达式包含：Further, the expressions of the fundamental component of the input voltage of the LLC resonant part, the fundamental component of the input voltage of the auxiliary bridge part, the fundamental component of the converter output voltage and the fundamental component of the converter output current include:
； ;
式中，φ1为uAC(t)超前的相位差，φ2为谐振槽输入电压uAB与LLC谐振部分变压器二次侧输出电压uo1之间的相位差，/>为电压UAB的基波分量，Uin为输入电压，为电压uAC的基波分量，is为变压器二次侧的输出电流，/>为is的基波分量，IO为输出电流，UO为输出电压，ωs为开关频率fs的角频率，t为时间函数，D为占空比,/>为输出电压UO的交流分量。In the formula, φ1 is uAC (t) leading Phase difference, φ2 is the phase difference between the resonant tank input voltage uAB and the LLC resonant part transformer secondary side output voltage uo1 , /> is the fundamental component of voltage UAB , Uin is the input voltage, is the fundamental component of voltage uAC , is is the output current on the secondary side of the transformer,/> is the fundamental wave component of is , IO is the output current, UO is the output voltage, ωs is the angular frequency of the switching frequency fs , t is the time function, and D is the duty cycle,/> is the AC component of the output voltage UO.
进一步的，所述变换器的归一化直流电压增益的表达式，包含：Further, the expression of the normalized DC voltage gain of the converter includes:
将变换器电路中的电压、电流变量的基波分量带入所述约束方程，变换器的归一化直流电压增益可表示为:Bringing the fundamental components of the voltage and current variables in the converter circuit into the constraint equation, the normalized DC voltage gain of the converter can be expressed as:
； ;
其中，为谐振变换器的品质因子，RO为输出电阻，fn为归一化开关频率（fn=fs/fr），fs为开关频率，fr为谐振频率, m为电感Lm1和电感Lr之间的比率。in, is the quality factor of the resonant converter, RO is the output resistance, fn is the normalized switching frequency (fn =fs /fr ), fs is the switching frequency,fr is the resonant frequency, m is the inductor Lm1 and the ratio between inductance Lr .
进一步的，所述变换器可根据预设的频率和移相角来实现在0.5至2.0间的电压增益变化范围。Furthermore, the converter can achieve a voltage gain variation range between 0.5 and 2.0 according to the preset frequency and phase shift angle.
进一步的，所述通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度，包含以下步骤：Further, by applying an intelligent optimization algorithm, while maintaining the normalized DC voltage gain of the converter unchanged, finding the frequency and phase shift angle with optimal converter efficiency includes the following steps:
步骤S401通过预设定的频率控制和相位角控制实现电压增益的初始调整；Step S401 realizes the initial adjustment of voltage gain through preset frequency control and phase angle control;
步骤S402计算当前变换器的效率，通过智能算法确定最优移相角度，并计算所述最优移相角度下的变换器的新效率；Step S402 calculates the efficiency of the current converter, determines the optimal phase shift angle through an intelligent algorithm, and calculates the new efficiency of the converter at the optimal phase shift angle;
步骤S403判断更新后的变换器的新效率是否大于更新前的变换器的效率，是则跳转到步骤S404，否则直接跳转到步骤S402；Step S403 determines whether the new efficiency of the updated converter is greater than the efficiency of the converter before the update, if yes, jumps to step S404, otherwise jumps directly to step S402;
步骤S404 应用智能算法确定的最优移相角度,通过调频稳定输出电压，跳转到步骤S402。Step S404 applies the optimal phase shift angle determined by the intelligent algorithm, stabilizes the output voltage through frequency modulation, and jumps to step S402.
进一步的，所述通过预设定的频率控制和相位角控制实现电压增益的初始调整，使用以下其中一种方式控制：移相加调频控制、固定频率移相控制和固定相位角调频控制。Further, the initial adjustment of the voltage gain is achieved through preset frequency control and phase angle control, using one of the following control methods: phase shift plus frequency modulation control, fixed frequency phase shift control, and fixed phase angle frequency modulation control.
进一步的，所述通过预设定的频率控制和相位角控制实现电压增益的初始调整的步骤包含：Further, the step of realizing the initial adjustment of the voltage gain through preset frequency control and phase angle control includes:
根据目标电压增益的数值进行判定，若目标电压增益大于等于0.5且小于1.5，则进行固定频率移相调整至目标电压增益；Determination is based on the value of the target voltage gain. If the target voltage gain is greater than or equal to 0.5 and less than 1.5, then a fixed frequency phase shift is performed to adjust to the target voltage gain;
若目标电压增益大于等于1.5并且小于等于2.0，则进行固定相位角调频控制调整至目标电压增益；If the target voltage gain is greater than or equal to 1.5 and less than or equal to 2.0, perform fixed phase angle frequency modulation control to adjust to the target voltage gain;
若目标电压增益的数值不在前两个判定范围之内，则超出变换器的有效电压增益调整范围，电压增益将调整至有效范围内最接近目标电压增益的数值。If the value of the target voltage gain is not within the first two determination ranges, it exceeds the effective voltage gain adjustment range of the converter, and the voltage gain will be adjusted to the value closest to the target voltage gain within the effective range.
本申请第二方面提供一种基于频率自适应移相调制控制的效率最优控制系统，包括：The second aspect of this application provides an efficiency-optimized control system based on frequency adaptive phase-shift modulation control, including:
第一处理模块，基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程；The first processing module establishes an equivalent model based on the circuit structure of the LLC resonance part and auxiliary bridge part of the converter, and establishes constraint equations through the relationship between the input voltage, input current, output voltage and output current of the converter;
第二处理模块，将变换器电路中的LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量带入所述约束方程，得出变换器的归一化直流电压增益的表达式；The second processing module combines the fundamental wave component of the input voltage of the LLC resonant part in the converter circuit, the fundamental wave component of the input voltage of the auxiliary bridge part, the fundamental wave component of the converter output voltage and the fundamental wave component of the converter output current. Enter the constraint equation to obtain the expression of the normalized DC voltage gain of the converter;
确定模块，将LLC谐振部分及辅助桥式部分的电能参数带入所述变换器的归一化直流电压增益的表达式，求解出变换器的归一化直流电压增益；Determine the module to bring the electric energy parameters of the LLC resonant part and the auxiliary bridge part into the expression of the normalized DC voltage gain of the converter, and solve for the normalized DC voltage gain of the converter;
优化模块，通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度。The optimization module, by applying an intelligent optimization algorithm, finds the frequency and phase shift angle at which the efficiency of the converter is optimal while maintaining the normalized DC voltage gain of the converter unchanged.
与现有技术相比，本发明的有益效果至少包括：Compared with the prior art, the beneficial effects of the present invention at least include:
本发明提供了一种基于频率自适应移相调制控制的效率最优控制方法及系统，通过计算变换器的归一化直流电压增益，利用调频和移相相结合的技术，有效地控制了变换器的工作状态，使其能在一定范围内调节输出电压；引入了智能优化算法以获得最佳的移相角度，保持在输出电压不变的情况下最大化变换器的效率，从而改善系统的性能并降低能源损耗。The present invention provides an efficiency optimal control method and system based on frequency adaptive phase-shift modulation control. By calculating the normalized DC voltage gain of the converter and using the technology of combining frequency modulation and phase-shifting, the conversion is effectively controlled. The working state of the converter allows it to adjust the output voltage within a certain range; an intelligent optimization algorithm is introduced to obtain the best phase shift angle, maximizing the efficiency of the converter while keeping the output voltage constant, thereby improving the system's efficiency. performance and reduce energy consumption.
附图说明Description of drawings
为了更清楚地说明本发明实施例中的技术方案，下面将对实施例描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图。In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the drawings needed to be used in the description of the embodiments will be briefly introduced below. Obviously, the drawings in the following description are only some embodiments of the present invention. For those of ordinary skill in the art, other drawings can also be obtained based on these drawings without exerting creative efforts.
图1是本发明提供的一种Si基功率器件和SiC 基功率器件混合桥臂LLC变换器的电路示意图；Figure 1 is a circuit schematic diagram of a hybrid bridge arm LLC converter of Si-based power devices and SiC-based power devices provided by the present invention;
图2是本发明提供的一种基于频率自适应移相调制控制与对应的电压增益的示意图；Figure 2 is a schematic diagram of a frequency-adaptive phase-shift modulation control and corresponding voltage gain provided by the present invention;
图3是本发明提供的一种基于频率自适应移相调制控制的效率最优控制方法流程图；Figure 3 is a flow chart of an efficiency optimal control method based on frequency adaptive phase-shift modulation control provided by the present invention;
图4是本发明提供的一种应用智能优化算法优化变换器效率的流程图；Figure 4 is a flow chart for optimizing converter efficiency using an intelligent optimization algorithm provided by the present invention;
图5是本发明提供的一种基于频率自适应移相调制控制的效率最优控制系统的示意图。FIG. 5 is a schematic diagram of an efficiency-optimized control system based on frequency adaptive phase-shift modulation control provided by the present invention.
具体实施方式Detailed ways
为使本发明的上述目的、特征和优点能够更加明显易懂，下面将结合附图和具体的实施例对本发明的技术方案进行详细说明。需要指出的是，所描述的实施例仅仅是本发明一部分实施例，而不是全部的实施例，基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。In order to make the above objects, features and advantages of the present invention more obvious and understandable, the technical solutions of the present invention will be described in detail below with reference to the accompanying drawings and specific embodiments. It should be pointed out that the described embodiments are only some of the embodiments of the present invention, rather than all of the embodiments. Based on the embodiments of the present invention, those of ordinary skill in the art can obtain all the results without creative efforts. Other embodiments fall within the protection scope of the present invention.
在本申请中，诸如第一和第二等之类的关系术语仅仅用来将一个实体或者操作与另一个实体或操作区分开来，而不一定要求或者暗示这些实体或操作之间存在任何这种实际的关系或者顺序。而且术语“包括”、“包含”或者其任何其他变体意在涵盖非排他性的包含，从而使得包括一系列要素的过程、方法、物品或者设备不仅包括那些要素，而且还包括没有明确列出的其他要素，或者是还包括为这种过程、方法、物品或者设备所固有的要素。在没有更多限制的情况下，由语句“包括一个……”限定的要素，并不排除在包括所述要素的过程、方法、物品或者设备中还存在另外的相同要素。In this application, relational terms such as first, second, etc. are only used to distinguish one entity or operation from another entity or operation and do not necessarily require or imply the existence of any such entity or operation. an actual relationship or sequence. Furthermore, the terms "comprises," "comprises," or any other variation thereof are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that includes a list of elements includes not only those elements, but also those not expressly listed Other elements, or elements inherent to the process, method, article or equipment. Without further limitation, an element defined by the statement "comprises a..." does not exclude the presence of additional identical elements in a process, method, article, or apparatus that includes the stated element.
本申请涉及的技术名词：Technical terms involved in this application:
LLC是英文 "Inductor-Inductor-Capacitor" 的缩写，中文意思是“电感-电感-电容器”，分别代表了LLC谐振变换器中的三个主要部件：两个串联的电感和一个并联的电容器。这三个部件构成了该设备的基本谐振电路结构。LLC is the abbreviation of "Inductor-Inductor-Capacitor" in English, which means "inductor-inductor-capacitor" in Chinese, which respectively represent the three main components in the LLC resonant converter: two series inductors and a parallel capacitor. These three components form the basic resonant circuit structure of the device.
Si基功率器件是一种以硅（Silicon）为主要材料制造的功率半导体器件，通常包括MOSFET（金属氧化物半导体场效应晶体管）、BJT（双极结型晶体管）、IGBT（绝缘栅双极晶体管）等类型。它们具有高效率、低导通电阻、耐高压等特点，在电源转换、电机控制、汽车电子等领域有着广泛的应用。Si-based power devices are power semiconductor devices made of silicon as the main material, usually including MOSFET (metal oxide semiconductor field effect transistor), BJT (bipolar junction transistor), IGBT (insulated gate bipolar transistor) ) and other types. They have the characteristics of high efficiency, low on-resistance, and high voltage resistance, and are widely used in power conversion, motor control, automotive electronics and other fields.
SiC基功率器件是以碳化硅（Silicon Carbide）为主要材料制造的功率半导体器件，属于第三代半导体。其具有更高的击穿电场强度、更高的饱和电子漂移速度和更低的介电常数等优点，能够在高温、高压、高频等环境下工作，并且可以提高开关频率、降低开关损耗和缩小体积，因此在电力电子领域具有广泛的应用前景。SiC-based power devices are power semiconductor devices made of silicon carbide (Silicon Carbide) as the main material and belong to the third generation of semiconductors. It has the advantages of higher breakdown electric field strength, higher saturated electron drift velocity and lower dielectric constant. It can work in high temperature, high pressure, high frequency and other environments, and can increase switching frequency, reduce switching losses and The size is reduced, so it has broad application prospects in the field of power electronics.
实施例一Embodiment 1
参考图1的Si基功率器件和SiC 基功率器件混合桥臂LLC变换器电路示意图，本申请实施例提供一种基于频率自适应移相调制控制的宽电压增益控制方法，包括如下步骤：Referring to the schematic circuit diagram of a hybrid bridge-arm LLC converter of Si-based power devices and SiC-based power devices in Figure 1, embodiments of the present application provide a wide voltage gain control method based on frequency adaptive phase-shift modulation control, including the following steps:
步骤S100、基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程；Step S100: Establish an equivalent model based on the circuit structure of the LLC resonant part and the auxiliary bridge part of the converter, and establish constraint equations through the relationship between the input voltage, input current, output voltage and output current of the converter;
进一步的，所述基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程，包含以下步骤：Further, the equivalent model is established based on the circuit structure of the LLC resonant part and the auxiliary bridge part of the converter, and the constraint equation is established through the relationship between the input voltage, input current, output voltage and output current of the converter, including the following steps :
变换器分为LLC谐振部分和辅助桥式部分，由此可以得到四个约束方程:The converter is divided into LLC resonance part and auxiliary bridge part, from which four constraint equations can be obtained:
； ;
式中，uAB为LLC谐振部分的输入电压，ir1为LLC谐振部分的输入电流，Lr为谐振电感，j为复数单位，ω为角谐振频率，Cr为谐振电容，is为二次侧的电流，n1为LLC谐振部分的变压器变比，Lm1为变压器Tr1的励磁电感，uAC为辅助桥式部分的输入电压，ir2为辅助桥式部分的输入电流，n2为辅助桥式部分的变压器变比，Lm2为变压器Tr2的励磁电感，uo1为LLC谐振部分的二次侧变压器电压，uo2为辅助桥式部分的二次侧变压器电压，uo为输出电压。In the formula, uAB is the input voltage of the LLC resonant part, ir1 is the input current of the LLC resonant part, Lr is the resonant inductance, j is the complex unit, ω is the angular resonant frequency, Cr is the resonant capacitance, and is is two The current on the secondary side, n1 is the transformer ratio of the LLC resonant part, Lm1 is the excitation inductance of the transformer Tr1 , uAC is the input voltage of the auxiliary bridge part, ir2 is the input current of the auxiliary bridge part, n2 is the transformer ratio of the auxiliary bridge part, Lm2 is the excitation inductance of the transformer Tr2 , uo1 is the secondary side transformer voltage of the LLC resonant part, uo2 is the secondary side transformer voltage of the auxiliary bridge part, uo is The output voltage.
步骤S200、将变换器电路中的LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量带入所述约束方程，得出变换器的归一化直流电压增益的表达式；Step S200: Bring the fundamental wave component of the LLC resonant part input voltage, the fundamental wave component of the auxiliary bridge part input voltage, the fundamental wave component of the converter output voltage, and the fundamental wave component of the converter output current in the converter circuit into the converter circuit. The above constraint equation is used to obtain the expression of the normalized DC voltage gain of the converter;
进一步的，所述LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量，表达式包含：Further, the expressions of the fundamental component of the input voltage of the LLC resonant part, the fundamental component of the input voltage of the auxiliary bridge part, the fundamental component of the converter output voltage and the fundamental component of the converter output current include:
； ;
式中，φ1为uAC(t)超前的相位差，φ2为谐振槽输入电压uAB与LLC谐振部分变压器二次侧输出电压uo1之间的相位差，/>为电压UAB的基波分量，Uin为输入电压，为电压uAC的基波分量，is为变压器二次侧的输出电流，/>为is的基波分量，IO为输出电流，UO为输出电压，ωs为开关频率fs的角频率，t为时间函数，D为占空比,/>为输出电压UO的交流分量。In the formula, φ1 is uAC (t) leading Phase difference, φ2 is the phase difference between the resonant tank input voltage uAB and the LLC resonant part transformer secondary side output voltage uo1 , /> is the fundamental component of voltage UAB , Uin is the input voltage, is the fundamental component of voltage uAC , is is the output current on the secondary side of the transformer,/> is the fundamental wave component of is , IO is the output current, UO is the output voltage, ωs is the angular frequency of the switching frequency fs , t is the time function, and D is the duty cycle,/> is the AC component of the output voltage UO.
进一步的，所述变换器的归一化直流电压增益的表达式，包含：Further, the expression of the normalized DC voltage gain of the converter includes:
将变换器电路中的电压、电流变量的基波分量带入所述约束方程，变换器的归一化直流电压增益可表示为:Bringing the fundamental components of the voltage and current variables in the converter circuit into the constraint equation, the normalized DC voltage gain of the converter can be expressed as:
； ;
其中，为谐振变换器的品质因子，RO为输出电阻，fn为归一化开关频率（fn=fs/fr），fs为开关频率，fr为谐振频率, m为电感Lm1和电感Lr之间的比率。in, is the quality factor of the resonant converter, RO is the output resistance, fn is the normalized switching frequency (fn =fs /fr ), fs is the switching frequency,fr is the resonant frequency, m is the inductance Lm1 and the ratio between inductance Lr .
步骤S300、将LLC谐振部分及辅助桥式部分的电能参数带入所述变换器的归一化直流电压增益的表达式，求解出变换器的归一化直流电压增益；Step S300: Bring the electric energy parameters of the LLC resonant part and the auxiliary bridge part into the expression of the normalized DC voltage gain of the converter, and solve for the normalized DC voltage gain of the converter;
进一步的，所述变换器可根据预设的频率和移相角来实现在0.5至2.0间的电压增益变化范围。Furthermore, the converter can achieve a voltage gain variation range between 0.5 and 2.0 according to the preset frequency and phase shift angle.
进一步的，所述通过预设定的频率控制和相位角控制实现电压增益的初始调整的步骤包含：Further, the step of realizing the initial adjustment of the voltage gain through preset frequency control and phase angle control includes:
根据目标电压增益的数值进行判定，若目标电压增益大于等于0.5且小于1.5，则进行固定频率移相调整至目标电压增益；Determination is based on the value of the target voltage gain. If the target voltage gain is greater than or equal to 0.5 and less than 1.5, then a fixed frequency phase shift is performed to adjust to the target voltage gain;
若目标电压增益大于等于1.5并且小于等于2.0，则进行固定相位角调频控制调整至目标电压增益；If the target voltage gain is greater than or equal to 1.5 and less than or equal to 2.0, perform fixed phase angle frequency modulation control to adjust to the target voltage gain;
若目标电压增益的数值不在前两个判定范围之内，则超出变换器的有效电压增益调整范围，电压增益将调整至有效范围内最接近目标电压增益的数值。If the value of the target voltage gain is not within the first two determination ranges, it exceeds the effective voltage gain adjustment range of the converter, and the voltage gain will be adjusted to the value closest to the target voltage gain within the effective range.
如图2所示，通过采用移相加调频的控制方法，本发明的变换器可以实现从0.5-2.0的电压增益范围。运行轨迹为从A到B，对应着固定频率移相；从B到C，对应着固定相位角调频；可以通过A到B，C到D的策略实现不同的增益，从而实现输出电压的调节，但不是系统效率最优方案；由于可以通过调频加移相调节输出的电压，所以对于同一个输出电压与增益，有不同的调频和移相配比。而不同的相位角导致对应的Si基功率器件和SiC 基功率器件的电流也发生改变，从而产生不同的变换器的效率。As shown in Figure 2, by adopting the control method of phase shift and frequency modulation, the converter of the present invention can achieve a voltage gain range from 0.5 to 2.0. The running trajectory is from A to B, which corresponds to a fixed frequency phase shift; from B to C, which corresponds to a fixed phase angle frequency modulation; different gains can be achieved through the strategies of A to B, C to D, thereby adjusting the output voltage. But it is not the optimal solution for system efficiency; since the output voltage can be adjusted through frequency modulation and phase shift, there are different frequency modulation and phase shift ratios for the same output voltage and gain. Different phase angles cause the currents of the corresponding Si-based power devices and SiC-based power devices to also change, resulting in different converter efficiencies.
步骤S400、通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度。Step S400: By applying an intelligent optimization algorithm, while maintaining the normalized DC voltage gain of the converter unchanged, find the frequency and phase shift angle with optimal converter efficiency.
进一步的，如图3所示，所述通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度，包含以下步骤：Further, as shown in Figure 3, by applying an intelligent optimization algorithm, while maintaining the normalized DC voltage gain of the converter unchanged, the frequency and phase shift angle with optimal converter efficiency are found, including Following steps:
步骤S401通过预设定的频率控制和相位角控制实现电压增益的初始调整；Step S401 realizes the initial adjustment of voltage gain through preset frequency control and phase angle control;
步骤S402计算当前变换器的效率，通过智能算法确定最优移相角度，并计算所述最优移相角度下的变换器的新效率；Step S402 calculates the efficiency of the current converter, determines the optimal phase shift angle through an intelligent algorithm, and calculates the new efficiency of the converter at the optimal phase shift angle;
步骤S403判断更新后的变换器的新效率是否大于更新前的变换器的效率，是则跳转到步骤S404，否则直接跳转到步骤S402；Step S403 determines whether the new efficiency of the updated converter is greater than the efficiency of the converter before the update, if so, jump to step S404, otherwise jump directly to step S402;
步骤S404 应用智能算法确定的最优移相角度,通过调频稳定输出电压，跳转到步骤S402。Step S404 applies the optimal phase shift angle determined by the intelligent algorithm, stabilizes the output voltage through frequency modulation, and jumps to step S402.
进一步的，所述通过预设定的频率控制和相位角控制实现电压增益的初始调整，使用以下其中一种方式控制：移相加调频控制、固定频率移相控制和固定相位角调频控制。Further, the initial adjustment of the voltage gain is achieved through preset frequency control and phase angle control, and is controlled using one of the following methods: phase shift plus frequency modulation control, fixed frequency phase shift control, and fixed phase angle frequency modulation control.
本申请第二方面提供一种基于频率自适应移相调制控制的效率最优控制控制系统，包括：The second aspect of this application provides an efficiency-optimized control system based on frequency adaptive phase-shift modulation control, including:
第一处理模块，基于变换器的LLC谐振部分及辅助桥式部分的电路结构建立等效模型，并通过变换器的输入电压、输入电流、输出电压及输出电流间关系建立约束方程；The first processing module establishes an equivalent model based on the circuit structure of the LLC resonance part and auxiliary bridge part of the converter, and establishes constraint equations through the relationship between the input voltage, input current, output voltage and output current of the converter;
第二处理模块，将变换器电路中的LLC谐振部分输入电压的基波分量、辅助桥式部分输入电压的基波分量、变换器输出电压的基波分量和变换器输出电流的基波分量带入所述约束方程，得出变换器的归一化直流电压增益的表达式；The second processing module combines the fundamental wave component of the input voltage of the LLC resonant part in the converter circuit, the fundamental wave component of the input voltage of the auxiliary bridge part, the fundamental wave component of the converter output voltage and the fundamental wave component of the converter output current. Enter the constraint equation to obtain the expression of the normalized DC voltage gain of the converter;
确定模块，将LLC谐振部分及辅助桥式部分的电能参数带入所述变换器的归一化直流电压增益的表达式，求解出变换器的归一化直流电压增益；Determine the module to bring the electric energy parameters of the LLC resonant part and the auxiliary bridge part into the expression of the normalized DC voltage gain of the converter, and solve for the normalized DC voltage gain of the converter;
优化模块，通过应用智能优化算法，在维持所述变换器归一化直流电压增益不变的情况下，寻得变换器效率最优的频率及移相角度。The optimization module, by applying an intelligent optimization algorithm, finds the frequency and phase shift angle at which the efficiency of the converter is optimal while maintaining the normalized DC voltage gain of the converter unchanged.
与现有技术相比，本发明的有益效果至少包括：Compared with the prior art, the beneficial effects of the present invention at least include:
本发明提供了一种基于频率自适应移相调制控制的效率最优控制方法及系统，通过计算变换器的归一化直流电压增益，利用调频和移相相结合的技术，有效地控制了变换器的工作状态，使其能在一定范围内调节输出电压；引入了智能优化算法以获得最佳的移相角度，保持在输出电压不变的情况下最大化变换器的效率，从而改善系统的性能并降低能源损耗。The present invention provides an efficiency optimal control method and system based on frequency adaptive phase-shift modulation control. By calculating the normalized DC voltage gain of the converter and using the technology of combining frequency modulation and phase-shifting, the conversion is effectively controlled. The working state of the converter allows it to adjust the output voltage within a certain range; an intelligent optimization algorithm is introduced to obtain the best phase shift angle, maximizing the efficiency of the converter while keeping the output voltage constant, thereby improving the system's efficiency. performance and reduce energy consumption.
以上所述实施例仅表达了本发明的几种实施方式，其描述较为具体和详细，但并不能因此而理解为对本发明专利范围的限制。应当指出的是，对于本领域的普通技术人员来说，在不脱离本发明构思的前提下，还可以做出若干变形和改进，这些都属于本发明的保护范围。因此，本发明专利的保护范围应以所附权利要求为准。The above-mentioned embodiments only express several implementation modes of the present invention, and their descriptions are relatively specific and detailed, but they should not be construed as limiting the patent scope of the present invention. It should be noted that, for those of ordinary skill in the art, several modifications and improvements can be made without departing from the concept of the present invention, and these all belong to the protection scope of the present invention. Therefore, the scope of protection of the patent of the present invention should be determined by the appended claims.
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