技术领域technical field
本发明涉及5G通信技术领域，具体来说是一种面向5G通信的小型化超宽带滤波功分馈电网络及其设计方法。The invention relates to the technical field of 5G communication, in particular to a miniaturized ultra-wideband filtering power division feeding network oriented to 5G communication and a design method thereof.
背景技术Background technique
伴随着现代无线通信技术的快速发展，5G通信的商用也已经迫在眉睫。工信部已经公布了我国5G中频段内的频率使用规划，明确了3300-3400MHz(原则上限室内使用)、3400-3600MHz和4800-5000MHz频段作为5G通信系统的工作频段。而随着5G通信技术研究的深入，对于微波射频电路的要求也在逐渐提高，追求超宽带、高集成度、小型化、低插入损耗的性能特点。With the rapid development of modern wireless communication technology, the commercialization of 5G communication is imminent. The Ministry of Industry and Information Technology has announced the frequency use plan in my country's 5G mid-band, specifying the 3300-3400MHz (in principle upper limit indoor use), 3400-3600MHz and 4800-5000MHz frequency bands as the working frequency bands of the 5G communication system. With the in-depth research of 5G communication technology, the requirements for microwave radio frequency circuits are gradually increasing, and the performance characteristics of ultra-wideband, high integration, miniaturization, and low insertion loss are pursued.
在5G通信系统中，滤波器作为射频前端中不可缺少的一部分，其主要作用就是滤波和选频。通过滤除无用的频率信号，选择有用的信号并且对各种不同的信号进行分离来抑制噪声信号，减少对不同电路的干扰，滤波器的性能会影响整个通信系统的性能。功分器同样作为微波射频系统中的重要电路之一，是相控阵雷达、有源放大电路和天线阵等的主要组成硬件。功分器的作用是把一路输入信号分成两路或多路输出相等或不相等能量，也可以反过来将多路信号能量合成一路输出。In the 5G communication system, the filter is an indispensable part of the RF front-end, and its main function is filtering and frequency selection. By filtering out useless frequency signals, selecting useful signals and separating various signals to suppress noise signals and reduce interference to different circuits, the performance of the filter will affect the performance of the entire communication system. As one of the important circuits in the microwave radio frequency system, the power divider is also the main component hardware of phased array radar, active amplifier circuit and antenna array. The function of the power divider is to divide an input signal into two or multiple channels to output equal or unequal energy, and it can also conversely combine the energy of multiple channels into one output.
滤波器和功分器这两款无源器件在射频前端系统里占据着很大的空间，在一定程度限制着系统的小型化设计。5G通信频段的宣布意味着未来的频段将会增加，频段的增加对射频前端器件的数量影响最大，随着终端支持的频段数的增加，其器件数量急剧增加，这样会与未来的5G通信下要求的射频系统小尺寸电路相矛盾。传统的解决办法是将这两款器件分别进行小型化设计，这样整个系统的尺寸能得到减小，但是整体的尺寸缩小还是非常有限的。并且在滤波器与功分器的的小型化设计中，有一部分是以牺牲插入损耗作为代价的。因此，研究人员开始提出了这种滤波器与功分器集成化设计的方案，把两个功能独立的微波器件集成为一个单独的器件使其同时实现信号滤波与功率分配的功能。这样集成的设计方法将会在结构上直接减小系统的尺寸，同时还能使系统的整体性能得到改善，更好的完成现代通信系统的小型化、集成化设计。The two passive components, filter and power divider, occupy a lot of space in the RF front-end system, which limits the miniaturization design of the system to a certain extent. The announcement of the 5G communication frequency band means that the frequency band will increase in the future, and the increase in the frequency band will have the greatest impact on the number of RF front-end devices. The required small size circuit of the RF system is contradictory. The traditional solution is to miniaturize the two devices separately, so that the size of the entire system can be reduced, but the overall size reduction is still very limited. And in the miniaturization design of filter and power divider, part of it is at the expense of sacrificing insertion loss. Therefore, researchers began to propose a scheme for the integrated design of this filter and power divider, integrating two microwave devices with independent functions into a single device to realize the functions of signal filtering and power distribution at the same time. Such an integrated design method will directly reduce the size of the system in structure, and at the same time, it can improve the overall performance of the system, and better complete the miniaturized and integrated design of modern communication systems.
近年来对于滤波功分馈电网络的集成化设计可以归纳为三种方式：In recent years, the integrated design of the filter power division feeding network can be summarized into three ways:
第一种是将滤波器和功分器通过级联的方式省去滤波器与功分器之间的50欧姆微带连接线来同时实现功率分配和滤波的功能，虽然在一定程度上能够减小电路的尺寸和损耗，但是效果并不明显；The first is to cascading the filter and the power divider to eliminate the 50-ohm microstrip connection line between the filter and the power divider to realize the functions of power distribution and filtering at the same time, although it can reduce the power to a certain extent. Small circuit size and loss, but the effect is not obvious;
第二种方法是使用滤波器来代替传统功分器中的四分之一波长线来达到集成的目的，这种设计中用来替代的滤波结构需要满足在工作频带内，输入与输出相位相差90度或90度的奇数倍，并且输入输出阻抗与四分之一的波长线特性阻抗相等；The second method is to use a filter to replace the quarter-wavelength line in the traditional power divider to achieve the purpose of integration. The filter structure used in this design needs to satisfy the input and output phase difference within the working frequency band. 90 degrees or odd multiples of 90 degrees, and the input and output impedance is equal to the characteristic impedance of a quarter wavelength line;
第三种方法是采用特殊的结构将两种器件进行一体化综合设计，这种功分器的设计方法是通过结合等效四分之一阻抗变换器的思路，将具有带通特性的多模谐振器替代Wilkinson的四分之一波长线并利用耦合矩阵重构其结构，这种方法设计的滤波功分馈电网络能够显著减小器件体积。The third method is to use a special structure to integrate the two devices into an integrated design. The design method of this power divider is to combine the idea of an equivalent quarter-impedance converter to combine the multi-mode with band-pass characteristics. The resonator replaces Wilkinson's quarter-wavelength line and uses the coupling matrix to reconstruct its structure. The filter power division feeding network designed by this method can significantly reduce the size of the device.
然而，随着目前通信技术的不断进步、5G的逐渐应用，更多的频段的通信需求将会一直存在，因此对通信系统中的超宽带、小型化的器件设计要求也越发显著，但是传统的滤波功分馈电网络还不能实现覆盖3G、4G、5G全部通信频段的超宽带特性，且部分存在尺寸较大的局限性。However, with the continuous progress of communication technology and the gradual application of 5G, the communication needs of more frequency bands will always exist, so the design requirements for ultra-wideband and miniaturized devices in communication systems are becoming more and more significant, but the traditional The filter power division feeding network cannot achieve the ultra-wideband characteristics covering all communication frequency bands of 3G, 4G and 5G, and some have the limitation of large size.
因此，面向5G通信的滤波功分馈电网络其必须同时具备小型化、高选择性、超宽带的滤波特性、功率分配这三个必要条件才能满足于5G通信的应用需要，同时兼顾3G、4G通信系统同步工作的需要。Therefore, the filtering power division feed network for 5G communication must have the three necessary conditions of miniaturization, high selectivity, ultra-wideband filtering characteristics, and power distribution to meet the application needs of 5G communication, while taking into account 3G and 4G. Communication system needs to work synchronously.
发明内容SUMMARY OF THE INVENTION
本发明的目的是为了解决现有技术中滤波功分馈电网络难以同时实现小型化、高带宽、高滤波特性的缺陷，提供一种面向5G通信的小型化超宽带滤波功分馈电网络及其设计方法来解决上述问题。The purpose of the present invention is to solve the defect in the prior art that it is difficult to realize miniaturization, high bandwidth and high filtering characteristics in the filtering power division feeding network at the same time, and provide a miniaturized ultra-wideband filtering power division feeding network oriented to 5G communication and Its design method to solve the above problems.
为了实现上述目的，本发明的技术方案如下：In order to achieve the above object, technical scheme of the present invention is as follows:
一种面向5G通信的小型化超宽带滤波功分馈电网络，包括微波介质基板，微波介质基板的正面印刷有微带电路组件，微波介质基板的背面印刷有金属接地板，A miniaturized ultra-wideband filtering power division feeding network oriented to 5G communication, comprising a microwave dielectric substrate, a microstrip circuit component is printed on the front of the microwave dielectric substrate, and a metal grounding plate is printed on the back of the microwave dielectric substrate,
所述的微带电路组件包括50欧姆输入传输线、微带三线耦合结构和两条50欧姆输出传输线，所述的微带三线耦合结构包括三条依次平行布置的第一耦合导体、第二耦合导体和第三耦合导体，50欧姆输入传输线的末端与第二耦合导体相连，第一耦合导体、第三耦合导体的末端分别与两条50欧姆输出传输线相连；The microstrip circuit assembly includes a 50-ohm input transmission line, a microstrip three-wire coupling structure and two 50-ohm output transmission lines, and the microstrip three-wire coupling structure includes three parallelly arranged first coupling conductors, second coupling conductors and The third coupling conductor, the end of the 50 ohm input transmission line is connected to the second coupling conductor, and the ends of the first coupling conductor and the third coupling conductor are respectively connected to two 50 ohm output transmission lines;
所述50欧姆输入传输线的末端连接有两条短路枝节线，两条短路枝节线分别位于微带三线耦合结构的两侧，两条短路枝节线呈镜像对应，两条短路枝节线的末端均金属化过孔连接至金属接地板，隔离电阻的一端接在第一耦合导体的首端，隔离电阻的另一端接在第三耦合导体的首端，第一耦合导体、第三耦合导体的末端均连接有改进型阶梯阻抗谐振器，两个改进型阶梯阻抗谐振器分别位于微带三线耦合结构的两侧，两个改进型阶梯阻抗谐振器呈镜像对应。The ends of the 50-ohm input transmission line are connected with two short-circuit branch lines, the two short-circuit branch lines are respectively located on both sides of the microstrip three-wire coupling structure, the two short-circuit branch lines are mirror images corresponding to each other, and the ends of the two short-circuit branch lines are all metal. The via hole is connected to the metal ground plate, one end of the isolation resistor is connected to the head end of the first coupling conductor, the other end of the isolation resistor is connected to the head end of the third coupling conductor, and the ends of the first coupling conductor and the third coupling conductor are both connected. The improved stepped impedance resonator is connected, and the two improved stepped impedance resonators are respectively located on both sides of the microstrip three-wire coupling structure, and the two improved stepped impedance resonators are in mirror image correspondence.
所述改进型阶梯阻抗谐振器的高阻抗传输线连接在第一耦合导体或第三耦合导体的末端，改进型阶梯阻抗谐振器的高阻抗传输线以低阻抗传输线为中心围绕布置在低阻抗传输线四周,两个改进型阶梯阻抗谐振器分别在微带三线耦合结构的两侧产生两个传输零点。The high impedance transmission line of the improved stepped impedance resonator is connected to the end of the first coupling conductor or the third coupling conductor, and the high impedance transmission line of the improved stepped impedance resonator is arranged around the low impedance transmission line around the low impedance transmission line, The two improved stepped impedance resonators generate two transmission zeros on both sides of the microstrip three-wire coupling structure, respectively.
所述的短路枝节线为“几”字形，两个短路枝节线分别在微带三线耦合结构的边缘产生两个传输极点。The short-circuit branch line is in the shape of a "ji", and the two short-circuit branch lines respectively generate two transmission poles at the edge of the microstrip three-wire coupling structure.
所述的第一耦合导体和第三耦合导体的传输线线宽相同，第一耦合导体、第二耦合导体和第三耦合导体的传输线长度相同，第一耦合导体的传输线长度为中心频率波长的四分之一。The transmission line width of the first coupling conductor and the third coupling conductor is the same, the transmission line length of the first coupling conductor, the second coupling conductor and the third coupling conductor is the same, and the transmission line length of the first coupling conductor is four times the wavelength of the center frequency. one part.
所述的改进型阶梯阻抗谐振器呈方形，改进型阶梯阻抗谐振器的总长度为中心频率波长的二分之一。The improved stepped impedance resonator is square, and the total length of the improved stepped impedance resonator is half of the wavelength of the center frequency.
一种面向5G通信的小型化超宽带滤波功分馈电网络的设计方法，包括以下步骤：A design method for a miniaturized ultra-wideband filtering power division feeding network for 5G communication, comprising the following steps:
微带三线耦合结构的设计，根据中心频率设定微带三线耦合结构的长度为中心频率波长的四分之一，In the design of the microstrip three-line coupling structure, the length of the microstrip three-line coupling structure is set to be a quarter of the wavelength of the center frequency according to the center frequency.
设微带三线耦合结构的长度为d、电长度为θ，其计算公式如下：Let the length of the microstrip three-wire coupling structure be d and the electrical length be θ, the calculation formula is as follows:
β·d＝πβ·d=π
其中：β为介质材料的导波数，λg为导波波长，c为自由空间中的光速，f0为中心频率，εeff为介质材料的有效介电常数；Where: β is the guided wave number of the dielectric material, λg is the guided wave wavelength, c is the speed of light in free space, f0 is the center frequency, and εeff is the effective dielectric constant of the dielectric material;
改进型阶梯阻抗谐振器的设计，根据传输零点的位置，结合改进型阶梯阻抗谐振器产生谐振的频率确定阻抗比，其产生谐振的条件表达式如下：In the design of the improved stepped impedance resonator, the impedance ratio is determined according to the position of the transmission zero point and combined with the resonance frequency of the improved stepped impedance resonator. The conditional expression for the resonance is as follows:
Z1tanθ1-Z2cotθ2＝0；Z1 tanθ1 -Z2 cotθ2 =0;
隔离电阻阻值的设计，根据Wilkinson的设计理论和奇模分析下所确定的关系，在Zino＝Z0时获得较好的隔离度，计算隔离电阻的阻值大小，其之间的计算公式如下：For the design of the resistance value of the isolation resistor, according to Wilkinson's design theory and the relationship determined under the odd-mode analysis, better isolation is obtained when Zino = Z0 , and the resistance value of the isolation resistor is calculated, and the calculation formula between them as follows:
其中，Zaoo和Zaee是在奇模激励下的奇-奇模式和偶-偶模式阻抗，εr是介质材料的相对介电常数。where Zaoo and Zaee are the odd-odd and even-even mode impedances under odd-mode excitation, and εr is the relative permittivity of the dielectric material.
有益效果beneficial effect
本发明的一种面向5G通信的小型化超宽带滤波功分馈电网络及其设计方法，与现有技术相比在小型化的微波介质基板上实现了高带宽、高滤波功能，满足了5G通信的实际应用需求。Compared with the prior art, a miniaturized ultra-wideband filtering power division feeding network oriented to 5G communication and a design method thereof of the present invention realizes high bandwidth and high filtering function on a miniaturized microwave dielectric substrate, and satisfies the requirements of 5G The practical application requirements of communication.
本发明较Wilkinson型的传统滤波功分馈电网络相比能具有较宽的通带带宽，通过在输入传输线的的末端加载一对短路枝节传输线，来进一步增大带宽，使得通带带宽覆盖3G、4G、5G全部通信频段，并且通带裙带更加陡峭。同时，加载的改进型阶梯阻抗谐振器能够在通带两侧形成两个传输零点，提高了频率选择性；通过对改进型阶梯阻抗谐振器做特殊的折叠处理，能够减小整个电路的尺寸，并且保证了该滤波功分馈电网络还具有低插入损耗和较好的隔离特性。Compared with the Wilkinson-type traditional filtering power division feeding network, the present invention can have a wider passband bandwidth. By loading a pair of short-circuit branch transmission lines at the end of the input transmission line, the bandwidth is further increased, so that the passband bandwidth covers 3G , 4G, 5G all communication frequency bands, and the passband crony is more steep. At the same time, the loaded improved stepped impedance resonator can form two transmission zeros on both sides of the passband, which improves the frequency selectivity. And it is ensured that the filter power division feeding network also has low insertion loss and better isolation characteristics.
基于本发明设计的滤波功分馈电网络，设计仿真的中心频率为3.5GHz，获得的相对带宽达到了101％，从1.73GHz-5.26GHz；电路尺寸大小为0.28λg×0.21λg；并且其两个输出端口的插入损耗最小处分别达到3.16dB和3.41dB，在通带内的隔离均小于10.3dB；与传统基于Wilkinson型的滤波器功分器相比，具有尺寸小、相对带宽大、插入损耗小的优点，适合于小型化、高性能微波电路系统，能够适应5G通信基站，并兼容3G、4G通信系统工作的应用环境需要。Based on the filtering power division feeding network designed by the present invention, the center frequency of the design simulation is 3.5GHz, the obtained relative bandwidth reaches 101%, from 1.73GHz-5.26GHz; the circuit size is0.28λg ×0.21λg ; and The minimum insertion loss of the two output ports reaches 3.16dB and 3.41dB respectively, and the isolation in the passband is less than 10.3dB; , The advantages of small insertion loss, suitable for miniaturized and high-performance microwave circuit systems, can adapt to 5G communication base stations, and are compatible with the application environment of 3G and 4G communication systems.
附图说明Description of drawings
图1为本发明本发明的结构示意图；Fig. 1 is the structural representation of the present invention;
图2为本发明的等效电路模型结构示意图；2 is a schematic structural diagram of an equivalent circuit model of the present invention;
图3a为本发明中偶模激励的等效电路图；Fig. 3a is the equivalent circuit diagram of even mode excitation in the present invention;
图3b为本发明中奇模激励的等效电路图；Fig. 3b is the equivalent circuit diagram of odd-mode excitation in the present invention;
图4a为本发明中改进型阶梯阻抗谐振器的低阻抗传输线不同特性阻抗大小的S参数比较图；Fig. 4a is the S-parameter comparison diagram of different characteristic impedance magnitudes of the low-impedance transmission line of the improved stepped impedance resonator in the present invention;
图4b为本发明中改进型阶梯阻抗谐振器的低阻抗传输线不同电长度大小的S参数比较图；Fig. 4b is the S-parameter comparison diagram of the low-impedance transmission line of the improved stepped impedance resonator of the present invention with different electrical lengths;
图5为本发明的微带三线耦合结构已加载和未加载短路枝节线S参数比较图；5 is a comparison diagram of the S-parameters of the loaded and unloaded short-circuit branch lines of the microstrip three-wire coupling structure of the present invention;
图6为本发明中隔离电阻不同大小值时S参数比较图；Fig. 6 is the S parameter comparison diagram when the isolation resistance is different in the present invention;
图7a和图7b为本发明的仿真与测试结果比较图；Figure 7a and Figure 7b are simulation and test results comparison diagrams of the present invention;
其中，101-50欧姆输入传输线、102-微带三线耦合结构、103-改进型阶梯阻抗谐振器、104-短路枝节线、105-隔离电阻、106-微波介质基板、107-50欧姆输出传输线、108-第一耦合导体、109-第二耦合导体、110-第三耦合导体。Among them, 101-50 ohm input transmission line, 102- microstrip three-wire coupling structure, 103- improved stepped impedance resonator, 104- short-circuit branch line, 105- isolation resistor, 106- microwave dielectric substrate, 107-50 ohm output transmission line, 108-first coupling conductor, 109-second coupling conductor, 110-third coupling conductor.
具体实施方式Detailed ways
为使对本发明的结构特征及所达成的功效有更进一步的了解与认识，用以较佳的实施例及附图配合详细的说明，说明如下：In order to have a further understanding and understanding of the structural features of the present invention and the effects achieved, the preferred embodiments and accompanying drawings are used in conjunction with detailed descriptions, and the descriptions are as follows:
如图1所示，本发明所述的一种面向5G通信的小型化超宽带滤波功分馈电网络，包括微波介质基板106。微波介质基板106可以为Roger RO4003C，微波介质基板的介电常数为3.55、损耗角正切为0.027、厚度为0.508mm。微波介质基板106的背面印刷有金属接地板，微波介质基板106正面印刷有微带电路组件，即将50欧姆输入传输线101与微带三线耦合结构102连接，两个改进型阶梯阻抗谐振器103对称分布在输出口，两个短路枝节线104加载在输入端，隔离电阻105跨接在微带三线耦合结构的两条不相邻传输线的始端。50欧姆输入传输线101、两条50欧姆输出传输线107都采用微带线形式，并与SMA同轴接头匹配。As shown in FIG. 1 , a miniaturized ultra-wideband filtering power division feeding network for 5G communication according to the present invention includes a microwave dielectric substrate 106 . The microwave dielectric substrate 106 can be Roger RO4003C, and the dielectric constant of the microwave dielectric substrate is 3.55, the loss tangent is 0.027, and the thickness is 0.508 mm. A metal grounding plate is printed on the back of the microwave dielectric substrate 106, and a microstrip circuit component is printed on the front of the microwave dielectric substrate 106, that is, the 50-ohm input transmission line 101 is connected to the microstrip three-wire coupling structure 102, and the two improved stepped impedance resonators 103 are symmetrically distributed At the output port, two short-circuit branch lines 104 are loaded at the input end, and an isolation resistor 105 is connected across the beginning ends of two non-adjacent transmission lines of the microstrip three-wire coupling structure. The 50-ohm input transmission line 101 and the two 50-ohm output transmission lines 107 are all in the form of microstrip lines and are matched with SMA coaxial connectors.
微带电路组件包括50欧姆输入传输线101、微带三线耦合结构102和两条50欧姆输出传输线107。微带三线耦合结构102能够实现传输线之间的强耦合，以此实现带宽，微带三线耦合结构102包括三条依次平行布置的第一耦合导体108、第二耦合导体109和第三耦合导体110，第一耦合导体108和第三耦合导体110的传输线线宽相同，第一耦合导体108、第二耦合导体109和第三耦合导体110的传输线长度相同，第一耦合导体108的传输线长度为中心频率波长的四分之一。相邻两传输线(第一耦合导体108与第二耦合导体109或第二耦合导体109与第三耦合导体110)的距离设置按照最低可加工尺寸而定，通过减小相邻耦合线之间的间距，能够获得强耦合来增大带宽。The microstrip circuit assembly includes a 50 ohm input transmission line 101 , a microstrip three-wire coupling structure 102 and two 50 ohm output transmission lines 107 . The microstrip three-wire coupling structure 102 can realize strong coupling between transmission lines, thereby realizing the bandwidth, and the microstrip three-wire coupling structure 102 includes three first coupling conductors 108, second coupling conductors 109 and third coupling conductors 110 arranged in parallel in sequence, The transmission line widths of the first coupling conductor 108 and the third coupling conductor 110 are the same, the transmission line lengths of the first coupling conductor 108, the second coupling conductor 109 and the third coupling conductor 110 are the same, and the transmission line length of the first coupling conductor 108 is the center frequency quarter of the wavelength. The distance between two adjacent transmission lines (the first coupling conductor 108 and the second coupling conductor 109 or the second coupling conductor 109 and the third coupling conductor 110 ) is set according to the minimum processable size. By reducing the distance between adjacent coupling lines Spacing, strong coupling can be obtained to increase the bandwidth.
50欧姆输入传输线101的末端与第二耦合导体109(微带三线耦合结构102的中间导体)(首端)相连，用于经输入信号引入端口。第一耦合导体108、第三耦合导体110的末端分别与两条50欧姆输出传输线107相连，将微带三线耦合结构102不相邻的两传输线终端作为两输出端口。The end of the 50 ohm input transmission line 101 is connected to the second coupling conductor 109 (the middle conductor of the microstrip three-wire coupling structure 102 ) (head end) for introducing the port through the input signal. The ends of the first coupling conductor 108 and the third coupling conductor 110 are respectively connected to two 50 ohm output transmission lines 107 , and the two transmission line terminals that are not adjacent to the microstrip three-wire coupling structure 102 are used as two output ports.
50欧姆输入传输线101的末端连接有两条短路枝节线104，两条短路枝节线104分别位于微带三线耦合结构102的两侧，两条短路枝节线104呈镜像对应。通过在输出端口加对称的短路枝节，可以在通带内多产生两个传输极点，通过控制改变枝节特性阻抗的大小影响极点的位置，让极点落在原通带的边界处，以增大带宽，从而增加通带频率宽度。Two short-circuit branch lines 104 are connected to the end of the 50-ohm input transmission line 101 . The two short-circuit branch lines 104 are respectively located on both sides of the microstrip three-wire coupling structure 102 , and the two short-circuit branch lines 104 correspond to mirror images. By adding a symmetrical short-circuit branch to the output port, two more transmission poles can be generated in the passband, and the position of the pole can be affected by controlling and changing the characteristic impedance of the branch, so that the pole falls on the boundary of the original passband to increase the bandwidth. Thereby increasing the passband frequency width.
两条短路枝节线104的末端均金属化过孔连接至金属接地板，使微带线与介质基板的接地面相连形成短路连接，短路枝节线104的加载会在通带的边缘额外产生两个传输极点，进一步增大通带带宽，其传输线长度应为对应的中心频率的四分之一。通过调整传输线特性阻抗的大小可以用来改变极点的位置。本发明中是将传输极点的位置落在原通带内的最低和最高频率处，以此来增大滤波功分馈电网络的通带带宽并且会让通带裙带变得更加陡峭。值得注意的是，常规的增加通带频率宽度多采用增加耦合强度的方式来实现，如进一步缩小耦合线间距等，但其受加工工艺精度限制。为此，本技术创新性地采用在主传输线上级联短路枝节线，通过在通带范围内引入传输极点来增加带宽；进一步，通过计算短路枝节线长度，来调整传输极点的频率位置，使其位于通带两边，从而改善通带的边缘陡峭度，以提高频率选择特性。The ends of the two short-circuit stub lines 104 are connected to the metal ground plane through metallized vias, so that the microstrip line is connected to the ground plane of the dielectric substrate to form a short-circuit connection. The transmission pole further increases the passband bandwidth, and the length of the transmission line should be a quarter of the corresponding center frequency. The position of the pole can be changed by adjusting the characteristic impedance of the transmission line. In the present invention, the position of the transmission pole is located at the lowest and highest frequencies in the original passband, thereby increasing the passband bandwidth of the filtering power division feeding network and making the passband skirt more steep. It is worth noting that the conventional increase of the passband frequency width is mostly achieved by increasing the coupling strength, such as further reducing the spacing of the coupling lines, etc., but it is limited by the precision of the processing technology. To this end, the technology innovatively uses cascading short-circuit branch lines on the main transmission line, and increases the bandwidth by introducing transmission poles within the passband range; further, by calculating the length of the short-circuit branch lines, the frequency position of the transmission pole is adjusted to make it Located on both sides of the passband, thereby improving the edge steepness of the passband to improve frequency selection characteristics.
为了进一步使得结构紧凑、缩小尺寸，在此将所述的短路枝节线104弯折为“几”字形。In order to further make the structure compact and reduce the size, the short-circuit branch line 104 is bent into a "ji" shape.
根据设计理论需要，在此通过加装隔离电阻105使得隔离度更佳，隔离电阻105的一端接在第一耦合导体108的首端，隔离电阻105的另一端接在第三耦合导体110的首端，即隔离电阻105跨接在第一耦合导体108的首端和第三耦合导体110的首端。隔离电阻的引入将会加强两输出端口之前的隔离，不同电阻阻值是影响隔离特性的主要因素之一，其可以采用0402型封装贴片电阻,将会使两输出端口之间的隔离性能得到增强,阻值为200欧姆。According to the needs of the design theory, the isolation resistance 105 is installed here to make the isolation better. One end of the isolation resistor 105 is connected to the head end of the first coupling conductor 108, and the other end of the isolation resistor 105 is connected to the head end of the third coupling conductor 110. The terminal, that is, the isolation resistor 105 is connected across the head end of the first coupling conductor 108 and the head end of the third coupling conductor 110 . The introduction of the isolation resistor will strengthen the isolation between the two output ports. Different resistance values are one of the main factors affecting the isolation characteristics. It can use 0402 type packaged chip resistors, which will improve the isolation performance between the two output ports. Enhanced, the resistance is 200 ohms.
第一耦合导体108、第三耦合导体110的末端均连接有改进型阶梯阻抗谐振器103，改进型阶梯阻抗谐振器103按现有方式由一条高特性阻抗传输线和一条低特性阻抗传输线组成。两个改进型阶梯阻抗谐振器103分别位于微带三线耦合结构102的两侧，两个改进型阶梯阻抗谐振器103呈镜像对应。改进型阶梯阻抗谐振器103根据传统的阶梯阻抗谐振器改变而来，在输出端接阶梯阻抗谐振器，可以让其在通带两侧产生两个传输零点，从而改善通带陡峭度，提高频率选择特性。需要指出的是，为了提高频率抑制特性，常规的方法是通过增加开路枝节线来增加传输零点。然而，该方式的枝节线长度随传输零点的四分之一波长变化，不利于实现电路的小型化。为此，本技术创新性的采用阶梯阻抗谐振器来产生零点，通过调节阶梯阻抗比来实现结构的小型化，进一步的为使电路结构紧凑，结合电路布局将阶梯阻抗谐振器成几字形弯折。The ends of the first coupling conductor 108 and the third coupling conductor 110 are both connected with an improved stepped impedance resonator 103. The improved stepped impedance resonator 103 is composed of a high characteristic impedance transmission line and a low characteristic impedance transmission line in the existing manner. The two modified stepped impedance resonators 103 are located on two sides of the microstrip three-wire coupling structure 102 respectively, and the two modified stepped impedance resonators 103 are mirror images corresponding to each other. The improved stepped impedance resonator 103 is modified from the traditional stepped impedance resonator. Connecting the stepped impedance resonator at the output can make it generate two transmission zeros on both sides of the passband, thereby improving the passband steepness and increasing the frequency. Select Properties. It should be pointed out that, in order to improve the frequency rejection characteristic, the conventional method is to increase the transmission zero point by increasing the open-circuit branch line. However, the length of the branch line in this method varies with the quarter wavelength of the transmission zero point, which is not conducive to realizing the miniaturization of the circuit. For this reason, this technology innovatively uses a stepped impedance resonator to generate the zero point, and realizes the miniaturization of the structure by adjusting the stepped impedance ratio. Further, in order to make the circuit structure compact, the stepped impedance resonator is bent into a several-shaped shape in combination with the circuit layout. .
改进型阶梯阻抗谐振器103的高阻抗传输线连接在第一耦合导体108或第三耦合导体110的末端，改进型阶梯阻抗谐振器103的高阻抗传输线以低阻抗传输线为中心围绕布置在低阻抗传输线四周。The high impedance transmission line of the improved stepped impedance resonator 103 is connected to the end of the first coupling conductor 108 or the third coupling conductor 110, and the high impedance transmission line of the improved stepped impedance resonator 103 is arranged around the low impedance transmission line around the low impedance transmission line. all around.
优选地，改进型阶梯阻抗谐振器103呈方形，改进型阶梯阻抗谐振器103的总长度为中心频率波长的二分之一，即改进型阶梯阻抗谐振器将低阻抗传输线的宽度和尺寸长度设置为近似相等的矩形状，高阻抗传输线沿着低阻抗传输线的矩形边折叠、连接。这样在实际应用中，能够减小电路的尺寸。阶梯阻抗谐振器的引入能够在通带两侧分别形成一个传输零点，能够提高频率的选择性。Preferably, the modified stepped impedance resonator 103 is in a square shape, and the total length of the modified stepped impedance resonator 103 is half of the wavelength of the center frequency, that is, the modified stepped impedance resonator sets the width and size of the low impedance transmission line. In an approximately equal rectangular shape, the high-impedance transmission line is folded and connected along the rectangular side of the low-impedance transmission line. In this way, in practical applications, the size of the circuit can be reduced. The introduction of the stepped impedance resonator can form a transmission zero on both sides of the passband, which can improve the frequency selectivity.
在此，还提供一种面向5G通信的小型化超宽带滤波功分馈电网络的设计方法，包括以下步骤：Herein, a design method of a miniaturized ultra-wideband filter power division feeding network for 5G communication is also provided, including the following steps:
第一步，微带三线耦合结构102的设计，根据中心频率设定微带三线耦合结构102的长度为中心频率波长的四分之一。如图2所示，将改进型的阶梯阻抗谐振器的两条传输线的特性阻抗和电长度分别记为Z1,Z2,θ1和θ2，并且将两特性阻抗相除，记作阻抗比：RZ＝Z2/Z1，两传输线的总的电长度为π，将短路枝节线的特性阻抗和电长度记为Z3和θ3。In the first step, in the design of the microstrip three-wire coupling structure 102, the length of the microstrip three-wire coupling structure 102 is set to be a quarter of the wavelength of the center frequency according to the center frequency. As shown in Fig. 2, the characteristic impedance and electrical length of the two transmission lines of the improved stepped impedance resonator are denoted as Z1 , Z2 , θ1 and θ2 respectively, and the two characteristic impedances are divided, denoted as impedance Ratio: RZ = Z2 /Z1 , the total electrical length of the two transmission lines is π, and the characteristic impedance and electrical length of the short-circuit branch line are denoted as Z3 and θ3 .
设微带三线耦合结构(102)的长度为d、电长度为θ，其计算公式如下：Suppose the length of the microstrip three-wire coupling structure (102) is d and the electrical length is θ, and its calculation formula is as follows:
β·d＝πβ·d=π
其中：β为介质材料的导波数，λg为导波波长，c为自由空间中的光速，f0为中心频率，εeff为介质材料的有效介电常数；Where: β is the guided wave number of the dielectric material, λg is the guided wave wavelength, c is the speed of light in free space, f0 is the center frequency, and εeff is the effective dielectric constant of the dielectric material;
第二步，改进型阶梯阻抗谐振器103的设计，根据传输零点的位置，结合改进型阶梯阻抗谐振器103产生谐振的频率确定阻抗比，其产生谐振的条件表达式如下：The second step is the design of the improved stepped impedance resonator 103. According to the position of the transmission zero point, the impedance ratio is determined in combination with the frequency at which the improved stepped impedance resonator 103 generates resonance. The conditional expression for the resonance is as follows:
Z1tanθ1-Z2cotθ2＝0。Z1 tanθ1 −Z2 cotθ2 =0.
假设已知零点的位置计算阶梯阻抗谐振器的线宽和电长度，以及已知回波损耗计算微带三线耦合结构的线宽。Assuming that the position of the zero point is known, the linewidth and electrical length of the stepped impedance resonator are calculated, and the return loss is known to calculate the linewidth of the microstrip three-wire coupling structure.
如图3a所示为偶模激励下的二分结构等效图，在偶模激励下将耦合线的特性阻抗分别记为Z0e,Z0o，其阶梯阻抗谐振器的输入阻抗记为Zt，从耦合线的端口4的输入阻抗记为Zin4，短路枝节线的输入阻抗记为Zins，从端口2输入的输入阻抗记为Zine。其计算公式分别如下：Figure 3a shows the equivalent diagram of the bipartite structure under the even-mode excitation. Under the even-mode excitation, the characteristic impedance of the coupled line is recorded as Z0e , Z0o , and the input impedance of the stepped impedance resonator is recorded as Zt , The input impedance from port 4 of the coupling line is denoted as Zin4 , the input impedance of the short-circuit branch line is denoted as Zins , and the input impedance from port 2 is denoted as Zine . The calculation formulas are as follows:
Zins＝jZ3tanθ3Zins =jZ3 tanθ3
已知回波损耗因为滤波电路可以被看作为一个无损耗电路，当传输系数时，在|S12|＝0时，得到传输零点，其传输零点的产生条件为：Known return loss Because the filter circuit can be regarded as a lossless circuit, when the transmission coefficient , when |S12 |=0, the transmission zero point is obtained, and the generation condition of the transmission zero point is:
Z1tanθ1-Z2cotθ2＝0Z1 tanθ1 -Z2 cotθ2 =0
由已知的回波损耗，可以计算Zine，在确定的零点的情况并且已知下Zine下Zin4可以被计算。此时耦合线结构可以被视为一个二端口网络，Zin4可以被自身阻抗和传输阻抗来表达。From the known return loss, Zine can be calculated, and Zin4 can be calculated in the case of a determined zero and given Zine . At this time, the coupled line structure can be regarded as a two-port network, and Zin4 can be expressed by its own impedance and transmission impedance.
因此可以计算在偶模激励下的特性阻抗，计算其耦合线的线宽。Therefore, the characteristic impedance under even-mode excitation can be calculated, and the line width of its coupled line can be calculated.
至此，还可以按微带三线耦合结构102的设计方法，以短路枝节线的长度为四分之一波长为基础，通过调节特性阻抗Z3和电长度θ3使产生的传输极点落在合适的位置，以此来加大带宽。So far, according to the design method of the microstrip three-wire coupling structure 102, on the basis that the length of the short-circuit branch line is a quarter wavelength, by adjusting the characteristic impedance Z3 and the electrical length θ3 , the generated transmission pole can be placed at a suitable value. location to increase bandwidth.
第三步，隔离电阻105阻值的设计。The third step is to design the resistance value of the isolation resistor 105 .
根据Wilkinson的设计理论和奇模分析下所确定的关系，在Zino＝Z0时获得较好的隔离度，计算隔离电阻的阻值大小。如图3b所示，其为奇模激励下的二分结构等效图，在奇模激励下将耦合线的特性阻抗分别记为Zaoe,从端口2输入的输入阻抗记为Zino，从耦合线的端口4的输入阻抗记为Zi'n4，其阶梯阻抗谐振器的输入阻抗记为Zt，其之间的计算公式如下：According to Wilkinson's design theory and the relationship determined under the odd-mode analysis, better isolation is obtained when Zino = Z0 , and the resistance value of the isolation resistor is calculated. As shown in Figure 3b, it is the equivalentdiagram of thebisection structure under odd-mode excitation. The input impedance of port 4 of the line is denoted as Zi 'n4 , the input impedance of its stepped impedance resonator is denoted as Zt , and the calculation formula between them is as follows:
其中，Zaoo和Zaee是在奇模激励下的奇-奇模式和偶-偶模式阻抗，εr是介质材料的相对介电常数。根据Wilkinson的设计理论，当Zino等于Z0时，将会形成较好的隔离特性。因此在Zaoo和Zaee确定的情况下，电阻阻值将会根据上式能够被计算。where Zaoo and Zaee are the odd-odd and even-even mode impedances under odd-mode excitation, and εr is the relative permittivity of the dielectric material. According to Wilkinson's design theory, when Zino is equal to Z0 , better isolation characteristics will be formed. Therefore, in the case whereZaoo andZaee are determined, the resistance value of the resistor can be calculated according to the above formula.
通过上述方法，本专利突破了现有的电路板工艺加工精度的限制，在三线耦合传输线的基础上，通过在主传输线上增加短路枝节线、阶梯阻抗谐振器等方式来增加通带宽度、提高通带边缘选择特性，增加带外抑制度。同时，为进一步实现电路结构紧凑，结合电路结构的布局，通过合理分配通带传输极点和带外传输零点的位置来计算创新手段的结构尺寸和位置。与传统方法相比，本发明专利设计的滤波功分电路，可同时实现小型化、大带宽、频率选择特性好、带外抑制深等优点。Through the above method, this patent breaks through the limitation of the processing accuracy of the existing circuit board process. On the basis of the three-wire coupled transmission line, the passband width is increased by adding short-circuit branch lines, stepped impedance resonators, etc. on the main transmission line. Passband edge selection feature to increase out-of-band rejection. At the same time, in order to further realize the compact circuit structure, combined with the layout of the circuit structure, the structure size and position of the innovative means are calculated by rationally allocating the positions of the pass-band transmission pole and the out-band transmission zero point. Compared with the traditional method, the filter power division circuit designed by the patent of the present invention can simultaneously realize the advantages of miniaturization, large bandwidth, good frequency selection characteristics, and deep out-of-band suppression.
如图4a和图4b所示，其提供了根据本发明提供的改进型谐振器的低阻抗传输线不同线宽和长度时的S21参数图，S21是指所有端口接50欧姆负载时，输入端口到上输出端口的传输系数。图4a中的实线、点划线、点线分别表示在低阻抗线的线宽(W5)等于3.9、2.9、1.9mm时的S21曲线图，图4b中的实线、划线、点划线分别表示在低阻抗线的长度(l2)等于2.8、3.3、3.8mm时的S21曲线图。由图4a和图4b可知，通过减小低阻抗传输线的长度和或增大传输线的宽度时会使谐振频率增大，零点往右移动。因为根据零点产生的条件，零点产生的位置由阻抗比和谐振器的电长度共同决定。As shown in Figure 4a and Figure 4b, which provide theS21 parameter diagram of the low impedance transmission line of the improved resonator provided according to the present invention with different line widths and lengths,S21 refers to when all ports are connected to a 50 ohm load, the input The transfer coefficient of the port to the upper output port. The solid line, dashed-dotted line, and dotted line in Fig. 4a represent theS21 curve when the line width (W5) of the low impedance line is equal to 3.9, 2.9, and 1.9 mm, respectively. The solid line, dashed line, and dotted line in Fig. 4b The dashed lines represent theS21 graphs when the length (l2) of the low impedance line is equal to 2.8, 3.3, and 3.8 mm, respectively. It can be seen from Figure 4a and Figure 4b that by reducing the length of the low-impedance transmission line and or increasing the width of the transmission line, the resonant frequency will increase, and the zero point will move to the right. Because according to the conditions of zero point generation, the position of zero point generation is determined by the impedance ratio and the electrical length of the resonator.
如图5所示，其提供了根据本发明提供的是否加载短路枝节线时分布的S11参数比较图，S11是指输入端口接50欧姆负载时的反射系数。实线、点划线分别代表在在加载短路枝节线和没有加载时的S11曲线图。由图5可知，当加载了短路枝节线后，通带内会额外形成两个传输极点，这将会使通带带宽进一部扩大，并且使通带的裙带变得陡峭，提高了其频率选择性。As shown in FIG. 5 , it provides a comparison diagram ofS11 parameters distributed according to the present invention when the short-circuit branch line is loaded or not,S11 refers to the reflection coefficient when the input port is connected to a 50 ohm load. The solid line and the dashed-dotted line represent the S11 curves when the short-circuit branch line is loaded and when there is no loading, respectively. It can be seen from Figure 5 that when the short-circuit branch line is loaded, two additional transmission poles will be formed in the passband, which will expand the passband bandwidth and make the skirt of the passband steeper, increasing its frequency. Optional.
如图6所示，其提供了根据本发明提供的不同阻值大小的S23参数比较图。S23是指输入端口接负载时，两个输出端口之间的隔离度。实线、点线、点划线依次代表在电阻等于160欧姆、200欧姆、240欧姆时的S23曲线图。由图6可知，当电阻值等于200欧姆，两端口之间在带内会形成的隔离性能优于在电阻等于160欧姆和240欧姆时。因为根据设计步骤中的分析可知，在模式阻抗确定了以后，影响两端口隔离性能的因素将会是电阻阻值的大小。As shown in FIG. 6 , it provides a comparison chart ofS23 parameters of different resistance values provided according to the present invention. S23 refers to the isolation between the two output ports when the input port is connected to the load. The solid line, the dotted line, and the dashed-dotted line represent theS23 graphs at resistances equal to 160 ohms, 200 ohms, and 240 ohms in turn. It can be seen from FIG. 6 that when the resistance value is equal to 200 ohms, the in-band isolation performance between the two ports is better than when the resistance value is equal to 160 ohms and 240 ohms. Because according to the analysis in the design step, after the mode impedance is determined, the factor that affects the isolation performance of the two ports will be the size of the resistance value of the resistor.
如图7所示，显示了根据本发明提供的基于微带三线耦合结构而设计的小型化超宽带滤波功分馈电网络的仿真与测试结果比较图。图7a中的S11是指输入端口接50欧姆负载时的反射系数，S21是指所有端口接50欧姆负载时，输入端口到上输出端口的传输系数，S31是指所有端口接50欧姆负载时，输入端口到下输出端口的传输系数。图7b中的S22是指输出端口接50欧姆负载的反射系数，S23是指输入端口接负载时，两个输出端口之间的隔离度。仿真与测试结果基本吻合，测试结果显示中心频率为3.34GHz，通带内的输出端口的最小插入损耗为3.14dB，3dB相对带宽为95.2％，频率范围为1.75到4.93GHz，两个传输零点位置分别在1.35GHz和5.85GHz，功分端口的隔离度大于10.3dB。As shown in FIG. 7 , it shows a comparison diagram of simulation and test results of the miniaturized ultra-wideband filter power division feeding network designed based on the microstrip three-wire coupling structure provided by the present invention. S11 in Figure 7a refers to the reflection coefficient when the input port is connected to a 50 ohm load, S21 refers to the transmission coefficient from the input port to the upper output port when all ports are connected to a 50 ohm load, and S31 refers to all ports connected to a 50 ohm load Under load, the transfer coefficient from the input port to the lower output port.S22 in Fig. 7b refers to the reflection coefficient of the output port connected to a 50 ohm load, andS23 refers to the isolation degree between the two output ports when the input port is connected to the load. The simulation and test results are basically consistent. The test results show that the center frequency is 3.34GHz, the minimum insertion loss of the output port in the passband is 3.14dB, the 3dB relative bandwidth is 95.2%, the frequency range is 1.75 to 4.93GHz, and the two transmission zero positions are At 1.35GHz and 5.85GHz, the isolation of the power division port is greater than 10.3dB.
以上显示和描述了本发明的基本原理、主要特征和本发明的优点。本行业的技术人员应该了解，本发明不受上述实施例的限制，上述实施例和说明书中描述的只是本发明的原理，在不脱离本发明精神和范围的前提下本发明还会有各种变化和改进，这些变化和改进都落入要求保护的本发明的范围内。本发明要求的保护范围由所附的权利要求书及其等同物界定。The foregoing has shown and described the basic principles, main features and advantages of the present invention. It should be understood by those skilled in the art that the present invention is not limited by the above-mentioned embodiments. The above-mentioned embodiments and descriptions describe only the principles of the present invention. Without departing from the spirit and scope of the present invention, there are various Variations and improvements are intended to fall within the scope of the claimed invention. The scope of protection claimed by the present invention is defined by the appended claims and their equivalents.
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910326287.XACN110034361B (en) | 2019-04-23 | 2019-04-23 | Miniaturized ultra-wideband filtering power division feed network for 5G communication and design method thereof |
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910326287.XACN110034361B (en) | 2019-04-23 | 2019-04-23 | Miniaturized ultra-wideband filtering power division feed network for 5G communication and design method thereof |
| Publication Number | Publication Date |
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| CN110034361Atrue CN110034361A (en) | 2019-07-19 |
| CN110034361B CN110034361B (en) | 2021-04-02 |
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201910326287.XAActiveCN110034361B (en) | 2019-04-23 | 2019-04-23 | Miniaturized ultra-wideband filtering power division feed network for 5G communication and design method thereof |
| Country | Link |
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| CN (1) | CN110034361B (en) |
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