技术领域technical field
本发明涉及电机系统及控制领域，尤其涉及一种开绕组永磁电机零序电流控制方法。The invention relates to the field of motor systems and control, in particular to a zero-sequence current control method for an open-winding permanent magnet motor.
背景技术Background technique
开绕组电机是将传统三相交流电机的中性点打开，构成具有双端口的绕组开放式结构。电机的磁路及结构没有任何改变，开绕组结构电机不改变传统电机的基本性能，并且由于中性点打开之后各相电机绕组之间的约束关系不再存在，各相绕组独立，可以在一定程度上提高电机本体的可靠性和电机驱动系统的容错能力。开绕组电机两个端口可以分别连接变换器，通过两端口的变换器协调控制，可以使各变换器承担一半的功率，较好的地满足了大功率电机系统变对换器的需求，因此开绕组电机控制技术的研究成为当前交流电机研究的重要拓展方向。目前，开绕组永磁电机驱动系统因为兼具传统永磁电机高功率密度、高效率、高性能的特点和开绕组电机的优点已经成为电机系统发展的新方向。The open-winding motor is to open the neutral point of the traditional three-phase AC motor to form an open-winding structure with dual ports. There is no change in the magnetic circuit and structure of the motor, and the open-winding structure motor does not change the basic performance of the traditional motor, and because the constraint relationship between the windings of each phase motor no longer exists after the neutral point is opened, the windings of each phase are independent and can be used at a certain time. To a certain extent, the reliability of the motor body and the fault tolerance of the motor drive system are improved. The two ports of the open-winding motor can be connected to the converters respectively. Through the coordinated control of the two-port converters, each converter can bear half of the power, which better meets the needs of the high-power motor system. The research of winding motor control technology has become an important development direction of current AC motor research. At present, the open-winding permanent magnet motor drive system has become a new direction of motor system development because it combines the characteristics of high power density, high efficiency, and high performance of traditional permanent magnet motors and the advantages of open-winding motors.
根据绕组两端所接变流器供电方式的不同，开绕组永磁电机驱动系统可分为单电源供电的共直流母线型和双电源供电的隔离型两种拓扑结构。与隔离型结构相比，共直流母线型结构因其较低的成本和较小的体积得到广泛应用。在该类结构中，由于变流器、电机和直流母线形成回路，当变流器输出电压含有共模分量时会在回路中形成零序电流，这会对电机轴和开关器件造成危害，因此在开绕组电机的控制中，对共模电压的抑制是一个重要内容。According to the different power supply modes of the converters connected to both ends of the winding, the open-winding permanent magnet motor drive system can be divided into two types of topologies: the common DC bus type with single power supply and the isolated type with dual power supply. Compared with the isolated structure, the common DC bus structure is widely used because of its lower cost and smaller volume. In this type of structure, since the converter, the motor and the DC bus form a loop, when the output voltage of the converter contains a common mode component, a zero-sequence current will be formed in the loop, which will cause harm to the motor shaft and switching devices. In the control of open-winding motors, the suppression of common mode voltage is an important content.
目前开绕组永磁电机零序电流控制多采用基于反馈控制方法，控制器多采用比例谐振(PR)控制器或采用基于锁相环(PLL)的共模电压补偿法。PR控制器需要整定的参数较多且较为复杂，基于锁相环的共模电压补偿法需要在添加零轴控制器的基础上添加额外的锁相环，结构较为复杂。因此研究参数整定更简单的控制器具有重要的工程应用价值。At present, the zero-sequence current control of the open-winding permanent magnet motor mostly adopts the feedback control method, and the controller mostly adopts the proportional resonance (PR) controller or the common mode voltage compensation method based on the phase locked loop (PLL). The PR controller needs to set many parameters and is more complex. The common mode voltage compensation method based on the phase-locked loop needs to add an additional phase-locked loop on the basis of adding the zero-axis controller, and the structure is more complicated. Therefore, the research on the controller with simpler parameter tuning has important engineering application value.
发明内容SUMMARY OF THE INVENTION
本发明提供了一种永磁电机零序电流2自由度PI控制方法，本发明克服了传统开绕组永磁电机零序电流反馈控制中PR控制器参数整定复杂、以及采用基于锁相环的共模电压补偿法中结构复杂的不足，提出一种参数整定更加简单可靠的新型控制器，详见下文描述：The invention provides a 2-degree-of-freedom PI control method for the zero-sequence current of a permanent magnet motor, which overcomes the complex parameter setting of the PR controller in the zero-sequence current feedback control of the traditional open-winding permanent magnet motor, and the use of a phase-locked loop-based common Due to the complex structure of the modulo voltage compensation method, a new controller with simpler and more reliable parameter setting is proposed, as described below:
开绕组永磁电机零序电流2自由度PI控制原理为，通过延迟120°和240°电角度将零轴单相交流回路扩展为虚拟三相回路，所述虚拟三相回路中，原零轴单相回路为a相，经延迟得到的两相作为b相和c相；通过坐标变换将虚拟三相回路变换到dq0坐标系，实现交流量到直流量的转化；The 2-DOF PI control principle of the zero-sequence current of the open-winding permanent magnet motor is to extend the zero-axis single-phase AC circuit into a virtual three-phase circuit by delaying the electrical angle of 120° and 240°. In the virtual three-phase circuit, the original zero-axis The single-phase loop is a-phase, and the two phases obtained by delay are regarded as b-phase and c-phase; the virtual three-phase loop is transformed into the dq0 coordinate system through coordinate transformation to realize the conversion of AC quantity to DC quantity;
设计2自由度PI控制器作为零轴控制器，将2自由度PI控制器的输出变换到三相静止坐标系下得到a、b、c轴的3个分量，将a轴分量作用到调制环节实现零序电流的抑制；Design a 2-DOF PI controller as a zero-axis controller, transform the output of the 2-DOF PI controller into a three-phase static coordinate system to obtain three components of a, b, and c axes, and apply the a-axis component to the modulation link Realize the suppression of zero sequence current;
所述2自由度PI控制器的控制器参数只有一个控制器带宽，易于参数整定；The controller parameters of the 2-DOF PI controller have only one controller bandwidth, which is easy to set parameters;
所述2自由度PI控制器结构如下：The structure of the 2-DOF PI controller is as follows:
式中，u0dq,ref为2自由度PI控制器输出；u'0dq为传统PI控制器的输出；k1c为反馈系数；s为拉普拉斯算子；i0dq,ref为dq坐标系下零轴回路参考值；i0dq为dq坐标系下零轴回路反馈值；αc为控制器带宽；ω3r为三次谐波电角速度；L0为零轴电感；Ra为虚拟有源电阻。In the formula, u0dq,ref is the output of the 2-DOF PI controller; u'0dq is the output of the traditional PI controller; k1c is the feedback coefficient; s is the Laplace operator; i0dq,ref is the dq coordinate system The reference value of the lower zero-axis loop; i0dq is the feedback value of the lower zero-axis loop in the dq coordinate system; αc is the controller bandwidth; ω3r is the third harmonic electrical angular velocity; L0 is the zero-axis inductance; Ra is the virtual active resistance .
所述控制器还包括：The controller also includes:
在αβ坐标系下分别对采样周期的计算延时时间、以及半个采样周期的PWM调制延迟时间进行补偿。In the αβ coordinate system, the calculation delay time of the sampling period and the PWM modulation delay time of half the sampling period are compensated respectively.
本发明提供的技术方案的有益效果是：The beneficial effects of the technical scheme provided by the present invention are:
1、本发明中的零序电流反馈控制器采用2自由度PI(2DOF-PI)控制器，控制器参数只有一个(控制器带宽αc)，且无需附加锁相环环节，简化了控制器的结构和参数整定过程；1. The zero-sequence current feedback controller in the present invention adopts a 2-degree-of-freedom PI (2DOF-PI) controller, with only one controller parameter (controller bandwidth αc ), and no additional phase-locked loop links are required, which simplifies the controller structure and parameter tuning process;
2、克服了传统开绕组永磁电机零序电流反馈控制中PR控制器参数整定复杂、以及采用基于锁相环的共模电压补偿法中结构复杂的不足，满足了实际应用中的多种需要。2. It overcomes the shortcomings of the complex parameter setting of the PR controller in the zero-sequence current feedback control of the traditional open-winding permanent magnet motor and the complex structure of the common-mode voltage compensation method based on the phase-locked loop, and meets various needs in practical applications. .
附图说明Description of drawings
图1为开绕组永磁电机零序电流2自由度PI控制结构图；Figure 1 is a structural diagram of the zero-sequence current 2-DOF PI control of an open-winding permanent magnet motor;
其中，虚框内即为零序回路控制器。Among them, the virtual frame is the zero-sequence loop controller.
图中，θm为转子机械角度；θ为基波电角度；ωm为机械转速；ωm,ref为外部给定参考机械转速，通过外部速度环反馈控制；由转速外环输出iq,ref作为电流内环q轴的给定值，d轴给定值id,ref由外部给定，且id,ref＝0。In the figure, θm is the mechanical angle of the rotor; θ is the fundamental wave electrical angle; ωm is the mechanical speed;ωm,ref is the external reference mechanical speed, which is controlled by the external speed loop feedback;ref is used as the given value of the q-axis of the current inner loop, and the given value of the d-axisid,ref is given externally, and id,ref =0.
通过电流内环反馈控制，经过坐标变换后，得到αβ坐标下参考电压uα,ref和uβ,ref，配合零序电流控制器输出共模电压参考量u0，经过空间矢量调制后生成开关信号Sabc,1和Sabc,2作用到变流器，即可实现对电机的控制。Through the current inner loop feedback control, after coordinate transformation, the reference voltages uα,ref and uβ,ref under the αβ coordinate are obtained, cooperate with the zero-sequence current controller to output the common mode voltage reference u0 , and then generate the switch after space vector modulation The signals Sabc,1 and Sabc,2 act on the converter to control the motor.
图2为零序回路等效电路图；Figure 2 is an equivalent circuit diagram of a zero-sequence loop;
图中，e0是电机三次反电势，u01和u02分别是两个变流器产生的共模电压，i0是零序电流。In the figure, e0 is the third back EMF of the motor, u01 and u02 are the common-mode voltages generated by the two converters, respectively, and i0 is the zero-sequence current.
图3为扩展后的虚拟三相回路等效电路图。FIG. 3 is an equivalent circuit diagram of an expanded virtual three-phase loop.
图中，上虚框表示原有零轴作为虚拟三相回路的a相，下虚框表示经过延迟处理后得到的虚拟零序回路系统的b相和c相。In the figure, the upper dashed box represents the original zero axis as the a-phase of the virtual three-phase loop, and the lower dashed box represents the b-phase and c-phase of the virtual zero-sequence loop system obtained after delay processing.
u0a、i0a、e0a分别为原零序回路中变流器输出共模电压u0、零序电流i0、三次反电势e0。为表述方便，以下采用u0、i0、e0表示。u0a , i0a , and e0a are respectively the output common-mode voltage u0 , the zero-sequence current i0 , and the third-order back EMF e0 of the converter in the original zero-sequence loop. For convenience of expression, u0 , i0 , and e0 are used below to represent.
u0b、i0b、e0b分别为u0、i0、e0经过延迟120°电角度得到；u0c、i0c、e0c分别为u0、i0、e0经过延迟240°电角度得到。u0b , i0b , e0b are obtained by u0 , i0 , e0 after a delay of 120° electrical angle respectively; u0c , i0c , e0c are obtained by u0 , i0 , e0 after a delay of 240° electrical angle get.
具体实施方式Detailed ways
为使本发明的目的、技术方案和优点更加清楚，下面对本发明实施方式作进一步地详细描述：In order to make the purpose, technical solutions and advantages of the present invention clearer, the embodiments of the present invention are described in further detail below:
实施例1Example 1
本发明实施例提供了一种共直流母线型开绕组永磁电机控制系统，该控制系统采用三闭环控制，即速度外环、电流内环、零序电流控制环。三个控制环均采用2自由度PI(2-DOF PI)控制器，其中速度外环和电流内环参考已有文献进行设计整定，本专利对此不在进行说明。零序电流控制环是本发明实施例的核心，本发明实施例对此进行详细说明。The embodiment of the present invention provides a common DC bus type open-winding permanent magnet motor control system, the control system adopts three closed-loop control, that is, a speed outer loop, a current inner loop, and a zero-sequence current control loop. The three control loops all use a 2-degree-of-freedom PI (2-DOF PI) controller, in which the outer speed loop and the inner current loop are designed and adjusted with reference to the existing literature, which is not described in this patent. The zero-sequence current control loop is the core of the embodiments of the present invention, which will be described in detail in the embodiments of the present invention.
在只考虑电机中三次反电势时，电机中的零序电流主要含有三次谐波。在本发明实施例中，得到零序电流后，通过一定时间的延迟(具体延迟时间由转子角速度计算得到，本发明实施例对此不做限制)，将采样得到的零序电流分别延迟120°电角度和240°电角度，这样由采集得到的零序电流和经延时得到的电流可组成三相交流电流，同理对三次反电势进行同样的处理，即将单相零序回路扩展为虚拟三相回路系统。When only considering the third back EMF in the motor, the zero sequence current in the motor mainly contains the third harmonic. In the embodiment of the present invention, after the zero-sequence current is obtained, the zero-sequence current obtained by sampling is delayed by 120° respectively through a delay of a certain time (the specific delay time is calculated from the rotor angular velocity, which is not limited in the embodiment of the present invention). The electrical angle and the 240° electrical angle, so that the zero-sequence current obtained by the collection and the current obtained by the delay can form a three-phase alternating current. Three-phase loop system.
通过坐标变换(变换角度为基波电角度的3倍)，将虚拟三相回路系统转换到两相旋转坐标系(即dq坐标系，该坐标系旋转角速度为基波电角速度的3倍)下，这样就实现零序回路交流量向直流量的转化。Through coordinate transformation (the transformation angle is 3 times the fundamental wave electrical angle), the virtual three-phase loop system is converted into a two-phase rotating coordinate system (ie the dq coordinate system, the rotational angular velocity of this coordinate system is three times the fundamental wave electrical angular velocity) under , so as to realize the conversion of zero-sequence loop AC quantity to DC quantity.
零序回路控制器采用2自由度的PI控制器，当零序电流参考值设为0时即可实现对零序电流的控制。特别的，当需考虑电机中其它次数的谐波时，只需要改变延迟时间即可。The zero-sequence loop controller adopts a PI controller with 2 degrees of freedom. When the zero-sequence current reference value is set to 0, the zero-sequence current can be controlled. In particular, when other harmonics in the motor need to be considered, it is only necessary to change the delay time.
综上所述，本发明实施例通过采用2自由度PI控制器，控制器参数只有一个(控制器带宽αc)，且无需附加锁相环环节，简化了控制器的结构和参数整定过程。To sum up, by using a 2-DOF PI controller in the embodiment of the present invention, there is only one controller parameter (controller bandwidth αc ), and no additional phase-locked loop link is required, which simplifies the structure of the controller and the parameter setting process.
实施例2Example 2
下面结合图1-图3，以及具体的计算公式对实施例1中的方案进行进一步地介绍，详见下文描述：Below in conjunction with Fig. 1-Fig. 3, and the specific calculation formula, the scheme in embodiment 1 is further introduced, see below for details:
图1所示为开绕组永磁电机零序电流2自由度PI控制结构图，速度外环和电流内环都采用2-DOF PI控制。速度外环和电流内环的设计和参数整定方法参考传统电机闭环控制设计方法，且已有大量文献对此作了详细说明，本发明实施例对此不做赘述。下面重点介绍零序回路控制器的设计：Figure 1 shows the open-winding permanent magnet motor zero-sequence current 2-degree-of-freedom PI control structure diagram. Both the speed outer loop and the current inner loop are controlled by 2-DOF PI. The design and parameter setting method of the speed outer loop and the current inner loop refer to the traditional motor closed-loop control design method, which has been described in detail in a large number of documents, and will not be repeated in the embodiment of the present invention. The following focuses on the design of the zero-sequence loop controller:
双变流器供电时，设两个变流器输出的共模电压分别为u01、u02，则作用到电机上的共模电压u0为：When dual-converter supplies power, set the common-mode voltages output by the two converters to be u01 and u02 respectively, then the common-mode voltage u0 acting on the motor is:
u0＝u01-u02 (1)u0 =u01 -u02 (1)
当只考虑反电势中的三次谐波时，三次反电势e0表达式为：When only the third harmonic in the back EMF is considered, the third back EMF e0 is expressed as:
e0＝-ω3rψf3sin(3θ) (2)e0 =-ω3r ψf3 sin(3θ) (2)
式中，Ψf3为转子磁链三次谐波分量，ω3r为三次谐波电角速度，θ为基波电角度。其中，ω3r与基波电角速度ωr的关系为：In the formula, Ψf3 is the third harmonic component of the rotor flux linkage, ω3r is the third harmonic electrical angular velocity, and θ is the fundamental electrical angle. Among them, the relationship between ω3r and the fundamental wave electrical angular velocity ωr is:
ω3r＝3ωr (3)ω3r = 3ωr (3)
此时零序回路方程为：At this time, the zero-sequence loop equation is:
式中，R为电枢电阻，L0为零序回路电感，i0为零序回路电流。零序回路可表示为图2所示。In the formula, R is the armature resistance, L0 is the sequence loop inductance, and i0 is the sequence loop current. The zero sequence loop can be represented as shown in Figure 2.
为了将零序回路电流转化为直流量，将零序回路通过延时扩展为虚拟三相回路系统，具体操作如下：In order to convert the zero-sequence loop current into DC quantity, the zero-sequence loop is extended into a virtual three-phase loop system through delay, and the specific operations are as follows:
将测量得到的零序电流i0作为扩展后三相电流的a相i0a，将该a相电流分别延时120°电角度和240°电角度，得到其它两相电流i0b和i0c，这样就得到了虚拟三相回路系统的电流。同理，将三次反电势e0作为扩展后三相电压的a相e0a，分别延迟120°和240°电角度，得到其它两相e0b和e0c，这样便构成了虚拟三相回路系统的电压，如图3所示。Take the measured zero-sequence current i0 as the a-phase i0a of the expanded three-phase current, delay the a-phase current by 120° electrical angle and 240° electrical angle respectively, and obtain the other two-phase currents i0b and i0c , In this way, the current of the virtual three-phase loop system is obtained. In the same way, take the third back EMF e0 as the a-phase e0a of the expanded three-phase voltage, delay 120° and 240° electrical angle respectively, and obtain the other two phases e0b and e0c , thus forming a virtual three-phase loop system voltage, as shown in Figure 3.
将上述得到的虚拟三相回路系统变换到dq坐标系下，这样就实现了交流量向直流量的转化。构建虚拟三相回路系统时用到的延时时间tb和tc(延迟120°对应于tb，延迟和240°对应于tc)根据转子的转速ωm得到，即：The virtual three-phase loop system obtained above is transformed into the dq coordinate system, so that the conversion of AC quantity to DC quantity is realized. The delay times tb and tc used in constructing the virtual three-phase loop system (120° delay corresponds to tb , and 240° delay corresponds to tc ) are obtained according to the rotor speed ωm , namely:
式中，np为极对数。将扩展后的虚拟三相回路系统转化到dq坐标下，其数学模型为：In the formula, np is the number of pole pairs. Convert the expanded virtual three-phase loop system to dq coordinates, and its mathematical model is:
式中，i0dq为dq坐标下零序电流，u0dq为dq坐标下共模电压，L0为零轴电感，R为定子电阻。In the formula, i0dq is the zero-sequence current under the dq coordinate, u0dq is the common mode voltage under the dq coordinate, L0 is the zero-axis inductance, and R is the stator resistance.
将虚拟三相回路系统中的反电势作为零轴的输入扰动E，则有：Taking the back EMF in the virtual three-phase loop system as the input disturbance E of the zero axis, we have:
E＝jω3rψf3 (7)E=jω3r ψf3 (7)
由式(6)可得虚拟三相回路系统的传递函数可表示为：From equation (6), the transfer function of the virtual three-phase loop system can be expressed as:
其中，s为拉普拉斯算子。Among them, s is the Laplacian operator.
2DOF-PI控制器是在传统PI控制器的基础上增加了反馈环节。2-DOF PI的表达式为：The 2DOF-PI controller adds a feedback link on the basis of the traditional PI controller. The expression for 2-DOF PI is:
其中，u0dq,ref为2DOF-PI控制器的输出；u'0dq为传统PI控制器的输出；k1c为反馈系数；kp为PI控制器比例系数；ki为PI控制器积分系数；i0dq,ref为dq坐标系下零序电流参考值。Wherein, u0dq,ref is the output of the 2DOF-PI controller; u'0dq is the output of the traditional PI controller; k1c is the feedback coefficient; kp is the proportional coefficient of the PI controller; ki is the integral coefficient of the PI controller; i0dq,ref is the zero-sequence current reference value in the dq coordinate system.
由上式(9)可知，由i0dq生成u0dq＇时采用传统PI控制器。It can be known from the above formula (9) that the traditional PI controller is used when u0dq ' is generated from i0dq .
当零序回路采用2-DOF PI控制时，下面介绍控制器设计方法：When the zero-sequence loop adopts 2-DOF PI control, the following describes the controller design method:
由虚拟三相回路系统的方程(6)可以看出，dq轴存在耦合。引入电流反馈控制并对dq轴解耦(即消去方程中的复系数部分)，设：It can be seen from equation (6) of the virtual three-phase loop system that the dq axis is coupled. Introducing current feedback control and decoupling the dq axis (that is, eliminating the complex coefficient part in the equation), set:
u0dq＝u'0dq+(jω3rL0-Ra)i0dq (10)u0dq =u'0dq +(jω3r L0 -Ra )i0dq (10)
式中，Ra为引入的虚拟有源电阻。将式(10)带入虚拟三相回路系统方程(6)中得：In the formula, Ra is the introduced virtual active resistance. Putting equation (10) into equation (6) of virtual three-phase loop system, we get:
上式(11)中电流中不存在复系数，即实现了dq轴电流的解耦。将E作为输入扰动时，此时u0dq＇到i0dq的传递函数可表示为：There is no complex coefficient in the current in the above formula (11), that is, the decoupling of the dq-axis current is realized. When E is perturbed as input, the transfer function from u0dq ' to i0dq can be expressed as:
由上式(9)知，由i0dq生成u0dq＇时采用传统PI控制器时，即：From the above formula (9), when u0dq ' is generated by i0dq , the traditional PI controller is used, namely:
设控制器带宽为αc，则：Let the controller bandwidth be αc , then:
且：and:
所以可以得到2-DOF PI的控制结构为：So the control structure of 2-DOF PI can be obtained as:
式中，u0dq,ref为2-DOF PI控制器输出。In the formula, u0dq,ref is the output of the 2-DOF PI controller.
在实际系统中通常使用数字控制，当控制系统采样周期为Ts时，这时系统存在时间为Td的控制延迟(该延迟时间由两部分组成，即时间为Ts的计算延迟和时间为0.5Ts的PWM调制延迟，此时Td＝1.5Ts)，为了提高控制系统的控制性能，需要对此延迟进行补偿。通常的补偿方法是在两项静止坐标系(即αβ坐标系)下进行补偿。Digital control is usually used in practical systems. When the sampling period of the control system is Ts , the system has a control delay of time Td (this delay time consists of two parts, namely the calculation delay of time Ts and the time of 0.5Ts PWM modulation delay, at this time Td =1.5Ts ), in order to improve the control performance of the control system, this delay needs to be compensated. The usual compensation method is to perform compensation in two stationary coordinate systems (ie αβ coordinate system).
将u0dq,ref变换到αβ坐标系下，当考虑时间补偿(延迟时间Td＝1.5Ts)时，有：Transforming u0dq,ref into the αβ coordinate system, when considering time compensation (delay time Td =1.5Ts ), there are:
式中，u0αβ,ref为αβ坐标内的参考电压。In the formula, u0αβ,ref is the reference voltage in the αβ coordinate.
将u0αβ,ref变换到三相静止坐标下，则a相电压记为u0a，将u0a作为零序控制器的输出(u0)作用到PWM调制环节即可实现零序电流的闭环控制(PWM调制策略可以参考有关文献[1]，此处不做详细说明)。Transform u0αβ,ref into three-phase static coordinates, then the voltage of phase a is recorded as u0a , and the closed-loop control of the zero-sequence current can be realized by applying u0a as the output (u0 ) of the zero-sequence controller to the PWM modulation link (The PWM modulation strategy can refer to the relevant literature[1] , which will not be described in detail here).
综上所述，本发明实施例通过采用2自由度PI控制器，控制器参数只有一个(控制器带宽αc)，且无需附加锁相环环节，简化了控制器的结构和参数整定过程。To sum up, by using a 2-DOF PI controller in the embodiment of the present invention, there is only one controller parameter (controller bandwidth αc ), and no additional phase-locked loop link is required, which simplifies the structure of the controller and the parameter setting process.
参考文献references
[1]Zhou Y,Nian H.Zero-Sequence Current Suppression Strategy of Open-Winding PMSG System With Common DC Bus Based on Zero Vector Redistribution[J].IEEE Transactions on Industrial Electronics,2015,62(6):3399-3408.[1]Zhou Y,Nian H.Zero-Sequence Current Suppression Strategy of Open-Winding PMSG System With Common DC Bus Based on Zero Vector Redistribution[J].IEEE Transactions on Industrial Electronics,2015,62(6):3399-3408 .
本发明实施例对各器件的型号除做特殊说明的以外，其他器件的型号不做限制，只要能完成上述功能的器件均可。In the embodiment of the present invention, the models of each device are not limited unless otherwise specified, as long as the device can perform the above functions.
本领域技术人员可以理解附图只是一个优选实施例的示意图，上述本发明实施例序号仅仅为了描述，不代表实施例的优劣。Those skilled in the art can understand that the accompanying drawing is only a schematic diagram of a preferred embodiment, and the above-mentioned serial numbers of the embodiments of the present invention are only for description, and do not represent the advantages or disadvantages of the embodiments.
以上所述仅为本发明的较佳实施例，并不用以限制本发明，凡在本发明的精神和原则之内，所作的任何修改、等同替换、改进等，均应包含在本发明的保护范围之内。The above descriptions are only preferred embodiments of the present invention, and are not intended to limit the present invention. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present invention shall be included in the protection of the present invention. within the range.
| Application Number | Priority Date | Filing Date | Title |
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| CN201710489411.5ACN107370428B (en) | 2017-06-24 | 2017-06-24 | Two-degree-of-freedom PI control method for zero-sequence current of open-winding permanent magnet motor |
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| CN201710489411.5ACN107370428B (en) | 2017-06-24 | 2017-06-24 | Two-degree-of-freedom PI control method for zero-sequence current of open-winding permanent magnet motor |
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| CN103731079A (en)* | 2013-12-26 | 2014-04-16 | 浙江大学 | Permanent magnet motor system with shared bus structure and open winding and control method for suppressing zero-sequence current |
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