技术领域technical field
本发明涉及功率因数校正(Power Factor Correction,PFC)变换器的控制方法及实现装置，属于电力电子设备领域，具体为一种PFC变换器均值电流控制方法及其装置。The invention relates to a control method and a realization device of a power factor correction (Power Factor Correction, PFC) converter, which belongs to the field of power electronic equipment, in particular to a PFC converter mean value current control method and a device thereof.
背景技术Background technique
随着电力电子技术的发展，电力电子装置的运用越来越广泛。电力电子装置包含有各类非线性器件和储能器件，将其直接接入公共电网使用时，会使电网电流产生畸变，即在电网中注入了大量谐波，严重地影响了电网供电质量和其他用电设备的正常工作运行，甚至会造成用电设备的损坏。With the development of power electronic technology, the application of power electronic devices is becoming more and more extensive. Power electronic devices contain various nonlinear devices and energy storage devices. When they are directly connected to the public grid, the grid current will be distorted, that is, a large number of harmonics will be injected into the grid, which seriously affects the power supply quality and The normal operation of other electrical equipment may even cause damage to electrical equipment.
为了保证公共电网的正常供电，需要使用PFC技术，即使用滤波器。滤波器可以分为无源滤波器和有源滤波器，无源滤波器具有结构简单、成本低、可靠性高和EMI小等优点，但它的尺寸和重量大，工作性能受工作频率变化、负载变化和输入电压变化的影响。有源滤波器的功率因数校正性能好，其功率因数可以到达90％以上，使输入电流接近正弦。有源滤波器可以在较宽的输入电压范围和宽频带下工作，并且其体积和重量小，能稳定输出电压值。因此，有源PFC技术在工业中得到了广泛的应用。In order to ensure the normal power supply of the public grid, PFC technology needs to be used, that is, a filter is used. Filters can be divided into passive filters and active filters. Passive filters have the advantages of simple structure, low cost, high reliability and low EMI, but their size and weight are large, and their performance is affected by changes in operating frequency, effects of load changes and input voltage changes. The power factor correction performance of the active filter is good, and its power factor can reach more than 90%, making the input current close to sinusoidal. The active filter can work in a wide input voltage range and a wide frequency band, and its volume and weight are small, and it can stabilize the output voltage value. Therefore, active PFC technology has been widely used in industry.
传统的有源PFC变换器的控制方法分为变频控制和定频控制，变频控制主要为电流滞环控制；定频控制主要有峰值电流控制和平均电流控制。电流滞环控制PFC变换器的功率因数高，响应速度快，但是工作频率不固定，输出滤波器难于设计；峰值电流控制PFC变换器的功率因数较低，无法满足总谐波畸变(Total Harmonic Distortion，THD)的要求，并且该控制方法对噪声相当敏感；平均电流控制PFC变换器具有较高的功率因数和很小的THD，对噪声不敏感，并且可以适用于电感电流连续导电模式(continuous conduction mode,CCM)和断续导电模式(discontinuous conduction mode,DCM)。然而，平均电流控制使用了两个PI补偿器，因此平均电流控制的瞬态响应速度较慢。其中，外环PI补偿器用于调节输出电压，使之稳定；内环PI补偿器用于使电感电流跟随参考值；用其他方法替代内环PI补偿器，能有效地提高瞬态响应速度。The control methods of the traditional active PFC converter are divided into variable frequency control and fixed frequency control. The variable frequency control is mainly current hysteresis control; the fixed frequency control mainly includes peak current control and average current control. The power factor of the current hysteresis control PFC converter is high and the response speed is fast, but the operating frequency is not fixed, and the output filter is difficult to design; the power factor of the peak current control PFC converter is low, which cannot meet the total harmonic distortion (Total Harmonic Distortion) , THD) requirements, and the control method is quite sensitive to noise; the average current control PFC converter has a high power factor and small THD, is not sensitive to noise, and can be applied to the continuous conduction mode of the inductor current (continuous conduction mode, CCM) and discontinuous conduction mode (discontinuous conduction mode, DCM). However, the average current control uses two PI compensators, so the transient response of the average current control is slower. Among them, the outer loop PI compensator is used to adjust the output voltage to make it stable; the inner loop PI compensator is used to make the inductor current follow the reference value; replacing the inner loop PI compensator with other methods can effectively improve the transient response speed.
发明内容Contents of the invention
本发明的目的是提供一种PFC变换器均值电流控制方法及其装置，使之同时具有较高的功率因数(Power Factor,PF)值、较快的瞬态响应速度和较高的效率，适用于各类基本的PFC变换器拓扑。The purpose of the present invention is to provide a PFC converter average current control method and its device, so that it has a higher power factor (Power Factor, PF) value, faster transient response speed and higher efficiency at the same time, suitable for In all kinds of basic PFC converter topologies.
本发明实现其发明目的所采用的技术方案如下：The present invention realizes the technical scheme that its object of the invention adopts as follows:
一种功率因数校正变换器均值电流控制方法，在每个开关周期开始时刻，检测整流桥的输出电压和输出电流以及所述功率因数校正变换器的输出电压，分别得到信号Vs、In和Vn；将Vs送入放大器得到信号Vc，将Vn和电压基准值Vref送入补偿器得到信号Ve，将Vc和Ve送入乘法器得到信号Ic；将In、Vs、Ic和Vn送入第一占空比生成器得到信号dx1和dx2，将dx1和dx2送入第一脉宽调制器得到信号VP1；将In、Vs、Ic和Vn送入第二占空比生成器得到信号dy1和dy2，将dy1和dy2送入第二脉宽调制器得到信号VP2；将In、Vs、Ic和Vn送入判断器得到信号Vj；将VP1、VP2和Vj送入选择器得到信号VP，用以控制所述功率因数校正变换器开关管的导通与关断。A power factor correction converter average current control method, at the beginning of each switching cycle, the output voltage and output current of the rectifier bridge and the output voltage of the power factor correction converter are detected, and the signals Vs ,In and Vn ; send Vs to the amplifier to get signal Vc , send Vn and voltage reference value Vref to compensator to get signal Ve , send Vc and Ve to multiplier to get signal Ic ; putIn , Vs , Ic and Vn are sent to the first duty cycle generator to obtain signals dx1 and dx2 , and dx1 and dx2 are sent to the first pulse width modulator to obtain signal VP1;s , Ic and Vn are sent to the second duty ratio generator to obtain signals dy1 and dy2 , and dy1 and dy2 are sent to the second pulse width modulator to obtain signal VP2 ; In, Vs, Ic and Vn are sent to the judger to obtain the signal Vj ; VP1 , VP2 and Vj are sent to the selector to obtain the signal VP , which is used to control the turn-on and turn-off of the switch tube of the power factor correction converter .
进一步地，所述将In、Vs、Ic和Vn送入第一占空比生成器得到信号dx1和dx2的方法是，根据当前开关周期结束时的电感电流值等于Ic以及dx1等于dx2，第一占空比生成器计算dx1和dx2，dx1＝dx2＝0.5[K1+K2(Ic-In)]；所述将In、Vs、Ic和Vn送入第二占空比生成器得到信号dy1和dy2的方法是，根据当前开关周期结束时的电感电流值等于Ic以及当前开关周期内电感电流的平均值等于Ic，第二占空比生成器计算dy1和dy2，dy1＝K3In+(K4In2+K5Ic2+K6Ic)1/2,dy2＝K7Ic；其中K1、K2、K3、K4、K5、K6和K7是与信号Vn、Vs以及所述功率因数校正变换器的电感电流纹波相关的系数。Further, the method of sendingIn , Vs , Ic and Vn to the first duty cycle generator to obtain signals dx1 and dx2 is that according to the inductor current value at the end of the current switching period is equal to Ic and dx1 isequal to dx2 , the first duty cycle generator calculates dx1 and dx2 , dx1 =dx2 =0.5[K1 +K2 (Ic −In )];s , Ic and Vn are sent to the second duty ratio generator to obtain signals dy1 and dy2 according to the fact that the inductor current value at the end of the current switching cycle is equal to Ic and the average value of the inductor current in the current switching cycle equal to Ic , the second duty cycle generator calculates dy1 and dy2 , dy1 =K3 In +(K4 In2 +K5 Ic2 +K6 Ic )1/2 ,dy2 = K7 Ic ; where K1 , K2 , K3 , K4 , K5 , K6 and K7 are related to the signals Vn , Vs and the inductor current ripple of the power factor correction converter coefficient.
一种功率因数校正变换器均值电流控制装置，包括电流检测电路IS、第一电压检测电路VS1、第二电压检测电路VS2、补偿器EC、放大器GA、乘法器MUL、第一占空比生成器DG1、第二占空比生成器DG2、第一脉宽调制器DP1、第二脉宽调制器DP2、判断器JU和选择器CH；第一电压检测电路VS1、放大器GA、乘法器MUL依次相连；第二电压检测电路VS2、补偿器EC、乘法器MUL依次相连；电流检测电路IS与第一占空比生成器DG1、判断器JU、第二占空比生成器DG2分别相连；第一电压检测电路VS1与第一占空比生成器DG1、判断器JU、第二占空比生成器DG2分别相连；第二电压检测电路VS2与第一占空比生成器DG1、判断器JU、第二占空比生成器DG2分别相连；乘法器MUL与第一占空比生成器DG1、判断器JU、第二占空比生成器DG2分别相连；第一占空比生成器DG1、第一脉宽调制器DP1、选择器CH依次相连；判断器JU与选择器CH相连；第二占空比生成器DG2、第二脉宽调制器DP2、选择器CH依次相连。A power factor correction converter average current control device, including a current detection circuit IS, a first voltage detection circuit VS1, a second voltage detection circuit VS2, a compensator EC, an amplifier GA, a multiplier MUL, and a first duty cycle generator DG1, the second duty ratio generator DG2, the first pulse width modulator DP1, the second pulse width modulator DP2, the judger JU and the selector CH; the first voltage detection circuit VS1, the amplifier GA, and the multiplier MUL are connected in sequence ; The second voltage detection circuit VS2, the compensator EC, and the multiplier MUL are connected in sequence; the current detection circuit IS is connected to the first duty cycle generator DG1, the judging device JU, and the second duty cycle generator DG2 respectively; the first voltage The detection circuit VS1 is connected to the first duty cycle generator DG1, the judger JU, and the second duty cycle generator DG2 respectively; the second voltage detection circuit VS2 is connected to the first duty cycle generator DG1, the judger JU, and the second duty cycle generator DG1. The duty ratio generator DG2 is connected respectively; the multiplier MUL is connected with the first duty ratio generator DG1, the judging unit JU, and the second duty ratio generator DG2 respectively; the first duty ratio generator DG1, the first pulse width The modulator DP1 is connected to the selector CH in sequence; the judger JU is connected to the selector CH; the second duty ratio generator DG2 is connected to the second pulse width modulator DP2 and the selector CH in sequence.
与现有技术相比，本发明的有益效果是：Compared with prior art, the beneficial effect of the present invention is:
一、与传统平均电流控制的PFC变换器相比，本发明的PFC变换器在每个开关周期开始时，计算该周期的电感电流平均值，并通过控制开关管导通与关断的方式实现对平均值的跟踪，提高了PFC变换器的PF值。1. Compared with the PFC converter of traditional average current control, the PFC converter of the present invention calculates the average value of the inductor current of this cycle at the beginning of each switching cycle, and realizes it by controlling the switch tube to be turned on and off. The tracking of the average value improves the PF value of the PFC converter.
二、与传统平均电流控制的PFC变换器相比，本发明的PFC变换器在负载发生变化时，根据占空比算法有效地调整了每个开关周期内开关管导通与关断的时间，使电感电流值快速跟随平均值，提高了PFC变换器的负载瞬态性能。Two, compared with the PFC converter of traditional average current control, when the load changes, the PFC converter of the present invention effectively adjusts the turn-on and turn-off time of the switch tube in each switching cycle according to the duty ratio algorithm, The inductor current value follows the average value quickly, and the load transient performance of the PFC converter is improved.
三、与传统平均电流控制的PFC变换器相比，本发明的PFC变换器在输入电压过零时，减小了电感电流的畸变，从而减少了损耗，提高了PFC变换器的效率。3. Compared with the traditional average current control PFC converter, the PFC converter of the present invention reduces the distortion of the inductor current when the input voltage crosses zero, thereby reducing the loss and improving the efficiency of the PFC converter.
附图说明Description of drawings
图1为本发明实施例一方法的信号流程框图。FIG. 1 is a block diagram of a signal flow of a method according to an embodiment of the present invention.
图2为本发明实施例一的电路结构框图。FIG. 2 is a block diagram of the circuit structure of Embodiment 1 of the present invention.
图3a为本发明实施例一的第一脉宽调制器DP1算法示意图。Fig. 3a is a schematic diagram of an algorithm of the first pulse width modulator DP1 according to Embodiment 1 of the present invention.
图3b为本发明实施例一的第二脉宽调制器DP2算法示意图。Fig. 3b is a schematic diagram of an algorithm of the second pulse width modulator DP2 according to Embodiment 1 of the present invention.
图4为本发明实施例一PFC变换器稳态工作时的输入电压Vin和输入电流Iin的时域仿真波形图。FIG. 4 is a time-domain simulation waveform diagram of the input voltage Vin and the input current Iin when the PFC converter operates in a steady state according to Embodiment 1 of the present invention.
图5为分别采用本发明和传统平均电流控制的PFC变换器随负载电阻变化时的PF值曲线图。Fig. 5 is a curve diagram of PF value when the load resistance changes with the PFC converter adopting the present invention and the traditional average current control respectively.
图6为分别采用本发明和传统平均电流控制的PFC变换器随输入电压幅值变化时的PF值曲线图。Fig. 6 is a curve diagram of PF value when the input voltage amplitude varies with the PFC converter adopting the present invention and the traditional average current control respectively.
图7a为本发明实施例一PFC变换器在负载电阻由100Ω跳变到400Ω时输出电压瞬态时域仿真波形图。Fig. 7a is a time-domain simulation waveform diagram of output voltage transient when the load resistance of the PFC converter according to the embodiment of the present invention jumps from 100Ω to 400Ω.
图7b为采用传统平均电流控制的PFC变换器在负载电阻由100Ω跳变到400Ω时输出电压瞬态时域仿真波形图。Fig. 7b is a time-domain simulation waveform diagram of output voltage transient when the load resistance jumps from 100Ω to 400Ω of the PFC converter adopting traditional average current control.
图8a为本发明实施例一PFC变换器在负载电阻由500Ω跳变到400Ω时输出电压瞬态时域仿真波形图。Fig. 8a is a time-domain simulation waveform diagram of output voltage transient when the load resistance of the PFC converter according to the embodiment of the present invention jumps from 500Ω to 400Ω.
图8b为采用传统平均电流控制的PFC变换器在负载电阻由500Ω跳变到400Ω时输出电压瞬态时域仿真波形图。Fig. 8b is a time-domain simulation waveform diagram of output voltage transient when the load resistance jumps from 500Ω to 400Ω of the PFC converter adopting traditional average current control.
图9为分别采用本发明和传统平均电流控制的PFC变换器随负载变化时的效率曲线图。Fig. 9 is a graph showing efficiency curves of PFC converters using the present invention and conventional average current control as the load varies.
图10为本发明实施例二的电路结构图。FIG. 10 is a circuit structure diagram of Embodiment 2 of the present invention.
具体实施方式Detailed ways
下面通过具体的实例并结合附图对本发明做进一步详细的描述。The present invention will be further described in detail through specific examples and in conjunction with the accompanying drawings.
实施例一Embodiment one
图1示出，本发明的一种具体实施方式为：PFC变换器均值电流控制方法及其装置，包括电流检测电路IS、第一电压检测电路VS1、第二电压检测电路VS2、补偿器EC、放大器GA、乘法器MUL、第一占空比生成器DG1、第二占空比生成器DG2、第一脉宽调制器DP1、第二脉宽调制器DP2、判断器JU和选择器CH组成；电流检测电路IS用于获得整流桥的输出电流信息In，第一电压检测电路VS1用于获得整流桥的输出电压信息Vs、第二电压检测电路VS2用于获取变换器TD输出电压信息Vn，补偿器EC用于生成误差信号Ve，判断器JU用于生成选择信号Vj，判断电路工作在CCM或者DCM，第一占空比生成器DG1用于产生CCM占空比信号dx1和dx2，第二占空比生成器DG2用于产生DCM占空比信号dy1和dy2，第一脉宽调制器DP1用于产生CCM的控制时序VP1；第二脉宽调制器DP2用于产生DCM的控制时序VP2，选择器CH用于选择CCM或者DCM的控制时序，并输出控制信号VP，控制PFC变换器TD开关管的导通和关断。Figure 1 shows that a specific embodiment of the present invention is: PFC converter average current control method and device thereof, including a current detection circuit IS, a first voltage detection circuit VS1, a second voltage detection circuit VS2, a compensator EC, Amplifier GA, multiplier MUL, first duty ratio generator DG1, second duty ratio generator DG2, first pulse width modulator DP1, second pulse width modulator DP2, judger JU and selector CH; The current detection circuit IS is used to obtain the output current information In of the rectifier bridge, the first voltage detection circuit VS1 is used to obtain the output voltage information Vs of the rectifier bridge, and the second voltage detection circuit VS2 is used to obtain the output voltage information V of the converter TDn , the compensator EC is used to generate the error signal Ve , the judger JU is used to generate the selection signal Vj , the judgment circuit works in CCM or DCM, and the first duty ratio generator DG1 is used to generate the CCM duty ratio signal dx1 and dx2 , the second duty cycle generator DG2 is used to generate DCM duty cycle signals dy1 and dy2 , the first pulse width modulator DP1 is used to generate CCM control timing VP1 ; the second pulse width modulator DP2 It is used to generate the control sequence VP2 of DCM. The selector CH is used to select the control sequence of CCM or DCM, and output the control signal VP to control the turn-on and turn-off of the TD switch tube of the PFC converter.
其工作过程为，将Vn和预设的基准电压Vref送入补偿器EC用于生成误差信号Ve；放大器GA用于放缩整流桥输出电压信号Vs，得到整流桥输出电压参考信号Vc；将Vc和Ve送入乘法器得到电感电流平均值参考信号Ic，用于占空比信号dx1和dx2、dy1和dy2的计算以及选择信号Vj的计算；第一占空比生成器DG1用于产生第一脉宽调制器DP1计算所需的占空比信号dx1和dx2，dx1＝dx2＝0.5[K1+K2(Ic-In)]；第二占空比生成器DG2用于产生第二脉宽调制器DP2计算所需的占空比信号dy1和dy2，dy1＝K3In+(K4In2+K5Ic2+K6Ic)1/2,dy2＝K7Ic；判断器JU用于生成选择信号Vj，判断电路工作在CCM或者DCM，当Vj＝1时，电路工作在CCM，当Vj＝0时，电路工作在DCM；其中K1、K2、K3、K4、K5、K6和K7是与信号Vn、Vs以及所述功率因数校正变换器的电感电流纹波相关的系数。第一脉宽调制器DP1用于产生CCM时变换器TD开关管导通和关断的控制时序VP1；第二脉宽调制器DP2用于产生DCM时变换器TD开关管导通和关断的控制时序VP2；选择器CH用于根据选择信号Vj选择控制时序VP1或VP2，并产生控制信号VP。Its working process is that Vn and the preset reference voltage Vref are sent to the compensator EC to generate the error signal Ve ; the amplifier GA is used to scale the output voltage signal Vs of the rectifier bridge to obtain the output voltage reference signal of the rectifier bridge Vc ; send Vc and Ve into the multiplier to obtain the reference signal Ic of the average value of the inductor current, which is used for the calculation of the duty cycle signals dx1 and dx2 , dy1 and dy2 and the calculation of the selection signal Vj ; The first duty ratio generator DG1 is used to generate the duty ratio signals dx1 and dx2 required for the calculation of the first pulse width modulator DP1, dx1 =dx2 =0.5[K1 +K2 (Ic -In )]; the second duty ratio generator DG2 is used to generate the duty ratio signals dy1 and dy2 required for the calculation of the second pulse width modulator DP2, dy1 =K3 In +(K4 In2 +K5 Ic2 +K6 Ic )1/2 , dy2 =K7 Ic ; the judging unit JU is used to generate the selection signal Vj , the judging circuit works in CCM or DCM, when Vj =1, The circuit works in CCM, and when Vj =0, the circuit works in DCM; where K1 , K2 , K3 , K4 , K5 , K6 and K7 are related to the signals Vn , Vs and the power Factor correction coefficients related to the inductor current ripple of the converter. The first pulse width modulator DP1 is used to control the timing VP1 of the turn-on and turn-off of the converter TD switch tube when generating CCM; the second pulse width modulator DP2 is used to turn on and turn off the converter TD switch tube when generating DCM The control sequence VP2 ; the selector CH is used to select the control sequence VP1 or VP2 according to the selection signal Vj and generate the control signal VP .
上述K1、K2、K3、K4、K5、K6和K7的具体表达式如下：其中Ts为开关周期，m1和m2分别为电感电流变化的上升斜率和下降斜率，即：The specific expressions of the above K1 , K2 , K3 , K4 , K5 , K6 and K7 are as follows: Where Ts is the switching period, m1 and m2 are the rising slope and falling slope of the inductor current change, namely:
图2示出，本例的PFC变换器均值电流控制的实现装置，由变换器TD和控制装置组成。Fig. 2 shows that the implementation device of the PFC converter average current control in this example is composed of a converter TD and a control device.
本例的装置其工作过程和原理是：Its work process and principle of the device of this example are:
在每个开关周期开始时，检测变换器TD整流桥的输出电压和输出电流以及变换器TD的输出电压，得到信号Vs、In和Vn；将Vs经过放大器得到Vc，将Vn和Vref经过补偿器得到误差信号Ve,将Vc和Ve经过乘法器得到信号Ic；将In、Vs、Ic和Vn送入第一占空比生成器得到信号dx1和dx2，将dx1和dx2送入第一脉宽调制器得到信号VP1；将In、Vs、Ic和Vn送入第二占空比生成器得到信号dy1和dy2，将dy1和dy2送入第二脉宽调制器得到信号VP2；将In、Vs、Ic和Vn送入判断器得到信号Vj；将VP1、VP2和Vj送入选择器得到信号VP，控制功率因数校正变换器开关管的导通与关断。At the beginning of each switching cycle, the output voltage and current of the converter TD rectifier bridge and the output voltage of the converter TD are detected to obtain signals Vs ,In and Vn ; Vs is passed through the amplifier to obtain Vc , and Vn and Vref go through the compensator to get the error signal Ve , pass Vc and Ve through the multiplier to get the signal Ic ; sendIn , Vs , Ic and Vn to the first duty cycle generator to get the signal dx1 and dx2 , send dx1 and dx2 to the first pulse width modulator to get the signal VP1 ; sendIn , Vs , Ic and Vn to the second duty cycle generator to get the signal dy1 and dy2 , send dy1 and dy2 to the second pulse width modulator to get signal VP2 ; sendIn , Vs , Ic and Vn to the judger to get signal Vj ; put VP1 and VP2 and Vj are sent to the selector to obtain the signal VP to control the on and off of the switching tube of the power factor correction converter.
图3a为占空比dx1和dx2生成示意图,第一占空比生成器DG1的工作原理为：每个开关周期开始时，计算占空比dx1和dx2，计算条件为：①当前开关周期结束时的电感电流值等于Ic，②两段占空比相等。计算得到占空比dx1＝dx2＝0.5[K1+K2(Ic-In)],其中K1和K2为两个与信号Vn、Vs以及电感电流纹波相关的系数。图3b为占空比dy1和dy2生成示意图，第二占空比生成器DG2的工作原理为：每个开关周期开始时，计算占空比dy1和dy2，计算条件为：①当前开关周期结束时的电感电流值等于Ic，②当前开关周期内电感电流的平均值等于Ic。计算得到占空比dy1＝K3In+(K4In2+K5Ic2+K6Ic)1/2,dy2＝K7Ic，其中K3、K4、K5、K6和K7是与信号Vn、Vs以及电感电流纹波相关的系数。Figure 3a is a schematic diagram of the generation of duty ratios dx1 and dx2 . The working principle of the first duty ratio generator DG1 is: at the beginning of each switching cycle, the duty ratios dx1 and dx2 are calculated. The calculation conditions are: ① current The inductor current value at the end of the switching cycle is equal to Ic , and ② the duty ratios of the two sections are equal. Calculate the duty cycle dx1 =dx2 =0.5[K1 +K2 (Ic -In )], where K1 and K2 are two related to the signal Vn , Vs and the inductor current ripple coefficient. Figure 3b is a schematic diagram of the generation of duty ratios dy1 and dy2 , the working principle of the second duty ratio generator DG2 is: at the beginning of each switching cycle, the duty ratios dy1 and dy2 are calculated, and the calculation conditions are: ① current The inductor current value at the end of the switching cycle is equal to Ic , ② the average value of the inductor current in the current switching cycle is equal to Ic . Calculate the duty cycle dy1 = K3 In + (K4 In2 + K5 Ic2 + K6 Ic )1/2 , dy2 = K7 Ic , where K3 , K4 , K5 , K6 and K7 are coefficients related to the signals Vn , Vs and the inductor current ripple.
本例的变换器TD为Boost PFC变换器。The converter TD in this example is a Boost PFC converter.
用PSIM仿真软件对本例的方法进行时域仿真分析，结果如下。Use PSIM simulation software to carry on time domain simulation analysis to the method of this example, the result is as follows.
图4为本发明实施例一PFC变换器稳态工作时的输入电压Vin和输入电流Iin的时域仿真波形图。此时输入电流波形接近正弦，并与输入电压没有相位差，实现了功率因数校正的功能。仿真条件：输入电压Vin是幅值为200V、频率为50Hz的交流电压，参考电压Vref＝4V(对应输出电压400V)、电感L＝200μH、电容C＝470μF(其等效串联电阻为1mΩ)、负载电阻R＝100Ω、开关周期Ts＝20μs，补偿器参数为KP＝0.1、KI＝5。FIG. 4 is a time-domain simulation waveform diagram of the input voltage Vin and the input current Iin when the PFC converter operates in a steady state according to Embodiment 1 of the present invention. At this time, the input current waveform is close to sinusoidal, and there is no phase difference with the input voltage, realizing the function of power factor correction. Simulation conditions: the input voltage Vin is an AC voltage with an amplitude of 200V and a frequency of 50Hz, a reference voltage Vref = 4V (corresponding to an output voltage of 400V), an inductance L = 200μH, and a capacitance C = 470μF (its equivalent series resistance is 1mΩ ), load resistance R=100Ω, switching period Ts =20 μs, compensator parameters KP =0.1, KI =5.
图5为分别采用本发明和传统平均电流控制的PFC变换器随负载变化时的PF值曲线图。仿真条件与图4相同，负载电阻的变化范围为50Ω～500Ω。在负载电阻较大时，两种控制方法下PFC变换器具有相似的PF值。当负载电阻大于200Ω时，随着负载电阻的增大，两种控制方法下PFC变换器的PF值均减小；当负载电阻小于200Ω时，随着负载电阻的减小，传统平均电流控制PFC变换器的PF值减小，而本发明的PF值增加。在负载电阻变化范围内，本发明的PF值均高于99％。因此采用本发明的PFC变换器在不同负载下均有良好的PF值。Fig. 5 is a curve diagram of PF value when the load varies with the PFC converter adopting the present invention and the traditional average current control respectively. The simulation conditions are the same as those in Fig. 4, and the variation range of the load resistance is 50Ω-500Ω. When the load resistance is large, the PFC converter has similar PF values under the two control methods. When the load resistance is greater than 200Ω, as the load resistance increases, the PF value of the PFC converter under the two control methods decreases; when the load resistance is less than 200Ω, as the load resistance decreases, the traditional average current control PFC The PF value of the converter decreases, while the PF value of the present invention increases. Within the changing range of load resistance, the PF values of the present invention are all higher than 99%. Therefore, the PFC converter adopting the present invention has good PF values under different loads.
图6为分别采用本发明和传统平均电流控制的PFC变换器随输入电压幅值变化时的PF值曲线图。仿真条件与图4相同，输入电压幅值变化范围为180V～250V。随着输入电压幅值的减小时，两种控制下PFC变换器的PF值均减小，但是本发明的PF值均高于传统平均电流控制PFC变换器的PF值，并保持在99.5％以上。故本发明在不同输入电压幅值下具有良好的功率因数校正功能。Fig. 6 is a curve diagram of PF value when the input voltage amplitude varies with the PFC converter adopting the present invention and the traditional average current control respectively. The simulation conditions are the same as those in Figure 4, and the range of input voltage amplitude is 180V-250V. With the decrease of the input voltage amplitude, the PF value of the PFC converter under the two kinds of control all decreases, but the PF value of the present invention is higher than the PF value of the traditional average current control PFC converter, and remains above 99.5%. . Therefore, the present invention has a good power factor correction function under different input voltage amplitudes.
图7a和图7b分别为本发明、传统平均电流控制的PFC变换器在负载电阻由100Ω跳变到400Ω时输出电压瞬态时域仿真波形图，变换器仿真条件与图4相同。此时，变换器工作模式由CCM变化为DCM。图7可知，负载变化后，两种控制方法均能使电压稳定在400V，传统平均电流控制PFC变换器经过0.22s的时间恢复到400V；采用本发明的PFC变换器经过0.1s的时间恢复到400V，并且本发明的输出电压峰值波动小于传统平均电流控制，由此可知本发明拥有更快的负载瞬态响应速度。Fig. 7a and Fig. 7b are the time-domain simulation waveforms of output voltage transient when the load resistance jumps from 100Ω to 400Ω of the present invention and the traditional average current control PFC converter respectively, and the simulation conditions of the converter are the same as those in Fig. 4 . At this time, the working mode of the converter changes from CCM to DCM. It can be seen from Figure 7 that after the load changes, both control methods can stabilize the voltage at 400V, and the traditional average current control PFC converter returns to 400V after 0.22s; the PFC converter of the present invention returns to 400V after 0.1s. 400V, and the output voltage peak fluctuation of the present invention is smaller than the traditional average current control, so it can be seen that the present invention has faster load transient response speed.
图8a和图8b分别为本发明、传统平均电流控制的PFC变换器在负载电阻由500Ω跳变到400Ω时输出电压瞬态时域仿真波形图，变换器仿真条件与图4相同。此时，变换器均工作在DCM。由图8可知，本发明的调节时间为0.8s，传统平均电流控制的调节时间为1.3s。本发明的输出电压谷值波动约为4V，传统平均电流控制的输出电压谷值波动约为7V。对比可知，PFC变换器工作在DCM时，本发明具有更好的负载瞬态性能。Fig. 8a and Fig. 8b are respectively the time-domain simulation waveforms of the output voltage transient of the PFC converter of the present invention and the traditional average current control when the load resistance jumps from 500Ω to 400Ω, and the simulation conditions of the converter are the same as those in Fig. 4 . At this time, the converters all work in DCM. It can be seen from FIG. 8 that the adjustment time of the present invention is 0.8s, and the adjustment time of the traditional average current control is 1.3s. The valley value fluctuation of the output voltage of the present invention is about 4V, and the valley value fluctuation of the output voltage of the traditional average current control is about 7V. It can be seen from the comparison that when the PFC converter works in DCM, the present invention has better load transient performance.
图9为分别采用本发明和传统平均电流控制的PFC变换器随负载变化时的效率曲线图。变换器仿真条件与图4相同，负载电阻的变化范围为50Ω～500Ω。随着负载电阻的增加，两种控制下PFC变换器的效率均减小。在整个负载变化中，相比于传统平均电流控制，本发明具有更高的效率，并且效率均高于90％。由此可知，采用本发明的PFC变换器拥有较高的工作效率。Fig. 9 is a graph showing efficiency curves of PFC converters using the present invention and conventional average current control as the load varies. The simulation condition of the converter is the same as that in Fig. 4, and the variation range of the load resistance is 50Ω-500Ω. With the increase of the load resistance, the efficiency of the PFC converter under the two kinds of control decreases. In the whole load change, compared with the traditional average current control, the present invention has higher efficiency, and the efficiency is higher than 90%. It can be known that the PFC converter adopting the present invention has higher working efficiency.
实施例二Embodiment two
如图10所示，本例与实施例一基本相同，不同之处是：本例控制的变换器TD为Buck-boost PFC变换器。As shown in FIG. 10 , this example is basically the same as the first example, except that the converter TD controlled in this example is a Buck-boost PFC converter.
本发明除可用于以上实施例中的PFC变换器外，也可用于反激PFC变换器、半桥PFC变换器、全桥PFC变换器等PFC变换器拓扑中。In addition to the PFC converters in the above embodiments, the present invention can also be used in PFC converter topologies such as flyback PFC converters, half-bridge PFC converters, and full-bridge PFC converters.
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| CN201610720055.9ACN106253657B (en) | 2016-08-24 | 2016-08-24 | Power factor correcting converter mean value current control method and its device |
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